Micropower Step-Up/Step-Down Fixed 3.3 V, 5 V, 12 V,
Adjustable High Frequency Switching Regulator
ADP3000
FEATURES
FUNCTIONAL BLOCK DIAGRAMS
ILIM
1.245V
REFERENCE
SW1
400kHz
OSCILLATOR
DRIVER
COMPARATOR
R1
R2
GND
SW2
ADP3000
SENSE
Figure 1.
VIN
2V TO 3.2V
100µF
10V
O
3.3V
180mA
120V
1
2
ILIM
VIN
SW1 3
FB
8
(SENSE)
GND
SW2
5
4
+
C1
100µF
10V
C1, C2 = AVX TPS D107 M010R0100
L1 = SUMIDA CR43-6R8
00122-002
B
SO
Operating in pulse frequency mode (PFM), the device consumes
only 500 µA, making it ideal for applications requiring low
quiescent current. It delivers an output current of 180 mA at
3.3 V from a 2 V input in step-up mode, and an output current
of 100 mA at 3 V from a 5 V input in step-down mode.
The auxiliary gain amplifier can be used as a low battery detector,
linear regulator, undervoltage lockout, or error amplifier.
IN5817
ADP3000-3.3V
The ADP3000 is a versatile step-up/step-down switching
regulator. It operates from an input supply voltage of 2 V to
12 V in step-up mode, and from 2 V to 30 V in step-down mode.
The ADP3000 operates at 400 kHz switching frequency. This
allows the use of small external components (inductors and
capacitors), making it convenient for space-constrained designs.
6.8µH
Figure 2. Typical Application
VIN
5V TO 6V
C1
100µF
10V
RLIM
120Ω
1
ILIM
2
3
VIN SW1
FB 8
ADP3000
SW2 4
GND
5
D1
1N5818
L1
10µH
CL
+
100µF
10V
R2
150kΩ
1%
VOUT
3V
100mA
R1
110kΩ
1%
C1, C2 = AVX TPS D107 M010R0100
L1 = SUMIDA CR43-100
Figure 3. Step-Down Mode Operation
Rev. A
Information furnished by Analog Devices is believed to be accurate and reliable.
However, no responsibility is assumed by Analog Devices for its use, nor for any
infringements of patents or other rights of third parties that may result from its use.
Specifications subject to change without notice. No license is granted by implication
or otherwise under any patent or patent rights of Analog Devices. Trademarks and
registered trademarks are the property of their respective owners.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A.
Tel: 781.329.4700
www.analog.com
Fax: 781.326.8703
© 2004 Analog Devices, Inc. All rights reserved.
00122-003
GENERAL DESCRIPTION
A0
GAIN BLOCK/
ERROR AMP
LE
Notebook, palmtop computers
Cellular telephones
Hard disk drives
Portable instruments
Pagers
A1
VIN
00122-001
APPLICATIONS
SET
TE
Operates at supply voltages from 2 V to 30 V
Works in step-up or step-down mode
Very few external components required
High frequency operation up to 400 kHz
Low battery detector on-chip
User-adjustable current limit
Fixed and adjustable output voltage
8-lead PDIP, 8-lead SOIC, and 14-lead TSSOP packages
Small inductors and capacitors
ADP3000
TABLE OF CONTENTS
Specifications..................................................................................... 3
Programming the Gain Block................................................... 11
Absolute Maximum Ratings............................................................ 4
Power Transistor Protection Diode in Step-Down
Configuration ............................................................................. 11
Pin Configurations and Function Descriptions ........................... 5
Typical Performance Characteristics ............................................. 6
Theory of Operation ........................................................................ 9
Applications Information .............................................................. 10
Thermal Considerations............................................................ 11
Typical Application Circuits ......................................................... 13
Outline Dimensions ....................................................................... 15
Ordering Guide .......................................................................... 16
Component Selection................................................................. 10
Programming the Switching Current Limit............................ 10
9/04—Data Sheet Changed from Rev. 0 to Rev. A
LE
REVISION HISTORY
TE
ESD Caution.................................................................................. 4
B
SO
Added RU-14 Package ................................................. Universal
Changes to Table 4.....................................................................10
Changes to Table 5.....................................................................10
Updated Outline Dimensions ..................................................15
Changes to Ordering Guide .....................................................16
O
1/97—Revision 0: Initial Version
Rev. A | Page 2 of 16
ADP3000
SPECIFICATIONS
0°C ≤ TA ≤ +70°C, VIN = 3 V, unless otherwise noted.1
Table 1.
COMPARATOR HYSTERESIS
OUTPUT HYSTERESIS
OSCILLATOR FREQUENCY
DUTY CYCLE
SWITCH-ON TIME
SWITCH SATURATION VOLTAGE
Step-Up Mode
VFB < VREF
ILIM tied to VIN, VFB= 0
TA = +25°C
VIN = 3.0 V, ISW = 650 mA
VIN = 5.0 V, ISW = 1 A
VIN = 12 V, ISW = 650 mA
ADP3000 VFB = 0 V
VSET = VREF
ISINK = 300 µA, VSET = 1.00 V
5 V ≤ VIN ≤ 30 V
2 V ≤ VIN ≤ 5 V
B
SO
Step-Down Mode
FEEDBACK PIN BIAS CURRENT
SET PIN BIAS CURRENT
GAIN BLOCK OUTPUT LOW
REFERENCE LINE REGULATION
GAIN BLOCK GAIN
GAIN BLOCK CURRENT SINK
CURRENT LIMIT
CURRENT LIMIT TEMPERATURE COEFFICIENT
RL = 100 kΩ4
VSET ≤ 1 V
220 Ω from ILIM to VIN
SWITCH-OFF LEAKAGE CURRENT
Measured at SW1 pin
VSW1= 12 V, TA = +25°C
TA = +25°C
ISW1 ≤ 10 µA, switch off
O
MAXIMUM EXCURSION BELOW GND
Symbol
VIN
Min
2.0
IQ
VOUT
1.20
3.135
4.75
11.40
ADP3000
Typ
Max
12.6
30.0
500
1.245
1.30
3.3
3.465
5.00
5.25
12.00
12.60
8
12.5
32
50
32
50
75
120
400
450
80
2
2.55
TE
SHUT-DOWN QUIESCENT CURRENT
COMPARATOR TRIP POINT VOLTAGE
OUTPUT SENSE VOLTAGE
Conditions
Step-up mode
Step-down mode
VFB > 1.43 V; VSENSE > 1.1 × VOUT
ADP30002
ADP3000-3.33
ADP3000-53
ADP3000-123
ADP3000
ADP3000-3.3
ADP3000-5
ADP3000-12
fOSC
D
tON
VSAT
LE
Parameter
INPUT VOLTAGE
1
350
65
1.5
0.5
IFB
ISET
VOL
AV
ISINK
ILIM
1000
0.75
0.8
1.1
160
200
0.15
0.02
0.2
V
1.1
1.5
330
400
0.4
0.15
0.6
6000
300
400
−0.3
Unit
V
V
µA
V
V
V
V
mV
mV
mV
mV
kHz
%
µs
V
V
nA
nA
V
%/V
%/V
V/V
µA
mA
%/°C
1
10
µA
−400
−350
mV
All limits at temperature extremes are guaranteed via correlation using standard statistical methods.
This specification guarantees that both the high and low trip points of the comparator fall within the 1.20 V to 1.30 V range.
The output voltage waveform will exhibit a saw-tooth shape due to the comparator hysteresis. The output voltage on the fixed output versions will always be within
the specified range.
4
100 kΩ resistor connected between a 5 V source and the AO pin.
2
3
Rev. A | Page 3 of 16
ADP3000
ABSOLUTE MAXIMUM RATINGS
Table 2.
Rating
15 V
36 V
50 V
−0.5 V to VIN
5.5 V
1.5 A
500 mW
0°C to +70°C
−65°C to +150°C
300°C
Stresses above those listed under Absolute Maximum Ratings
may cause permanent damage to the device. This is a stress
rating only; functional operation of the device at these or any
other conditions above those indicated in the operational
section of this specification is not implied. Exposure to
Absolute Maximum Rating conditions for extended periods
may affect device reliability.
TE
Parameter
Input Supply Voltage, Step-Up Mode
Input Supply Voltage, Step-Down Mode
SW1 Pin Voltage
SW2 Pin Voltage
Feedback Pin Voltage (ADP3000)
Switch Current
Maximum Power Dissipation
Operating Temperature Range
Storage Temperature Range
Lead Temperature (Soldering, 10 s)
Thermal Impedance
R-8
RU-14
N-8
170°C/W
150°C/W
120°C/W
ESD CAUTION
O
B
SO
LE
ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily
accumulate on the human body and test equipment and can discharge without detection. Although
this product features proprietary ESD protection circuitry, permanent damage may occur on devices
subjected to high energy electrostatic discharges. Therefore, proper ESD precautions are
recommended to avoid performance degradation or loss of functionality.
Rev. A | Page 4 of 16
ADP3000
PIN CONFIGURATIONS AND FUNCTION DESCRIPTIONS
ILIM 1
SW1 3
SW2 4
ADP3000
FB (SENSE)*
7
SET
VIN 2
TOP VIEW
6 AO
(Not to Scale)
5 GND
*FIXED VERSIONS
Figure 6. 8-Lead SOIC (R-8)
NC
2
13
FB
ILIM
3
12
SET
VIN
4
11
AO
SW1
5
10
NC
NC
6
9
NC
SW2
7
8
GND
Figure 5. 14-lead TSSOP (RU-14)
Table 3. Pin Function Descriptions
FB/SENSE
O
SET
A2
A0
1.245V
REFERENCE
A1
1.245V
REFERENCE
DRIVER
SW2
ADP3000
GND
A0
FB
R1
GND
SW1
OSCILLATOR
COMPARATOR
Figure 7. Functional Block Diagram for Adjustable Version
ILIM
GAIN BLOCK/
ERROR AMP
SW1
OSCILLATOR
COMPARATOR
A1
VIN
ILIM
GAIN BLOCK/
ERROR AMP
00122-006
VIN
SET
DRIVER
ADP3000
R2
SENSE
Figure 8. Functional Block Diagram for Fixed Version
Rev. A | Page 5 of 16
SW2
00122-007
GND
AO
SET
Function
For normal conditions, connect to VIN. When lower current is required, connect a resistor between ILIM and VIN.
To limit the switch current to 400 mA, connect a 220 Ω resistor.
Input Voltage.
Collector of Power Transistor. For step-down configuration, connect to VIN. For step-up configuration, connect
to an inductor/diode.
Emitter of Power Transistor. For step-down configuration, connect to inductor/diode. For step-up
configuration, connect to ground. Do not allow pin to go more than a diode drop below ground.
Ground.
Auxiliary Gain Block (GB) Output. Open collector can sink 300 µA. This pin can be left open if not used.
Auxiliary Gain Amplifier Input. The amplifier’s positive input is connected to the SET pin, and its negative
input is connected to the 1.245 V reference. This pin can be left open if not used.
On the ADP3000 (adjustable) version, this pin is connected to the comparator input. On the ADP3000-3.3,
the ADP3000-5, and the ADP3000-12, the pin goes directly to the internal resistor divider that sets the
output voltage.
B
SO
SW2
TE
14
NC
NC = NO CONNECT
VIN
SW1
SET
LE
1
Mnemonic
ILIM
FB (SENSE)*
7
*FIXED VERSIONS
00122-035
NC
TOP VIEW
(Not to Scale)
8
6 AO
TOP VIEW
SW2 4 (Not to Scale) 5 GND
Figure 4. 8-Lead Plastic DIP (N-8)
ADP3000
ADP3000
SW1 3
00122-004
VIN 2
8
00122-005
ILIM 1
ADP3000
TYPICAL PERFORMANCE CHARACTERISTICS
2.5
406
OSCILLATOR FREQUENCY
@ TA = 25°C
405
OSCILLATOR FREQUENCY (kHz)
1.5
VIN = 5V @ TA = 25°C
1.0
VIN = 3V @ TA = 25°C
1.2
1.4
1.5
398
2
Figure 9. Switch-On Voltage vs. Switch Current in Step-Up Mode
0.8
10
12
15
18
INPUT VOLTAGE (V)
0.2
0.2
0.3
0.4
0.5
0.6
SWITCH CURRENT (A)
0.8
0.9
1200
30
TA = 0°C
600
400
TA = 85°C
0.4
0.3
0.2
10
100
1k
RLIM (Ω)
Figure 13. Maximum Switch Current vs. RLIM in Step-Down Mode (5 V)
1.8
VIN = 12V
TA = 25°C
1.6
TA = 0°C
1.4
SWITCH CURRENT (A)
O
800
TA = 25°C
0.5
1
QUIESCENT CURRENT @ TA = 25°C
1000
27
0
Figure 10. Saturation Voltage vs. Switch Current in Step-Down Mode
1400
24
0.1
00122-009
0.4
21
VIN = 5V
LE
0.6
SWITCH CURRENT (A)
VIN = 12V @ TA = 25°C
0.8
B
SO
VCE(SAT) (V)
8
0.6
1.0
1.2
TA = 85°C
1.0
0.8
0.6
0.4
200
0
1.5
0.2
3.0
6
9
12
15
18
21
INPUT VOLTAGE (V)
24
Figure 11. Quiescent Current vs. Input Voltage
27
30
0
00122-010
QUIESCENT CURRENT (µA)
6
0.7
VIN = 5V @ TA = 25°C
1.2
4
Figure 12. Oscillator Frequency vs. Input Voltage
1.4
0
0.1
400
00122-011
0.6
0.8
1.0
SWITCH CURRENT (A)
401
TE
0.4
00122-008
0.2
402
399
VIN = 2V @ TA = 25°C
0
0.1
403
00122-A-012
0.5
404
1
10
100
RLIM (Ω)
1k
00122-013
ON VOLTAGE (V)
2.0
Figure 14. Maximum Switch Current vs. RLIM in Step-Down Mode (12 V)
Rev. A | Page 6 of 16
ADP3000
1.8
100
VIN = 3V
90
1.6
80
TA = 0°C
70
1.2
DUTY CYCLE (%)
TA = 25°C
1.0
TA = 85°C
0.8
0.6
0.4
60
50
40
30
20
0.2
10
100
1k
RLIM (Ω)
Figure 15. Maximum Switch Current vs. RLIM in Step-Up Mode (3 V)
0
–40
0
25
TEMPERATURE (°C(T A))
70
85
TE
1
00122-014
10
0
00122-017
SWITCH CURRENT (A)
1.4
Figure 18. Duty Cycle vs. Temperature
440
0.56
430
SATURATION VOLTAGE (V)
LE
400
390
380
370
360
340
330
–40
0
25
TEMPERATURE (°C(T A))
70
85
2.20
2.10
2.05
2.00
1.95
0
25
TEMPERATURE (°C(T A))
70
85
1.25
1.20
1.15
VIN = 12V @ ISW = 0.65A
1.10
1.05
1.00
1.90
0.95
1.80
–40
0
25
TEMPERATURE (°C(T A))
70
85
Figure 17. Switch-On Time vs. Temperature
0.90
–40
0
25
TEMPERATURE (°C(T A))
70
85
Figure 20. Switch-On Voltage vs. Temperature in Step-Down Mode
Rev. A | Page 7 of 16
00122-019
1.85
00122-016
ON TIME (µs)
O
2.15
0.46
Figure 19. Saturation Voltage vs. Temperature in Step-Up Mode
ON VOLTAGE (V)
2.25
VIN = 3V @ ISW = 0.65A
0.48
0.42
–40
Figure 16. Oscillator Frequency vs. Temperature
2.30
0.50
0.44
00122-015
350
0.52
00122-018
410
B
SO
OSCILLATOR FREQUENCY (kHz)
0.54
420
ADP3000
250
350
300
200
BIAS CURRENT (nA)
BIAS CURRENT (nA)
250
150
100
200
150
100
50
25
TEMPERATURE (°C(T A))
70
85
Figure 21. Feedback Bias Current vs. Temperature
VIN = 20V
25
TEMPERATURE (°C(T A))
LE
500
400
300
0
25
TEMPERATURE (°C(T A))
70
85
00122-021
B
SO
200
Figure 22. Quiescent Current vs. Temperature
O
QUIESCENT CURRENT (µA)
600
0
–40
0
70
Figure 23. Set Pin Bias Current vs. Temperature
700
100
0
–40
Rev. A | Page 8 of 16
85
00122-022
0
TE
0
–40
00122-020
50
ADP3000
The ADP3000 is a versatile, high frequency, switch mode power
supply (SMPS) controller. The regulated output voltage can be
greater than the input voltage (in boost or step-up mode) or less
than the input voltage (in buck or step-down mode). This
device uses a gated oscillator technique to provide high
performance with low quiescent current.
The ADP3000 provides external connections for both the
collector and the emitter of its internal power switch,
permitting both step-up and step-down modes of operation.
For the step-up mode, the emitter (Pin SW2) is connected to
GND, and the collector (Pin SW1) drives the inductor. For stepdown mode, the emitter drives the inductor, while the collector
is connected to VIN.
The output voltage of the ADP3000 is set with two external
resistors. Three fixed voltage models are also available:
ADP3000-3.3 (3.3 V), ADP3000-5 (5 V), and ADP3000-12
(12 V). The fixed voltage models include laser-trimmed,
voltage-setting resistors on the chip. On the fixed voltage
models of the ADP3000, simply connect the feedback pin
(Pin 8) directly to the output voltage.
LE
Figure 7 is a functional block diagram of the ADP3000. The
internal 1.245 V reference is connected to one input of the
comparator, and the other input is externally connected (via the
FB pin) to a resistor divider, which is connected to the regulated
output. When the voltage at the FB pin falls below 1.245 V, the
400 kHz oscillator turns on. The ADP3000 internal oscillator
typically provides a 1.7 µs on time and a 0.8 µs off time. A driver
amplifier provides base drive to the internal power switch, and
the switching action raises the output voltage. When the voltage
at the FB pin exceeds 1.245 V, the oscillator shuts off. While the
oscillator is off, the ADP3000 quiescent current is only 500 µA.
The comparator’s hysteresis ensures loop stability without
requiring external components for frequency compensation.
An uncommitted gain block on the ADP3000 can be connected
as a low battery detector. The inverting input of the gain block
is internally connected to the 1.245 V reference. The
noninverting input is available at the SET pin. A resistor divider,
connected between VIN and GND with the junction connected
to the SET pin, causes the AO output to go low when the low
battery set point is exceeded. The AO output is an open
collector NPN transistor that can sink in excess of 300 µA.
TE
THEORY OF OPERATION
O
B
SO
The maximum current in the internal power switch is set by
connecting a resistor between VIN and the ILIM pin. When the
maximum current is exceeded, the switch is turned off. The
current limit circuitry has a time delay of about 0.3 µs. If an
external resistor is not used, connect ILIM to VIN. This yields the
maximum feasible current limit. Further information on ILIM is
included in the Applications Information section.
Rev. A | Page 9 of 16
ADP3000
Table 5. Recommended Capacitors
APPLICATIONS INFORMATION
Vendor
AVX
Sanyo
Sprague
Panasonic
Inductor Selection
For most applications, the inductor used with the ADP3000
falls in the range of 4.7 µH to 33 µH. Table 4 shows
recommended inductors and their vendors.
When selecting an inductor for the ADP3000, it is very important
to make sure the inductor is able to handle a current higher than
the ADP3000’s current limit, without becoming saturated.
In addition, inductor dc resistance causes power loss. To
minimize power loss, it is best to use an inductor with a dc
resistance lower than 0.2 Ω.
Table 4. Recommended Inductors
Series
OCTAPAC
UNIPAC
CR43, CR54
CDRH6D28,
CDRH73,
CDRH64
Core Type
Toroid
Open
Open
Semi-Closed
Geometry
Phone Number
(843) 448-9411
(619) 661-6835
(603) 224-1961
(800) 344-2112
Diode Selection
The ADP3000’s high switching speed demands the use of
Schottky diodes. Suitable choices include the 1N5817, the
1N5818, the 1N5819, the MBRS120LT3, and the MBR0520LT1.
Fast recovery diodes are not recommended because their high
forward drop lowers efficiency. General-purpose and smallsignal diodes should be avoided as well.
PROGRAMMING THE SWITCHING CURRENT LIMIT
The ADP3000’s RLIM pin permits the cycle-by-cycle switch
current limit to be programmed with a single external resistor.
This feature offers major advantages that ultimately decrease
the component’s cost and the PCB’s real estate. First, the RLIM
pin allows the ADP3000 to use low value, low saturation current
and physically small inductors. Additionally, it allows for a
physically small surface-mount tantalum capacitor with a
typical ESR of 0.1 Ω. With this capacitor, it achieves an output
ripple as low as 40 mV to 80 mV, as well as a low input ripple.
Phone Number
(561) 752-5000
(561) 752-5000
(847) 545-6700
(847) 545-6700
The current limit is usually set to approximately 3 to 5 times the
full load current for boost applications, and about 1.5 to 3 times
the full load current in buck applications.
B
SO
Capacitor Selection
For most applications, the capacitor used with the ADP3000
falls in the range of 33 µF to 220 µF. Table 5 shows
recommended capacitors and their vendors.
O
For input and output capacitors, use low ESR type capacitors for
best efficiency and lowest ripple. Recommended capacitors
include the AVX TPS series, the Sprague 595D series, the
Panasonic HFQ series, and the Sanyo OS-CON series.
The internal structure of the ILIM circuit is shown in Figure 24.
Q1, the ADP3000’s internal power switch, is paralleled by sense
transistor Q2. The relative sizes of Q1 and Q2 are scaled so that
IQ2 is 0.5% of IQ1. Current flows to Q2 through both the RLIM
resistor and an internal 80 Ω resistor. The voltage on these two
resistors biases the base-emitter junction of the oscillator-disable
transistor, Q3. When the voltage across R1 and RLIM exceeds 0.6 V,
Q3 turns on and terminates the output pulse. If only the 80 Ω
internal resistor is used (when the ILIM pin is connected directly to
VIN), the maximum switch current is 1.5 A. Figure 13, Figure 14,
and Figure 15 give values for lower current limit levels.
When selecting a capacitor, it is important to make sure the
maximum capacitor ripple current rms rating is higher than the
ADP3000’s rms switching current.
It is best to protect the input capacitor from high turn-on
current charging surges by derating the capacitor voltage by 2:1.
For very low input or output voltage ripple requirements, use
capacitors with very low ESR, such as the Sanyo OS-CON
series. Alternatively, two or more tantalum capacitors can be
used in parallel.
RLIM
(EXTERNAL)
VIN
VIN
ILIM
R1
Q3
ADP3000
400kHz
OSCILLATOR
80Ω
(INTERNAL)
IQ1
200
DRIVER
SW1
Q1
POWER
SWITCH
Q2
SW2
Figure 24. ADP3000 Current Limit Operation
Rev. A | Page 10 of 16
00122-023
Vendor
Coiltronics
Coiltronics
Sumida
Sumida
Type
Surface Mount
Through Hole
Surface Mount
Through Hole
LE
As a general rule, powdered iron cores saturate softly, whereas
Ferrite cores saturate abruptly. Rod and open drum core
geometry inductors saturate gradually. Inductors that saturate
gradually are easier to use. Even though rod and drum core
inductors are attractive in both price and physical size, they
must be used with care because they have high magnetic
radiation. When minimizing EMI is critical, toroid and closed
drum core geometry inductors should be used.
Series
TPS
OS-CON
595D
HFQ
TE
COMPONENT SELECTION
ADP3000
The ADP3000’s gain block can be used as a low battery detector,
an error amplifier, or a linear post regulator. It consists of an op
amp with PNP inputs and an open-collector NPN output. The
inverting input is internally connected to the 1.245 V reference,
and the noninverting input is available at the SET pin. The NPN
output transistor sinks in excess of 300 µA.
R1 =
where:
VL is the logic power supply voltage.
RL is the pull-up resistor.
RHYS creates the hysteresis.
POWER TRANSISTOR PROTECTION DIODE IN
STEP-DOWN CONFIGURATION
When operating the ADP3000 in step-down mode with the
switch off, the output voltage is impressed across the internal
power switch’s emitter-base junction. When the output voltage
is set to higher than 6 V, a Schottky diode must be placed in a
series with SW2 to protect the switch. Figure 26 shows the
proper way to place D2, the protection diode. The selection of
this diode is identical to the step-down commuting diode (refer
to the Diode Selection section).
VIN
V LOBATT − 1.245 V
1.245 V
C2
+
1
where VLOBATT is the desired low battery trip point.
B
SO
VIN
1.245V
REF
SET
RL
47kΩ
AO
GND
TO
PROCESSOR
Figure 25. Setting the Low Battery Detector Trip Point
The circuit of Figure 25 may produce multiple pulses when
approaching the trip point due to noise coupled into the SET
input. To prevent multiple interrupts to the digital logic, add
hysteresis to the circuit. Resistor RHYS, with a value of 1 MΩ to
10 MΩ, provides the hysteresis. The addition of RHYS alters the
trip point slightly, changing the new value for R1 to
L1
R2
SW2 4
5
D2
D1
C1
+
R1
Figure 26. Step-Down Mode VOUT > 6.0 V
THERMAL CONSIDERATIONS
Power dissipation internal to the ADP3000 can be
approximated with the following equations.
Step-Up
V IN I SW ⎤ ⎡ V IN ⎤ ⎡ 4 I O ⎤
⎡
PD = ⎢ I SW 2 R +
⎥⎢
⎥ + I Q [V IN ]
⎥ D ⎢1 −
β
VO ⎦ ⎣ I SW ⎦
⎣
⎦ ⎣
[ ]
RHYS
1.6MΩ
00122-024
O
R2
33kΩ
V – 1.245V
R1 = LB
37.7µA
VLB = BATTERY TRIP POINT
VOUT > 6V
3
FB 8
GND
5V
ADP3000
2
VIN SW1
ADP3000
Because the gain block output is an open-collector NPN, a
pull-up resistor should be connected to the positive logic
power supply.
R1
D1, D2 = 1N5818 SCHOTTKY DIODES
R3
ILIM
R2
VBATT
⎛ 1.245 V ⎞ ⎛⎜ VL − 1.245 V ⎞⎟
⎜⎜
⎟⎟ −
⎝ R2 ⎠ ⎜⎝ R L + R HYS ⎟⎠
LE
Figure 25 shows the gain block configured as a low battery
monitor. Set Resistors R1 and R2 to high values to reduce
quiescent current, but not so high that bias current in the SET
input causes large errors. A value of 33 kΩ for R2 is a good
compromise. The value for R1 is then calculated as follows:
VLOBATT − 1.245 V
00122-025
PROGRAMMING THE GAIN BLOCK
R1 =
TE
The delay through the current limiting circuit is approximately
0.3 µs. If the switch-on time is reduced to less than 1.7 µs,
accuracy of the current trip point is reduced as well. An attempt
to program a switch-on time of 0.3 µs or less produces spurious
responses in the switch-on time. However, the ADP3000 still
provides a properly regulated output voltage.
where:
ISW is ILIMIT when the current limit is programmed externally;
otherwise, ISW is the maximum inductor current.
V0 is the output voltage.
I0 is the output current.
VIN is the input voltage.
R is 1 Ω (typical RCE(SAT)).
D is 0.75 (typical duty ratio for a single switching cycle).
IQ is 500 µA (typical shutdown quiescent current).
β = 30 (typical forced beta).
Rev. A | Page 11 of 16
ADP3000
⎡
PD = ⎢ I SW VCESAT
⎢⎣
⎤⎡ 2 I O
⎛
VO
1 ⎞⎡
⎜1 + ⎟ ⎢
⎥⎢
⎜
⎟
β ⎠ ⎢⎣ V IN − VCE (SAT ) ⎦⎥ ⎣ I SW
⎝
⎤
⎤
⎥ + I Q [V IN ]⎥
⎥⎦
⎦
[ ]
where:
ISW is ILIMIT when the current limit is programmed externally;
otherwise, ISW is the maximum inductor current.
VCE(SAT) is 1.2 V (typical value). Check this value by applying ISW
to Figure 10.
VO is the output voltage.
IO is the output current.
VIN is the input voltage.
D is 0.75 (typical duty ratio for a single switching cycle).
IQ is 500 µA (typical shutdown quiescent current).
β is 30 (typical forced beta).
∆T = PD × θ JA
Using the step-up power dissipation equation:
(2)(0.8) ⎤
2 ⎡ (4) 0.18 ⎤
⎡
[0.75] ⎡⎢1 − ⎤⎥ ⎢
PD = ⎢0.8 2 × 1 +
⎥ + 500 E − 6 [2]
⎥
30 ⎦
⎣ 3.3 ⎦ ⎣ 0.8 ⎦
⎣
[
∆T is 185 mW (170°C/W) = 31.5°C, using the R-8 package.
∆T is 185 mW (120°C/W) = 22.2°C, using the N-8 package.
At a 70°C ambient, the die temperature would be 101.45°C for
the R-8 package and 92.2°C for the N-8 package. These junction
temperatures are well below the maximum recommended
junction temperature of 125°C.
Finally, the die temperature can be decreased up to 20% by
using a large metal ground plate as ground pickup for the
ADP3000.
O
B
SO
where:
∆T is temperature rise.
PD is device power dissipation.
θJA is thermal resistance (junction-to-ambient).
VIN is 2 V.
VO is 3.3 V.
IO is 180 mA.
ISW is 0.8 A (externally programmed).
LE
The temperature rise can be calculated using the following
equation:
For example, consider a boost converter with the following
specifications:
TE
Step-Down
Rev. A | Page 12 of 16
]
ADP3000
TYPICAL APPLICATION CIRCUITS
C1 +
100µF
10V
IN5817
VOUT
3.3V
180mA
120Ω
1
2
ILIM
VIN
VIN
4.5V TO 5.5V
L1
15µH
C1 +
100µF
10V
1
2
ILIM
VIN
SW1 3
SW1 3
ADP3000-12V
+
SENSE 8
C2
100µF
10V
SW2
GND
SW2
5
4
5
4
Figure 27. 2 V to 3.3 V/180 mA Step-Up Converter
Figure 30. 4.5 V to 12 V/50 mA Step-Up Converter
VIN
5V TO 6V
VOUT
5V
100mA
120Ω
L1 = SUMIDA CR54-150
C1 = AVX TPS D107 M010R0100
C2 = AVX TPS D107 M016R0100
TYPICAL EFFICIENCY = 75%
C1
100µF
10V
2
VIN
+
SENSE 8
SW2
5
4
C2
100µF
10V
00122-027
B
SO
GND
L1 = SUMIDA CR43-6R8
C1, C2 = AVX TPS D107 M010R0100
TYPICAL EFFICIENCY = 80%
IN5817
VOUT
5V
150mA
120Ω
1
2
ILIM
VIN
FB 8
SW2 4
5
D1
1N5817
VIN
10V TO 13V
C1+
33µF
20V
SW2
5
4
C2
100µF
10V
L1 = SUMIDA CR43-6R8
C1, C2 = AVX TPS D107 M010R0100
TYPICAL EFFICIENCY = 80%
R1
110kΩ
1
2
ILIM
3
VIN SW1
SENSE 8
ADP3000-5V
SW2 4
GND
VOUT
5V
250mA
L1
10µH
5
L1: SUMIDA CR43-100
C1 = AVX TPS D336 M020R0200
C2 = AVX TPS D107 M010R0100
TYPICAL EFFICIENCY = 77%
D1
1N5817
+
C2
100µF
10V
00122-028
O
GND
C2
+
100µF
10V
250Ω
ADP3000-5V
SENSE 8
VOUT
3V
100mA
R2
150kΩ
Figure 31. 5 V to 3 V/100 mA Step-Down Converter
SW1 3
+
L1
10µH
GND
L1 = SUMIDA CR43-100
C1, C2 = AVX TPS D107 M010R0100
TYPICAL EFFICIENCY = 75%
Figure 28. 2 V to 5 V/100 mA Step-Up Converter
L1
6.8µH
3
ADP3000-ADJ
SW1 3
100µF
10V
2
VIN SW1
00122-030
1
ILIM
C1 +
1
ILIM
ADP3000-5V
VIN
2.7V TO 4.5V
120Ω
LE
C1 +
100µF
10V
C2
100µF
16V
TE
00122-026
GND
IN5817
+
SENSE 8
L1 = SUMIDA CR43-6R8
C1, C2 = AVX TPS D107 M010R0100
TYPICAL EFFICIENCY = 75%
VIN
2V TO 3.2V
VOUT
12V
50mA
124Ω
ADP3000-3.3V
L1
6.8µH
IN5817
00122-029
L1
6.8µH
Figure 32. 10 V to 5 V/250 mA Step-Down Converter
Figure 29. 2.7 V to 5 V/150 mA Step-Up Converter
Rev. A | Page 13 of 16
00122-031
VIN
2V TO 3.2V
ADP3000
VIN
5V
C1 +
47µF
16V
240Ω
1
2
ILIM
3
VIN SW1
SENSE 8
ADP3000-5V
SW2 4
GND
L1
15µH
5
+
D1
1N5817
VOUT
–5V
100mA
TE
00122-032
L1 = SUMIDA CR54-150
C1 = AVX TPS D476 M016R0150
C2 = AVX TPS D107 M010R0100
TYPICAL EFFICIENCY = 60%
C2
100µF
10V
2.5V TO 4.2V
100kΩ
LE
Figure 33. 5 V to −5 V/100 mA Inverter
(SUMIDA – CDRH62)
120Ω
330kΩ
6.8µH
2N2907
100µF +
10V
AVX-TPS
ILIM
SET
1MΩ
1N5817
VIN
100kΩ
SW1
33nF
ADP3000
A0
FB
10kΩ
IN1
348kΩ
1%
90kΩ
+
IN2
100µF
10V
AVX-TPS
ADP3302AR1
SD
SW2
GND
200kΩ
1%
90kΩ
Figure 34. 1 Cell Li-Ion to 3 V/200 mA Converter with Shut-Down at VIN ≤ 2.5 V
@ VIN ≤ 2.5V
SHDN IQ = 500µA
IO = 50mA + 50mA
75
IO = 100mA + 100mA
65
2.6
3.0
3.4
3.8
4.2
Figure 35. Typical Efficiency of the Circuit of Figure 34
Rev. A | Page 14 of 16
VIN
(V)
00122-034
O
% EFFICIENCY
80
70
VO2
1µF
6V (MLC)
1µF
6V (MLC)
3V
100mA
3V
100mA
00122-033
B
SO
GND
VO1
ADP3000
OUTLINE DIMENSIONS
0.375 (9.53)
0.365 (9.27)
0.355 (9.02)
8
5
1
4
0.295 (7.49)
0.285 (7.24)
0.275 (6.98)
0.325 (8.26)
0.310 (7.87)
0.300 (7.62)
0.100 (2.54)
BSC
0.015
(0.38)
MIN
0.150 (3.81)
0.130 (3.30)
0.110 (2.79)
0.022 (0.56)
0.018 (0.46)
0.014 (0.36)
SEATING
PLANE
0.060 (1.52)
0.050 (1.27)
0.045 (1.14)
0.015 (0.38)
0.010 (0.25)
0.008 (0.20)
TE
0.180
(4.57)
MAX
0.150 (3.81)
0.135 (3.43)
0.120 (3.05)
COMPLIANT TO JEDEC STANDARDS MO-095AA
CONTROLLING DIMENSIONS ARE IN INCHES; MILLIMETER DIMENSIONS
(IN PARENTHESES) ARE ROUNDED-OFF INCH EQUIVALENTS FOR
REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN
LE
Figure 36. 8-Lead Plastic Dual In-Line Package [PDIP]
(N-8)
Dimensions shown in inches and (millimeters)
5.00 (0.1968)
4.80 (0.1890)
5
4
6.20 (0.2440)
5.80 (0.2284)
B
SO
8
4.00 (0.1574)
3.80 (0.1497) 1
1.27 (0.0500)
BSC
0.25 (0.0098)
0.10 (0.0040)
1.75 (0.0688)
1.35 (0.0532)
0.51 (0.0201)
COPLANARITY
SEATING 0.31 (0.0122)
0.10
PLANE
0.50 (0.0196)
× 45°
0.25 (0.0099)
8°
0.25 (0.0098) 0° 1.27 (0.0500)
0.40 (0.0157)
0.17 (0.0067)
O
COMPLIANT TO JEDEC STANDARDS MS-012AA
CONTROLLING DIMENSIONS ARE IN MILLIMETERS; INCH DIMENSIONS
(IN PARENTHESES) ARE ROUNDED-OFF MILLIMETER EQUIVALENTS FOR
REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN
Figure 37. 8-Lead Standard Small Outline Package [SOIC]
Narrow Body
(R-8)
Dimensions shown in millimeters and (inches)
Rev. A | Page 15 of 16
ADP3000
5.10
5.00
4.90
14
8
4.50
4.40
4.30
6.40
BSC
1
7
PIN 1
0.65
BSC
1.05
1.00
0.80
1.20
MAX
0.30
0.19
SEATING
COPLANARITY
PLANE
0.10
0.75
0.60
0.45
8°
0°
TE
0.15
0.05
0.20
0.09
COMPLIANT TO JEDEC STANDARDS MO-153AB-1
ORDERING GUIDE
Output Voltage
Adjustable
3.3 V
5V
12 V
Adjustable
Adjustable
3.3 V
3.3 V
5V
5V
12 V
12 V
Adjustable
Adjustable
Temperature Range
–40°C to +85°C
–40°C to +85°C
–40°C to +85°C
–40°C to +85°C
–40°C to +85°C
–40°C to +85°C
–40°C to +85°C
–40°C to +85°C
–40°C to +85°C
–40°C to +85°C
–40°C to +85°C
–40°C to +85°C
–40°C to +85°C
–40°C to +85°C
O
B
SO
Model
ADP3000AN
ADP3000AN-3.3
ADP3000AN-5
ADP3000AN-12
ADP3000AR
ADP3000AR-REEL
ADP3000AR-3.3
ADP3000AR-3.3-REEL
ADP3000AR-5
ADP3000AR-5-REEL
ADP3000AR-12
ADP3000AR-12-REEL
ADP3000ARU
ADP3000ARU-REEL
LE
Figure 38. 14-Lead Thin Shrink Small Outline Package [TSSOP]
(RU-14)
Dimensions shown in millimeters
© 2004 Analog Devices, Inc. All rights reserved. Trademarks and
registered trademarks are the property of their respective owners.
C00122–0–9/04(A)
Rev. A | Page 16 of 16
Package Description
8-lead plastic DIP
8-lead plastic DIP
8-lead plastic DIP
8-lead plastic DIP
8-lead SOIC
8-lead SOIC
8-lead SOIC
8-lead SOIC
8-lead SOIC
8-lead SOIC
8-lead SOIC
8-lead SOIC
14-lead TSSOP
14-lead TSSOP
Package Option
N-8
N-8
N-8
N-8
R-8
R-8
R-8
R-8
R-8
R-8
R-8
R-8
RU-14
RU-14
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