DRV8210P
DRV8210P
SLVSGC3
– MAY 2020
SLVSGC3 – MAY 2020
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DRV8210P 11-V H-Bridge Motor Driver with PWM Interface and Low-Power Sleep
Mode
1 Features
3 Description
•
The DRV8210P is an integrated motor driver with
four N-channel power FETs, charge pump regulator,
and protection circuitry. The tripler charge pump
architecture allows the device to operate down to 1.65
V to accommodate 1.8-V supply rails and low-battery
conditions. The charge pump integrates all capacitors
to reduce the overall solution size of the motor driver
on a PCB and allows for 100% duty cycle operation.
•
•
•
•
•
•
•
N-channel H-bridge motor driver
– MOSFET on-resistance: HS + LS 1 Ω
– Drives one bidirectional brushed DC motor
– One single- or dual-coil latching relay
1.65-V to 11-V operating supply voltage range
High output current capability: 1.76-A peak
Standard PWM Interface (IN1/IN2)
Supports 1.8-V, 3.3-V, and 5-V logic inputs
Ultra low-power sleep mode
– VUVLO,VCC rising
IOUT > IOCP
Disabled
tRETRY
TJ > TTSD
Disabled
TJ < TTSD – THYS
Overcurrent (OCP)
Thermal Shutdown (TSD)
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9 Application and Implementation
Note
Information in the following applications sections is not part of the TI component specification, and
TI does not warrant its accuracy or completeness. TI’s customers are responsible for determining
suitability of components for their purposes. Customers should validate and test their design
implementation to confirm system functionality.
9.1 Application Information
The application examples in this section highlight how to use the DRV8210P.
9.2 Typical Application
9.2.1 Full-Bridge Driving
A typical application for the DRV8210P is driving a brushed DC motor or single-coil bistable latching relay
bidriectionally (in forward and reverse) using the outputs as a full-bridge, or H-bridge, configuration. Figure 9-1
shows an example schematic for driving a motor, and Figure 9-2 shows an example schematic for driving a
latching relay.
VM
VM
VCC
0.1 …F
CBulk
VCC
CBulk
VCC
0.1 …F
0.1 …F
1
VM
0.1 …F
1
VM
DRV821xPDSG
8
3
Thermal
Pad
nSLEEP
OUT2
O
Singlecoil
relay
6
IN1
4
8
VCC
7
OUT1
3
7
OUT1
DRV821xPDSG
2
VCC
2
BDC
Controller
PWM
VCC
Controller
Thermal
Pad
O
nSLEEP
6
OUT2
IN1
GND
IN2
4
PWM
5
PWM
5
GND
IN2
PWM
Figure 9-2. PWM interface relay-driving application
Figure 9-1. PWM interface motor-driving
application
9.2.1.1 Design Requirements
Table 9-1 lists the required parameters for a typical usage case.
Table 9-1. System design requirements
DESIGN PARAMETER
REFERENCE
EXAMPLE VALUE
Motor supply voltage
VM
11 V
Logic supply voltage
VCC
3.3 V
Target motor RMS current
Imotor
300 mA
Target relay current
Irelay
50 mA
9.2.1.2 Detailed Design Procedure
9.2.1.2.1 Supply Voltage
The appropriate supply voltage depends on the ratings of the load (motor, solenoid, relay, etc.). In the case of a
brushed DC motor, the supply voltage will impact the desired RPM. A higher voltage spins a brushed dc motor
faster with the same PWM duty cycle applied to the power FETs. A higher voltage also increases the rate of
current change through the inductive windings of a motor, solenoid, or relay.
9.2.1.2.2 Control Interface
Section 8.3.2.1 describes the PWM control interface. The DRV8210P is pin-to-pin compatible with the DRV8837
and DRV8837C PCB footprints. Figure 9-3 and Figure 9-4 show waveform examples of driving a motor with the
PWM interface. Figure 9-5 and Figure 9-6 show waveform examples of driving a single-coil relay with the PWM
14
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interface. The relay can be driven between the forward/reverse states and the brake/coast states as shown in
the figures.
9.2.1.2.3 Low-Power Operation
Section 8.4.2 describes how to enter low-power sleep mode. When entering sleep mode, TI recommends setting
all inputs as a logic low to minimize system power.
9.2.1.3 Application Curves
A. Channel 1 = IN1
Channel 2 = IN2
Channel 3 = OUT1
A. Channel 1 = IN1
Channel 4 = OUT2
Channel 2 = Motor
Current
Channel 3 = OUT1
Channel 4 = OUT2
Figure 9-3. PWM driving for a motor with 50% duty
cycle, INx and OUTx voltages
Figure 9-4. PWM driving for a motor with 50% duty
cycle, signals and motor current
A. Channel 1 = IN1
Channel 2 = IN2
Channel 3 = VOUT1
A. Channel 1 = IN1
Channel 2 = IN2
Channel 3 = VOUT1
Channel 4 = VOUT2
Channel 6 = Relay
Switch
Channel 7 = Relay
Coil Current
Channel 4 = VOUT2
Channel 6 = Relay
Switch
Channel 7 = Relay
Coil Current
Figure 9-5. PWM driving for a single-coil latching
relay with driving profile FORWARD → COAST →
REVERSE → COAST
Figure 9-6. PWM driving for a single-coil latching
relay with driving profile FORWARD → BRAKE →
REVERSE → BRAKE
9.2.2 Dual-Coil Relay Driving
The PWM interface may also be used to drive a dual-coil latching relay. Figure 9-7 shows an example
schematic.
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VM
VCC
CBulk
0.1 …F
0.1 …F
1
8
DRV821xPDSG
VM
7
OUT1
3
Thermal
Pad
O
nSLEEP
OUT2
VM
Controller
VCC
2
Dualcoil
relay
VCC
6
IN1
4
PWM
5
GND
IN2
PWM
Figure 9-7. Dual-coil relay driving
9.2.2.1 Design Requirements
Table 9-2 provides example requirements for a dual-coil relay application.
Table 9-2. System design requirements
DESIGN PARAMETER
REFERENCE
Motor supply voltage
VM
EXAMPLE VALUE
6V
Logic supply voltage
VCC
3.3 V
Relay current
IOUT1, IOUT2
500 mA pulse for 100 ms
9.2.2.2 Detailed Design Procedure
9.2.2.2.1 Supply Voltage
The appropriate supply voltage depends on the ratings of the load.
9.2.2.2.2 Control Interface
The PWM interface can be used to drive dual-coil relays. Section 8.3.2.1 describes the PWM control interface.
Figure 9-8 and Figure 9-9 show a schematic and timing diagram for driving a dual-coil relay with the PWM
interface.
16
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VM
Sleep
mode
Drive Coil1
Sleep
mode
Drive Coil2
Sleep
mode
IN1
IN2
VM
Coil1
Coil2
VM
VOUT2
VOUT1
IOUT1
VOUT1
Hi-Z
IOUT2
Hi-Z
Hi-Z
Hi-Z
Hi-Z
GND
Dual-coil
relay
VM
VOUT2
Hi-Z
GND
IOUT1
Figure 9-8. Schematic of dual-coil relay driven by
the OUTx H-bridge
IOUT2
Figure 9-9. Timing diagram for driving a dual-coil
relay with PWM interface
Table 9-3 shows the logic table for the PWM interface. The descriptions in this table reflect how the input and
output states drive the dual coil relay. When Coil1 is driven (OUT1 voltage is at GND), The voltage at OUT2 will
go to VM. Because the center tap of the relay is also at VM, no current flows through Coil2. The same is true
when Coil2 is driven; Coil1 shorts to VM. The body diodes of the high-side FETs act as freewheeling diodes, so
extra external diodes are not needed. Figure 9-10 shows oscilloscope traces for this application.
Table 9-3. PWM control table for dual-coil relay driving
IN1
IN2
OUT1
OUT2
0
0
Hi-Z
Hi-Z
0
1
L
H
1
0
H
L
Drive Coil2
L
Drive Coil1 and Coil2 (invalid state for a
dual-coil latching relay)
1
1
L
DESCRIPTION
Outputs disabled (H-Bridge Hi-Z)
Drive Coil1
9.2.2.2.3 Low-Power Operation
Section 8.4.2 describes how to enter low-power sleep mode. When entering sleep mode, TI recommends setting
all inputs as a logic low to minimize system power.
To minimize leakage current into the OUTx pins (especially in battery-powered applications), connect the load
from OUTx to GND. As shown in the previous section, connecting the load from OUTx to VM is also possible,
but there may be some small leakage current into OUTx when it is disabled.
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9.2.2.3 Application Curves
A.
Channel 1 = IN1
Channel 2 = IN2
Channel 3 = VOUT1
Channel 4 = VOUT2
Channel 6 = Relay Switch
Channel 7 = Relay Coil1 Current
Channel 8 = Relay Coil2 Current
Figure 9-10. PWM driving for dual-coil relay
9.2.3 Current Sense
A small shunt resistor on the GND pin can provide current sense information back to the microcontroller ADC.
The microcontroller can use this information to detect motor load conditions, such as stall. shows an example
schematic using the DRL package. If better current sensing dynamic range is needed, an amplifier can be added
as shown in Figure 9-11.
The DSG thermal pad may be connected to the board ground net or the GND pin/sense signal net.
18
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VM
VCC
0.1 …F
CBulk
0.1 …F
1
VM
8
DRV821xPDSG
Controller
VCC
2
7
OUT1
BDC
VCC
nSLEEP
Thermal
Pad
3
O
6
OUT2
IN1
4
PWM
5
GND
IN2
+
PWM
TLV905I
ADC
RSENSE
CFILTER
R1
±
R2
Figure 9-11. Current sense amplifier example
9.2.3.1 Design Requirements
Table 9-4 provides example requirements for a current sensing application.
Table 9-4. System design requirements
DESIGN PARAMETER
REFERENCE
EXAMPLE VALUE
Motor supply voltage
VM
6V
Logic supply voltage
VCC
3.3 V
Maximum voltage across RSENSE
VSENSE
150 mV
Motor RMS current
IOUT1, IOUT2
500 mA
Motor stall current
IOUT1,stall, IOUT2,stall
1A
9.2.3.2 Detailed Design Procedure
9.2.3.2.1 Shunt Resistor Sizing
The Absolute Maximum Ratings for the INx pins set the maximum voltage across the shunt resistor. If the signal
on the INx pin is low, referenced at the board ground, then the INx pins are at a negative voltage with respect
to the GND pin voltage. This sets the maximum sense voltage/GND pin voltage to 0.5 V. Figure 9-12 shows the
relative pin voltages.
IN1
VIN2 = 0 V
+
VGND,pin = -0.5 V
+
RSENSE
IN2
GND
VSENSE = 0.5 V
-
VGND,board = 0 V
Figure 9-12. Pin voltages with respect to board ground using current sense resistor
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This example uses 150 mV for the maximum VSENSE, which is less than 0.5 V and provides some margin for
safety or error. The maximum current through the motor will be the stall current, which is 1 A for this example.
With this information, the sense resistance RSENSE can be calculated from the equation below.
RSENSE = VSENSE / ISTALL = 0.15 / 1 = 0.15 Ω
(1)
Because the device GND pin voltage will vary with current through the sense resistor, the designers must
also ensure that the logic pins meet VIL and VIH parameters,and the supply remains above VUVLO for proper
operation.
9.3 Current Capability and Thermal Performance
The output current and power dissipation capabilities of the driver depends heavily on the PCB design and
external system conditions. This section provides some guidelines for calculating these values.
9.3.1 Power Dissipation and Output Current Capability
Total power dissipation for the device consists of three main components: quiescent supply current dissipation
(PVM and PVCC), the power MOSFET switching losses (PSW), and the power MOSFET RDS(on) (conduction)
losses (PRDS). While other factors may contribute additional power losses, they are typically insignificant
compared to the three main items.
PTOT = PVM + PVCC + PSW + PRDS
(2)
PVM can be calculated from the nominal motor supply voltage (VVM) and the IVM active mode current
specification. PVCC can be calculated from the nominal logic supply voltage (VVCC) and the IVCC active mode
current specification. When VVCC < VVM, the DRV8210 draws active current from the VM pin rather than the VCC
pin. During this operating condition, IVCC is typically less than 500 nA.
PVM = VVM x IVM
(3)
PVM = 7 mW = 5 V x 1.4 mA
(4)
PVCC = VVCC x IVCC
(5)
PVCC = 0.594 mW = 3.3 V x 0.18 mA
(6)
PSW can be calculated from the nominal motor supply voltage (VVM), average output current (IRMS), switching
frequency (fPWM) and the device output rise (tRISE) and fall (tFALL) time specifications.
PSW = PSW_RISE + PSW_FALL
(7)
PSW_RISE = 0.5 x VM x IRMS x tRISE x fPWM
(8)
PSW_FALL = 0.5 x VM x IRMS x tFALL x fPWM
(9)
PSW_RISE = 3.75 mW = 0.5 x 5 V x 0.5 A x 150 ns x 20 kHz
(10)
PSW_FALL = 3.75 mW = 0.5 x 5 V x 0.5 A x 150 ns x 20 kHz
(11)
PSW = 7.5 mW = 3.75 mW + 3.75 mW
(12)
PRDS can be calculated from the device RDS(on) and average output current (IRMS).
PRDS = IRMS 2 x (RDS(ON)_HS + RDS(ON)_LS)
(13)
RDS(ON) has a strong correlation with the device temperature. Assuming a device junction temperature of 85
°C, RDS(on) could increase ~1.5x based on the normalized temperature data. The calculation below shows this
derating factor.
20
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PRDS = 394 mW = (0.5 A)2 x (525 mΩ x 1.5 + 525 mΩ x 1.5)
(14)
Based on the example calculations above, the expressions below calculate the total expected power dissipation
for the device.
PTOT = PVM + PVCC + PSW + PRDS
(15)
PTOT = 409 mW = 7 mW + 0.594 mW + 7.5 mW + 394 mW
(16)
The driver's junction temperature can be estimated using PTOT, device ambient temperature (TA), and package
thermal resistance (RθJA). The value for RθJA depends heavily on the PCB design and copper heat sinking
around the device. Section 9.3.2 describes this dependence in greater detail.
TJ = (PTOT x RθJA) + TA
(17)
TJ = 126°C = (0.409 W x 99.6 °C/W) + 85°C
(18)
The device junction temperature should remain below its absolute maximum rating for all system operating
conditions. The calculations in this section provide reasonable estimates for junction temperature. However,
other methods based on temperature measurements taken during system operation are more realistic and
reliable. Additional information on motor driver current ratings and power dissipation can be found in Section
9.3.2 and Section 12.1.1.
9.3.2 Thermal Performance
The datasheet-specified junction-to-ambient thermal resistance, RθJA, is primarily useful for comparing various
drivers or approximating thermal performance. However, the actual system performance may be better or worse
than this value depending on PCB stackup, routing, number of vias, and copper area around the thermal
pad. The length of time the driver drives a particular current will also impact power dissipation and thermal
performance. This section considers how to design for steady-state and transient thermal conditions.
The data in this section was simulated using the following criteria:
•
•
2-layer PCB, standard FR4, 1-oz (35 mm copper thickness) or 2-oz copper thickness. Thermal vias are only
present under the thermal pad (2 vias, 1.2mm spacing, 0.3 mm diameter, 0.025 mm Cu plating).
– Top layer: DRV8210P WSON package footprint and copper plane heatsink. Top layer copper area is
varied in simulation.
– Bottom layer: ground plane thermally connected through vias under the thermal pad for DRV8210P.
Bottom layer copper area varies with top copper area.
4-layer PCB, standard FR4. Outer planes are 1-oz (35 mm copper thickness) or 2-oz copper thickness. Inner
planes are kept at 1-oz. Thermal vias are only present under the thermal pad (2 vias, 1.2mm spacing, 0.3 mm
diameter, 0.025 mm Cu plating).
– Top layer: DRV8210P WSON package footprint and copper plane heatsink. Top layer copper area is
varied in simulation.
– Mid layer 1: GND plane thermally connected to DRV8210P thermal pad through vias. The area of the
ground plane is 74.2 mm x 74.2 mm.
– Mid layer 2: power plane, no thermal connection. The area of the power plane is 74.2 mm x 74.2 mm.
– Bottom layer: signal layer with small copper pad underneath DRV8210P and thermally connected through
via stitching from the TOP and internal GND planes. Bottom layer thermal pad is the same size as the
package (2 mm x 2 mm). Bottom pad size remains constant as top copper plane is varied.
Figure 9-13 shows an example of the simulated board for the HTSSOP package. Table 9-5 shows the
dimensions of the board that were varied for each simulation.
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A
A
Figure 9-13. WSON PCB model top layer
Table 9-5. Dimension A for 16-pin PWP package
Cu area (mm2)
Dimension A (mm)
2
15.11
4
20.98
8
29.27
16
40.99
9.3.2.1 Steady-State Thermal Performance
"Steady-state" conditions assume that the motor driver operates with a constant RMS current over a long
period of time. The figures in this section show how RθJA and ΨJB (junction-to-board characterization parameter)
change depending on copper area, copper thickness, and number of layers of the PCB. More copper area, more
layers, and thicker copper planes decrease RθJA and ΨJB, which indicate better thermal performance from the
PCB layout.
Figure 9-14. WSON, PCB junction-to-ambient
thermal resistance vs copper area
Figure 9-15. WSON, junction-to-board
characterization parameter vs copper area
9.3.2.2 Transient Thermal Performance
The motor driver may experience different transient driving conditions that cause large currents to flow for a
short duration of time. These may include
•
22
Motor start-up when the rotor is initially stationary.
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•
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Fault conditions when there is a supply or ground short to one of the motor outputs, and the overcurrent
protection triggers.
Briefly energizing a motor or solenoid for a limited time, then de-energizing.
For these transient cases, the duration of drive time is another factor that impacts thermal performance in
addition to copper area and thickness. In transient cases, the thermal impedance parameter ZθJA denotes the
junction-to-ambient thermal performance. The figures in this section show the simulated thermal impedances for
1-oz and 2-oz copper layouts for the WSON package. These graphs indicate better thermal performance with
short current pulses. For short periods of drive time, the device die size and package dominates the thermal
performance. For longer drive pulses, board layout has a more significant impact on thermal performance. Both
graphs show the curves for thermal impedance split due to number of layers and copper area as the duration of
the drive pulse duration increases. Long pulses can be considered steady-state performance.
Figure 9-16. WSON package junction-to-ambient thermal impedance for 1-oz copper layouts
Figure 9-17. WSON package Junction-to-ambient thermal impedance for 2-oz copper layouts
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10 Power Supply Recommendations
10.1 Bulk Capacitance
Having appropriate local bulk capacitance is an important factor in motor drive system design. Having more bulk
capacitance is generally beneficial, while the disadvantages are increased cost and physical size.
The amount of local bulk capacitance needed depends on a variety of factors, including:
• The highest current required by the motor or load
• The capacitance of the power supply and ability to source current
• The amount of parasitic inductance between the power supply and motor system
• The acceptable voltage ripple of the system
• The motor braking method (if applicable)
The inductance between the power supply and motor drive system limits how the rate current can change from
the power supply. If the local bulk capacitance is too small, the system responds to excessive current demands
or dumps from the motor with a change in voltage. When adequate bulk capacitance is used, the motor voltage
remains stable and high current can be quickly supplied.
The data sheet generally provides a recommended minimum value, but system level testing is required to
determine the appropriately sized bulk capacitor.
Power Supply
Parasitic Wire
Inductance
Motor Drive System
VBB
+
±
+
Motor
Driver
GND
Local
Bulk Capacitor
IC Bypass
Capacitor
Figure 10-1. System Supply Parasitics Example
24
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11 Layout
11.1 Layout Guidelines
Since the DRV8210P device has integrated power MOSFETs capable of driving high current, careful attention
should be paid to the layout design and external component placement. Some design and layout guidelines
are provided below. For more information on layout recommendations, please see the application note Best
Practices for Board Layout of Motor Drivers.
•
•
•
•
•
•
•
Low ESR ceramic capacitors should be utilized for the VM-to-GND and VCC-to-GND bypass capacitors. X5R
and X7R types are recommended.
The VM and VCC power supply capacitors should be placed as close to the device as possible to minimize
the loop inductance.
The VM power supply bulk capacitor can be of ceramic or electrolytic type, but should also be placed as
close as possible to the device to minimize the loop inductance.
VM, OUT1, OUT2, and GND carry the high current from the power supply to the outputs and back to ground.
Thick metal routing should be utilized for these traces as is feasible.
GND should connect directly on the PCB ground plane.
The device thermal pad should be attached to the PCB top layer ground plane and internal ground plane
(when available) through thermal vias to maximize the PCB heat sinking.
The copper plane area attached to the thermal pad should be maximized to ensure optimal heat sinking.
11.2 Layout Example
CBULK
0.1 …F
0.1 …F
VM
MOT+
VM
1
OUT1
2
8
VCC
7
nSLEEP
6
IN1
5
IN2
VCC
Thermal
MOT-
OUT2
3
GND
4
Pad
Figure 11-1. Simplified Layout Example
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12 Device and Documentation Support
12.1 Documentation Support
12.1.1 Related Documentation
For related documentation see the following:
• Texas Instruments, Calculating Motor Driver Power Dissipation application report
• Texas Instruments, PowerPAD™ Made Easy application report application report
• Texas Instruments, PowerPAD™ Thermally Enhanced Package application report
• Texas Instruments, Understanding Motor Driver Current Ratings application report
• Texas Instruments, Best Practices for Board Layout of Motor Drivers application report
12.2 Receiving Notification of Documentation Updates
To receive notification of documentation updates, navigate to the device product folder on ti.com. Click on
Subscribe to updates to register and receive a weekly digest of any product information that has changed. For
change details, review the revision history included in any revised document.
12.3 Support Resources
TI E2E™ support forums are an engineer's go-to source for fast, verified answers and design help — straight
from the experts. Search existing answers or ask your own question to get the quick design help you need.
Linked content is provided "AS IS" by the respective contributors. They do not constitute TI specifications and do
not necessarily reflect TI's views; see TI's Terms of Use.
12.4 Trademarks
TI E2E™ is a trademark of Texas Instruments.
All trademarks are the property of their respective owners.
12.5 Electrostatic Discharge Caution
This integrated circuit can be damaged by ESD. Texas Instruments recommends that all integrated circuits be handled
with appropriate precautions. Failure to observe proper handling and installation procedures can cause damage.
ESD damage can range from subtle performance degradation to complete device failure. Precision integrated circuits may
be more susceptible to damage because very small parametric changes could cause the device not to meet its published
specifications.
12.6 Glossary
TI Glossary
26
This glossary lists and explains terms, acronyms, and definitions.
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13 Mechanical, Packaging, and Orderable Information
The following pages include mechanical, packaging, and orderable information. This information is the most
current data available for the designated devices. This data is subject to change without notice and revision of
this document. For browser-based versions of this data sheet, refer to the left-hand navigation.
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PACKAGE OPTION ADDENDUM
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PACKAGING INFORMATION
Orderable Device
Status
(1)
Package Type Package Pins Package
Drawing
Qty
Eco Plan
(2)
Lead finish/
Ball material
MSL Peak Temp
Op Temp (°C)
Device Marking
(3)
(4/5)
(6)
DRV8210PDSGR
ACTIVE
WSON
DSG
8
3000
RoHS & Green
NIPDAU
Level-1-260C-UNLIM
-40 to 125
210P
(1)
The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2)
RoHS: TI defines "RoHS" to mean semiconductor products that are compliant with the current EU RoHS requirements for all 10 RoHS substances, including the requirement that RoHS substance
do not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, "RoHS" products are suitable for use in specified lead-free processes. TI may
reference these types of products as "Pb-Free".
RoHS Exempt: TI defines "RoHS Exempt" to mean products that contain lead but are compliant with EU RoHS pursuant to a specific EU RoHS exemption.
Green: TI defines "Green" to mean the content of Chlorine (Cl) and Bromine (Br) based flame retardants meet JS709B low halogen requirements of