LM10524
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SNVS986A – AUGUST 2013 – REVISED JANUARY 2014
LM10524 Triple Buck Power Management Unit
Check for Samples: LM10524
FEATURES
DESCRIPTION
•
LM10524 is an advanced PMU containing three
configurable, high-efficiency buck regulators for
supplying variable voltages. The device is ideal for
supporting ASIC and SOC designs for SSD and
Flash drives.
1
2
•
•
•
•
•
•
•
Three Highly Efficient Programmable Buck
Regulators
– Integrated FETs with Low RDSON
– Bucks Operate with Their Phases Shifted to
Reduce the Input Current Ripple and
Capacitor Size
– Programmable Output Voltage via the SPI
Interface
– Over and Under-Voltage-Lockout
– Automatic Internal Soft Start with PowerOn-Reset
– Current Overload and Thermal Shutdown
Protection
– PFM Mode for High Efficiency at Light Load
Conditions
Power-Down Data Protection Enhances Data
Integrity
Bypass Mode Available on Buck 1
Sleep Mode to Save Power During Idle Times
– DEVSLP Function
SPI-Programmable Interrupt Comparator (2.0V
to 4.0V)
Factory Programmable Startup Sequencing for
Varied Controllers
Fast Startup for all Voltage Rails in about
3.5ms to PWR_OK
Fast Turn-off / Active Discharge on Regulator
Outputs
The LM10524 can operate cooperatively with an
ASIC to optimize the supply voltage for low-power
conditions and to control power saving modes via the
SPI interface.
KEY SPECIFICATIONS
•
•
•
•
•
•
Single input rail with wide range: 3.3 to 5.5V
Programmable Buck Regulator Outputs:
– Buck 1: 1.1V to 3.6V; 1.6A
– Buck 2: 1.1V to 3.6V; 1A
– Buck 3: 0.7V to 1.95V; 2.5A
±3% feedback voltage accuracy
Up to 95% efficient buck regulators
2MHz switching frequency for smaller inductor
size
2.815mm, 3.215mm, 0.4mm pitch, 46 bump
micro SMD package
APPLICATION
•
Solid-State Drives
1
2
Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of
Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet.
All trademarks are the property of their respective owners.
PRODUCTION DATA information is current as of publication date.
Products conform to specifications per the terms of the Texas
Instruments standard warranty. Production processing does not
necessarily include testing of all parameters.
Copyright © 2013–2014, Texas Instruments Incorporated
LM10524
SNVS986A – AUGUST 2013 – REVISED JANUARY 2014
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Typical Application Diagram
LM10524
DEVSLP_OVR1
DEVSLP_OVR2
IO Input
Supply
Power Supply
3.3 / 5.5V
CONTROL LOGIC and REGISTERS
C8
2.2uF
VIN
VIN_B1
C5
4.7uF
VIN_B2
C6
4.7uF
IRQ
SW_B1
BUCK1
2.2uH
1.1 to 3.6V, 1.6A
C1
47uF
L2
SW_B2
BUCK2
2.2uH
1.1 to 3.6V, 1.0A
C2
47uF
FB_B2
L3
SW_B3
1.0uH
Host 1
Flash
Vcc
2.85V
Host 2
Domain
Vccq
1.8V
0.7 to 1.95V, 2.5A
C3
47uF
Host 3
Domain
Vcore
1.0V
GND
VIN_B3
GND
L1
FB_B1
BUCK3
GND
System
Control
Vcomp
COMP
FB_B3
C7
4.7uF
ASIC / SoC
SPI_CS
SPI_DI
SPI SPI_DO
SPI_CLK
VIN_IO
C4
2.2uF
SLEEP_EN
DEVSLP_ CTRL
POWERUP_MODE
DEVSLP
PWR_OK
2
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SNVS986A – AUGUST 2013 – REVISED JANUARY 2014
Overview
The LM10524 contains three buck converters. Supply Specification below lists the output characteristics of the
power regulators.
Supply Specification
(1)
Regulator
Default VOUT at Start-Up
VOUT if DEVSLP=High
(DEVSLP mode)
Output Voltage Range
Max Output Current
BUCK1 (1)
2.85 V
OFF
1.1V to 3.6V; 50 mV steps
1.6A
BUCK2 (1)
1.8 V
OFF
1.1V to 3.6V; 50 mV steps
1.0A
BUCK3 (1)
1.0V
OFF
0.7V to 1.95V; 10mV
steps
2.5A
Default voltage values are determined when working in PWM mode. Voltage may be 0.8-1.6% higher when in PFM mode..
3
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Connection Diagram And Package Marking
TOP VIEW LOOKING THROUGH THE PACKAGE
1
2
3
4
5
6
7
A
VIN_IO
PWR_OK
VIN
DEVSLP
VIN_B1
SW_B1
GND_B1
B
GND
GND
VCOMP
FB_B1
VIN_B1
SW_B1
GND_B1
C
SPI_
CLK
GND
IRQ
FB_B1
FB_B1
FREE
DEVSLP
_OVR1
D
SPI_DI
DEVSLP
_OVR2
E
SPI_DO
DEVSLP
_CTRL
F
SPI_CS
SW_B2
FB_B2
FREE
FB_B3
SW_B3
SLEEP
_EN
G
GND_B2
SW_B2
VIN_B2
FREE
VIN_B3
SW_B3
GND_B3
H
GND_B2
SW_B2
VIN_B2
POWER
UP_MODE
VIN_B3
SW_B3
GND_B3
Figure 1. 46 Bump Micro SMD with 0.4mm Pitch
4
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SNVS986A – AUGUST 2013 – REVISED JANUARY 2014
Table 1. 9.0 LM10524 Pin Description
(1)
Pin #
Pin Name
I/O
A4
DEVSLP
I
D
E7
DEVSLP_CTRL
O
D
Indicates DevSLP signal is active but drives low when device is in SLEEP mode.
C7
DEVSLP_OVR1
I
D
Used to gate activation of device sleep.
D7
DEVSLP_OVR2
I
D
C5
FB_B1
I/O
A
Buck Switcher Regulator 1 - Voltage output feedback plus Bypass Power.
B4
FB_B1
I/O
A
Buck Switcher Regulator 1 - Voltage output feedback plus Bypass Power.
C4
FB_B1
I/O
A
Buck Switcher Regulator 1 - Voltage output feedback plus Bypass Power.
F3
FB_B2
I
A
Buck Switcher Regulator 2 - Voltage output feedback.
F5
FB_B3
I
A
Buck Switcher Regulator 3 - Voltage output feedback.
C6
FREE
Not Used.
F4
FREE
Not Used.
G4
FREE
Not Used.
B1
GND
G
G
Ground. Connect to system Ground.
B2
GND
G
G
Ground. Connect to system Ground.
C2
GND
G
G
Ground. Connect to system Ground.
A7
GND_B1
G
P
Buck Switcher Regulator 1 - Power ground for Buck Regulator.
(1)
(2)
Type
(2)
Functional Description
Digital Input Control Signal for entering Device Sleep Mode. Input activates the device
sleep function in conjunction with DEVSLP_OVR1, DEVSLP_OVR2, and PowerUp_mode.
This is an active High pin with an option for an internal pullup resistor. Turns off all outputs
and internal oscillator.
Used to gate activation of device sleep.
B7
GND_B1
G
P
Buck Switcher Regulator 1 - Power ground for Buck Regulator.
G1
GND_B2
G
P
Buck Switcher Regulator 2 - Power ground for Buck Regulator.
H1
GND_B2
G
P
Buck Switcher Regulator 2 - Power ground for Buck Regulator.
G7
GND_B3
G
P
Buck Switcher Regulator 3 - Power ground for Buck Regulator.
H7
GND_B3
G
P
Buck Switcher Regulator 3 - Power ground for Buck Regulator.
C3
IRQ
O
D
Interrupt. Digital Output of Comparator to signal interrupt condition.
A2
PWR_OK
O
D
PWR_OK Signal, Push Pull output.
H4
POWERUP
_MODE
I/O
D
Used to indicate SSD initialization is complete. Once initialization is complete, this pin
should be externally pulled low to allow Sleep mode activation via DEVSLP
F7
SLEEP_EN
O
D
Active high output indicates device is in Sleep Mode.
C1
SPI_CLK
I
D
SPI Interface - serial clock input.
F1
SPI_CS
I
D
SPI Interface - chip select.
D1
SPI_DI
I
D
SPI Interface - serial data input.
E1
SPI_DO
O
D
SPI Interface - serial data output.
A6
SW_B1
I/O
P
Buck Switcher Regulator 1 - Power Switching node, connect to inductor.
B6
SW_B1
I/O
P
Buck Switcher Regulator 1 - Power Switching node, connect to inductor.
F2
SW_B2
I/O
P
Buck Switcher Regulator 2 - Power Switching node, connect to inductor.
G2
SW_B2
I/O
P
Buck Switcher Regulator 2 - Power Switching node, connect to inductor.
H2
SW_B2
I/O
P
Buck Switcher Regulator 2 - Power Switching node, connect to inductor.
F6
SW_B3
I/O
P
Buck Switcher Regulator 3 - Power Switching node, connect to inductor.
G6
SW_B3
I/O
P
Buck Switcher Regulator 3 - Power Switching node, connect to inductor.
H6
SW_B3
I/O
P
Buck Switcher Regulator 3 - Power Switching node, connect to inductor.
B3
VCOMP
I
A
Analog Input for Comparator.
A3
VIN
I
P
Power supply Input Voltage — must be present for device to work; decouple closely to D7.
A5
VIN_B1
I
P
Buck Switcher Regulator 1 - Power supply voltage input for power stage PFET, if Buck 1 is
not used, tie to ground to reduce leakage.
B5
VIN_B1
I
P
Buck Switcher Regulator 1 - Power supply voltage input for power stage PFET, if Buck 1 is
not used, tie to ground to reduce leakage.
I: Input Pin, O: Output Pin
A: Analog Pin, D: Digital Pin, G: Ground, P: Power Connection
5
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Table 1. 9.0 LM10524 Pin Description (continued)
(1)
Type (2) Functional Description
Pin #
Pin Name
I/O
G3
VIN_B2
I
P
Buck Switcher Regulator 2 - Power supply voltage input for power stage PFET, if Buck 2 is
not used, tie to ground to reduce leakage.
H3
VIN_B2
I
P
Buck Switcher Regulator 2 - Power supply voltage input for power stage PFET, if Buck 2 is
not used, tie to ground to reduce leakage.
G5
VIN_B3
I
P
Buck Switcher Regulator 3 - Power supply voltage input for power stage PFET.
H5
VIN_B3
I
P
Buck Switcher Regulator 3 - Power supply voltage input for power stage PFET..
A1
VIN_IO
I
A
Supply Voltage for Digital Interface.
Table 2. Device Information
Part Number
Buck 1 Bypass
FPWM Default
Package Type
Product
Identification
LM10524TME
Disabled
All Bucks
micro SMD
V088
Supplied as
250 Tape & Reel
LM10524TMX
LM10524TME-A
1000 Tape & Reel
Disabled
Bucks 2 + 3
micro SMD
V089
250 Tape & Reel
LM10524TMX-A
1000 Tape & Reel
These devices have limited built-in ESD protection. The leads should be shorted together or the device placed in conductive foam
during storage or handling to prevent electrostatic damage to the MOS gates.
Absolute Maximum Ratings (1) (2)
Pins
Min
Max
Units
VIN, VCOMP
-0.3
6
V
VIN_IO, VIN_B1, VIN_B2, VIN_B3, SPI_CS, SPI_DI, SPI_CLK, SPI_DO, DEVSLP,
DEVSLP_CTRL, SLEEP_EN, POWERUP MODE, SW_1, SW_2, SW_3, FB_1,
FB_2, FB_3, PWR_OK, IRQ, DEVSLP_OVR1, DEVSLP_OVR2
-0.3
VVIN
Junction Temperature, TJ-MAX
150
Storage Temperature
-65
ESD Rating, HBM – Human Body Model
(1)
(2)
°C
150
1
kV
Absolute Maximum Ratings are limits beyond which damage to the device may occur. Operating Ratings are conditions under which
operation of the device is ensured. Operating Ratings do not imply ensured performance limits. For ensured performance limits and
associated test conditions, see the Electrical Characteristics tables.
If Military/Aerospace specified devices are required, please contact the TI Sales Office/Distributors for availability and specifications.
Operating Ratings (1) (2) (3)
Pins
Min
Max
Units
3
5.5
V
1.72
VVIN
0
VVIN
Junction Temperature, TJ
-30
125
Ambient Temperature, TA
-30
85
VIN_B1, VIN_B2, VIN_B3, VIN
VIN_IO
All other Input Pins
°C
Junction-to-Ambient Thermal resistance, θJA
40
°C/W
Maximum Continuous Power Dissipation, PDMAX
1
W
(1)
(2)
(3)
Internal thermal shutdown protects device from permanent damage. Thermal shutdown engages at TJ = +140°C and disengages at TJ
= +120°C (typ.). Thermal shutdown is ensured by design.
In applications where high power dissipation and/or poor thermal resistance is present the maximum ambient temperature may have to
be derated. Maximum ambient temperature (TA-MAX) is dependent on the maximum operating junvction temperature (TJ-MAX-OP =
+125°C), the maximum power dissipation of the device in the application (PD-MAX), and the junction-to-ambient thermal resistance of the
part/package in the application (θJA), as given by the following equation: TA-MAX = TJ-MAX-OP – (θJA × PD-MAX).
The amount of Absolute Maximum power dissipation allowed for the device depends on the ambient temperature and can be calculated
using the formula: P = (TJ–TA)/θJA, where TJ is the junction temperature, TA is the ambient temperature, and θJA is the junction-toambient thermal resistance. θJA is highly application and board-layout dependent. Internal thermal shutdown circuitry protects the device
from permanent damage. (See General Electrical Characteristics).
6
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General Electrical Characteristics (1) (2)
Unless otherwise noted, VVIN = 5.0V where: VVIN=VVIN_B1 = VVIN_B2 = VVIN_B3. VVIN_I0 = 3.0V.
The application circuit used is the one shown in “Typical Application Circuit".
Limits in standard typeface are for TJ = 25°C.
Limits in boldface type apply over the full operating junction temperature range of -30°C ≤ TA=TJ ≤ +85°C.
Symbol
Parameter
Conditions
Min
IQ(DEVSLP)
Quiescent supply
current.
DevSLP=High
No load.
Typ
Max
Units
50
200
µA
V
UNDER/OVER VOLTAGE LOCK OUT
VUVLO_RISING
2.7
2.9
3.135
VUVLO_FALLING
2.45
2.6
2.75
VOVLO_RISING
6.05
VOVLO_FALLING
5.75
DIGITAL INTERFACE
VIL
Logic Input Low
VIH
Logic Input High
VIL
Logic Input Low
VIH
Logic Input High
VIL
Logic Input Low
VIH
Logic Input High
VOL
Logic output Low
VOH
Logic output High
IIL
Input Current, pin
driven low
SPI_CS, SPI_DI, SPI_CLK
-2
DEVSLP
-5
IIH
Input Current, pin
driven high
SPI_CS, SPI_DI, SPI_CLK,DEVSLP
fSPI_MAX
SPI max
frequency
(1)
(2)
(3)
SPI_CS, SPI_DI, SPI_CLK,
POWERUP_MODE
(3)
0.3*VVIN_IO
V
0.7*VVIN_IO
DEVSLP_OVR1, DEVSLP_OVR2
0.3*VVIN
(3)
0.7*VVIN
DEVSLP (3)
0.3V
1.2V
IRQ (at 2mA load), SPI_DO,
DEVSLP_CTRL (3), SLEEP_EN (3),PWR_OK
0.2*VVIN_IO
0.8*VVIN_IO
µA
2
10
MHz
All limits are ensured by design, test and/or statistical analysis. All electrical characteristics having room-temperature limits are tested
during production with TJ = 25°C. All hot and cold limits are ensured by correlating the electrical characteristics to process and
temperature variations and applying statistical process control.
Capacitors: Low-ESR Surface-Mount Ceramic Capacitors (MLCCs) are used in setting electrical characteristics.
Specification ensured by design. Not tested during production.
7
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Buck 1 Electrical Characteristics (1) (2) (3)
Unless otherwise noted, VVIN = 5.0V where: VVIN=VVIN_B1 = VVIN_B2 = VVIN_B3.
The application circuit used is the one shown in “Typical Application Circuit".
Limits in standard typeface are for TJ = 25°C.
Limits in boldface type apply over the full operating junction temperature range of -30°C ≤ TA=TJ ≤ +85°C.
Symbol
Parameter
Conditions
Min
IQ
DC Bias Current in VIN
No Load, PFM Mode
IOUT-MAX
Continuous maximum load
current (4) (5) (6)
Buck 1 enabled, switching in PWM
1.6
IPEAK
Peak switching current limit
Buck 1 enabled, switching in PWM
1.9
η
Efficiency peak, Buck 1 (4)
IOUT = 0.3 A, VVIN = 3.3V
FSW
Switching Frequency
CIN
Input Capacitor (4)
COUT
Output Filter Capacitor (4)
Typ
Max
Units
15
50
µA
A
2.2
1.75
0mA ≤ IOUT ≤ IOUT-MAX
2
47
∆VOUT
MHz
µF
100
20
Output Filter Inductance (4)
(4)
%
2.3
4.7
22
Output Capacitor ESR (4)
L
2.8
90
mΩ
2.2
µH
3.3V ≤ VVIN ≤ 5V, IOUT = IOUT-MAX
0.5
%/V
DC Load regulation, PWM (4)
VVIN=3.3V, 0.1 * IOUT-MAX ≤ IOUT ≤
IOUT-MAX
0.3
%/A
IFB
Feedback pin input bias
current
VFB = 2.85V
2.3
VFB
Feedback Accuracy
VFB = 2.85V
RDS-ON-HS
High Side Switch On
Resistance
RDS-ON-LS
Low Side Switch On
Resistance
RDS-ON-BYPASS
Bypass FET on resistance
DC Line regulation
-3
5
3
115
VVIN = 2.6V
µA
%
mΩ
190
60
110
Used in parallel with the high side
FET while in Bypass mode.
Resistance (DCR) of inductor = 100
mΩ
VIN = 3.1V
75
VIN = 2.6V
120
mΩ
Startup
Tstart_NoLoad
Internal soft-start (turn on
time) (4)
Start up from shutdown, VOUT=0V,
no load, LC = recommended circuit,
using software enable, to VOUT =
95% of final value
0.1
Tstart_FullLoad
Internal soft-start (turn on
time) (4)
Start up from shutdown, VOUT
=0V, Maximum Load, LC =
recommended circuit, using
software enable, to VOUT = 95% of
final value
0.5
(1)
(2)
(3)
(4)
(5)
(6)
ms
All limits are ensured by design, test and/or statistical analysis. All electrical characteristics having room-temperature limits are tested
during production with TJ = 25°C. All hot and cold limits are ensured by correlating the electrical characteristics to process and
temperature variations and applying statistical process control.
Capacitors: Low-ESR Surface-Mount Ceramic Capacitors (MLCCs) are used in setting electrical characteristics.
BUCK normal operation is ensured if VIN ≥ VOUT+1.0V.
Specification ensured by design. Not tested during production.
In applications where high power dissipation and/or poor thermal resistance is present the maximum ambient temperature may have to
be derated. Maximum ambient temperature (TA-MAX) is dependent on the maximum operating junction temperature (TJ-MAX-OP = +125°C),
the maximum power dissipation of the device in the application (PD-MAX), and the junction-to-ambient thermal resistance of the
part/package in the application (θJA), as given by the following equation: TA-MAX = TJ-MAX-OP – (θJA × PD-MAX).
The amount of Absolute Maximum power dissipation allowed for the device depends on the ambient temperature and can be calculated
using the formula: P = (TJ–TA)/θJA, where TJ is the junction temperature, TA is the ambient temperature, and θJA is the junction-toambient thermal resistance. θJA is highly application and board-layout dependent. Internal thermal shutdown circuitry protects the device
from permanent damage. (See General Electrical Characteristics.)
8
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Buck 2 Electrical Characteristics (1) (2) (3)
Unless otherwise noted, VVIN = 5.0V where: VVIN=VVIN_B1 = VVIN_B2 = VVIN_B3.
The application circuit used is the one shown in “Typical Application Circuit".
Limits in standard typeface are for TJ = 25°C.
Limits in boldface type apply over the full operating junction temperature range of -30°C ≤ TA=TJ ≤ +85°C.
Symbol
Parameter
Conditions
Min
IQ
DC Bias Current in VIN
No Load, PFM Mode
IOUT-MAX
Continuous maximum load
current (4) (5) (6)
Buck 2 enabled, switching in PWM
1
IPEAK
Peak switching current limit
Buck 2 enabled, switching in PWM
1.35
η
Efficiency peak, Buck2 (4)
IOUT = 0.3 A, VVIN = 3.3V
FSW
Switching Frequency
CIN
Input Capacitor (4)
COUT
Output Filter Capacitor (4)
Typ
Max
Units
15
50
µA
A
1.55
1.75
0mA ≤ IOUT ≤ IOUT-MAX
2
47
∆VOUT
µF
µH
%/V
3.3V ≤ VVIN ≤ 5V, IOUT = IOUT-MAX
0.5
V VIN=3.3V, 100mA ≤ IOUT ≤ IOUT-MAX
0.3
IFB
Feedback pin input bias
current
VFB = 1.8V
2.3
VFB
Feedback Accuracy
VFB = 1.8V
RDS-ON-HS
High Side Switch On
Resistance
RDS-ON-LS
Low Side Switch On
Resistance
-3
%/A
5
3
125
VVIN = 2.6V
mΩ
2.2
DC Load regulation, PWM (4)
DC Line regulation
MHz
100
20
Output Filter Inductance (4)
(4)
%
2.3
4.7
22
Output Capacitor ESR (4)
L
1.90
90
µA
%
mΩ
200
60
110
Startup
Tstart_NoLoad
Internal soft-start (turn on
time) (4)
Start up from shutdown, VOUT=0V, no
load, LC = recommended circuit, using
software enable, to VOUT = 95% of
final value
0.1
Tstart_FullLoad
Internal soft-start (turn on
time) (4)
Start up from shutdown, VOUT =0V,
Maximum Load, LC = recommended
circuit, using software enable, to
VOUT = 95% of final value
0.5
(1)
(2)
(3)
(4)
(5)
(6)
ms
All limits are ensured by design, test and/or statistical analysis. All electrical characteristics having room-temperature limits are tested
during production with TJ = 25°C. All hot and cold limits are ensured by correlating the electrical characteristics to process and
temperature variations and applying statistical process control.
Capacitors: Low-ESR Surface-Mount Ceramic Capacitors (MLCCs) are used in setting electrical characteristics.
BUCK normal operation is ensured if VIN ≥ VOUT+1.0V.
Specification ensured by design. Not tested during production.
In applications where high power dissipation and/or poor thermal resistance is present the maximum ambient temperature may have to
be derated. Maximum ambient temperature (TA-MAX) is dependent on the maximum operating junction temperature (TJ-MAX-OP = +125°C),
the maximum power dissipation of the device in the application (PD-MAX), and the junction-to-ambient thermal resistance of the
part/package in the application (θJA), as given by the following equation: TA-MAX = TJ-MAX-OP – (θJA × PD-MAX).
The amount of Absolute Maximum power dissipation allowed for the device depends on the ambient temperature and can be calculated
using the formula: P = (TJ–TA)/θJA, where TJ is the junction temperature, TA is the ambient temperature, and θJA is the junction-toambient thermal resistance. θJA is highly application and board-layout dependent. Internal thermal shutdown circuitry protects the device
from permanent damage. (See General Electrical Characteristics.)
9
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Product Folder Links: LM10524
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Buck 3 Electrical Characteristics (1) (2) (3)
Unless otherwise noted, VVIN = 5.0V where: VVIN=VVIN_B1 = VVIN_B2 = VVIN_B3.
The application circuit used is the one shown in “Typical Application Circuit".
Limits in standard typeface are for TJ = 25°C.
Limits in boldface type apply over the full operating junction temperature range of -30°C ≤ TA=TJ ≤ +85°C.
Symbol
Parameter
Conditions
Min
IQ
DC Bias Current in VIN
No Load, PFM Mode
IOUT-MAX
Continuous Peak load
current (4) (5) (6)
Buck 3 enabled, switching in PWM
2.5
IPEAK
Peak switching current limit
Buck 3 enabled, switching in PWM
2.9
η
Efficiency peak, Buck3 (4)
IOUT = 0.3 A, VVIN = 3.3V
FSW
Switching Frequency
CIN
Input Capacitor (4)
COUT
Output Filter Capacitor (4)
Typ
Max
Units
15
50
µA
A
3.5
90
1.75
0mA ≤ IOUT ≤ IOUT-MAX
2
4.7
47
47
Output Capacitor ESR (4)
∆VOUT
(4)
%/V
0.5
VIN=5V, 100mA ≤ IOUT ≤ IOUT-MAX
0.3
IFB
Feedback pin input bias
current
VFB = 1.0V
3.0
VFB
Feedback Accuracy
VFB = 1.0V
RDS-ON-HS
High Side Switch On
Resistance
-3
%/A
5
3
95
VVIN = 2.6V
Low Side Switch On
Resistance
mΩ
µH
3.3V ≤ VVIN ≤ 5V, IOUT = IOUT-MAX
RDS-ON-LS
µF
1
DC Load regulation, PWM (4)
DC Line regulation
MHz
100
20
Output Filter Inductance (4)
L
%
2.3
µA
%
mΩ
140
45
90
Startup
Tstart_NoLoad
Internal soft-start (turn on
time) (4)
Start up from shutdown, VOUT=0V, no
load, LC = recommended circuit, using
software enable, to VOUT = 95% of
final value
0.1
Tstart_FullLoad
Internal soft-start (turn on
time) (4)
Start up from shutdown, VOUT=0V,
Maximum Load, LC = recommended
circuit, using software enable, to VOUT
= 95% of final value
0.5
(1)
(2)
(3)
(4)
(5)
(6)
ms
All limits are ensured by design, test and/or statistical analysis. All electrical characteristics having room-temperature limits are tested
during production with TJ = 25°C. All hot and cold limits are ensured by correlating the electrical characteristics to process and
temperature variations and applying statistical process control.
Capacitors: Low-ESR Surface-Mount Ceramic Capacitors (MLCCs) are used in setting electrical characteristics.
BUCK normal operation is ensured if VIN ≥ VOUT+1.0V.
Specification ensured by design. Not tested during production.
In applications where high power dissipation and/or poor thermal resistance is present the maximum ambient temperature may have to
be derated. Maximum ambient temperature (TA-MAX) is dependent on the maximum operating junction temperature (TJ-MAX-OP = +125°C),
the maximum power dissipation of the device in the application (PD-MAX), and the junction-to-ambient thermal resistance of the
part/package in the application (θJA), as given by the following equation: TA-MAX = TJ-MAX-OP – (θJA × PD-MAX).
The amount of Absolute Maximum power dissipation allowed for the device depends on the ambient temperature and can be calculated
using the formula: P = (TJ–TA)/θJA, where TJ is the junction temperature, TA is the ambient temperature, and θJA is the junction-toambient thermal resistance. θJA is highly application and board-layout dependent. Internal thermal shutdown circuitry protects the device
from permanent damage. (See General Electrical Characteristics.)
10
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Comparators Electrical Characteristics (1) (2)
Unless otherwise noted, VVIN = 5.0V where: VVIN=VVIN_B1 = VVIN_B2 = VVIN_B3.
The application circuit used is the one shown in “Typical Application Circuit".
Limits in standard typeface are for TJ = 25°C.
Limits in boldface type apply over the full operating junction temperature range of -30°C ≤ TA=TJ ≤ +85°C.
Symbol
Parameter
Conditions
IVCOMP
VCOMP pin bias current
Min
Typ
Max
Units
VCOMP = 0.0V
0.1
2
µA
VCOMP = 5.0V
0.1
2
VCOMP_RISE
Comparator rising edge trigger
level
2.79
VCOMP_FALL
Comparator falling edge trigger
level
2.73
Hysteresis
tCOMP_IRQ
(1)
(2)
30
Transition time of Interrupt
output
V
60
80
mV
6
15
µs
All limits are ensured by design, test and/or statistical analysis. All electrical characteristics having room-temperature limits are tested
during production with TJ = 25°C. All hot and cold limits are ensured by correlating the electrical characteristics to process and
temperature variations and applying statistical process control.
Capacitors: Low-ESR Surface-Mount Ceramic Capacitors (MLCCs) are used in setting electrical characteristics.
11
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Typical Performance Characteristics
(All plots are representative typical plots) Vin=5.0V
Buck 2 Efficiency
100
90
90
80
80
70
70
Efficiency (%)
Efficiency (%)
Buck 1 Efficiency
100
60
50
40
30
60
50
40
30
VIN=3.7V
VIN=4.2V
VIN=5.0V
20
10
0
0.0
0.2
0.4
0.6
0.8
1.0
1.2
1.4
10
0
1.6
Load Current (A)
VIN=3.3V
VIN=4.2V
VIN=5.0V
20
0.0
0.1
0.2
0.3
Figure 2.
Buck 3 Efficiency
90
3.5
Output Voltage (V)
80
Efficiency (%)
70
60
50
40
30
3.0
Output Voltage (V)
5
0.9
1.0
C005
Buck 1
Buck 2
Buck 3
POK
2.0
1.5
0.5
0.0
Time (2ms/DIV)
C006
C001
Figure 4.
Figure 5.
POK at DEVSLP
DEVSLP Timing 5ms
Buck 1
Buck 2
Buck 3
POK
Voltage (1V/DIV)
6
0.8
2.5
0.0 0.2 0.4 0.6 0.8 1.0 1.2 1.4 1.6 1.8 2.0 2.2 2.4 2.6
Load Current (A)
0.7
1.0
VIN=3.3V
VIN=4.2V
VIN=5.0V
0
0.6
Startup
4.0
10
0.5
Figure 3.
100
20
0.4
Load Current (A)
C004
4
3
2
Buck 3
Buck 2
SLPEN
DEVSLP
1
0
Time (2ms/DIV)
Time (5ms/DIV)
C003
C002
Figure 6.
Figure 7.
12
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Typical Performance Characteristics (continued)
Voltage (1V/DIV)
DEVSLP Timing 10ms
Buck 1 - 0 to 750mA
Buck 3
Buck 2
SLPEN
DEVSLP
Time (5ms/DIV)
C004
Figure 8.
Figure 9.
Buck 1 - 750mA to 1.6A
Buck 2 - 0 to 500mA
Figure 10.
Figure 11.
Buck 2 - 500 to 1A
Buck 3 - 0 to 1.25A
Figure 12.
Figure 13.
13
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Typical Performance Characteristics (continued)
Buck 3 - 1.25 to 2.5A
Figure 14.
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APPLICATION INFORMATION
LM10524 is a highly efficient and integrated Power Management Unit for Systems-on-a-Chip (SoCs), ASICs, and
processors. It operates cooperatively and communicates with processors over an SPI interface with output
Voltage programmability.
The device incorporates three high-efficiency synchronous buck regulators that deliver three output voltages from
a single power source.
GND
GND
GND
SPI_CLK
SPI_DI
SPI_DO
SPI_CS
VIN_IO
The device also includes a SPI programmable Comparator Block that provides an interrupt output signal. The
device has a separate logic supply input.
SPI
VIN_B2
PowerUp_Mode
DEVSLP
SW_B2
CONTROL
LOGIC
BUCK 2
REGISTERS
DEVSLP_CTRL
DEVSLP_OVR1
GND_B2
FB_B2
DEVSLP_OVR2
EN
PWR_OK
SLEEP_EN
LM10524
VIN_B1
BUCK 1
GND_B1
EN
SEQUENCER
SW_B1
TSD
OVLO
UVLO
EN
FB_B1
VIN_B3
SW_B3
VCOMP
BUCK 3
COMPARATOR
GND_B3
FB_B3
IRQ
Figure 15. Internal Block Diagram of the LM10524 PMIC
SPI Data Interface
The device is programmable via 4-wire SPI Interface. The signals associated with this interface are CS, DI, DO
and CLK. Through this interface, the user can enable/disable the device, program the output voltages of the
individual Bucks and of course read the status of Flag registers.
By accessing the registers in the device through this interface, the user can get access and control the operation
of the buck controllers and program the reference voltage of the comparator in the device.
15
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Figure 16. SPI Interface Write
•
Data In (DI)
– 1 to 0 Write Command
– A4to A0 Register address to be written
– D7 to D0 Data to be written
•
Data Out (DO)
– All Os
Figure 17. SPI Interface Read
•
Data In (DI)
– 1 to 1 Read Command
– A4to A0 Register address to be read
– Don’t care after A0
•
Data Out (DO)
– D7 to D0 Data Read
16
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Registers Configurable Via The SPI Interface
Ad
dr
0x0
0
0x0
7
0x0
8
0x0
A
0x0
B
Reg Name
Buck 3
Voltage
Buck 1
Voltage
Buck 2
Voltage
Buck Control
Comparator
Control
Bit
R/W
Default
Description
7
—
-
6
R/W
0
Buck 3 Voltage Code[6]
5
R/W
0
Buck 3 Voltage Code[5]
4
R/W
1
Buck 3 Voltage Code[4]
3
R/W
1
Buck 3 Voltage Code[3]
2
R/W
1
Buck 3 Voltage Code[2]
1
R/W
1
Buck 3 Voltage Code[1]
0
R/W
0
Buck 3 Voltage Code[0]
7
—
-
Notes
Reset default:
0x1E (1.0V)
Range: 0.7V to 1.95V
Reset default:
6
—
-
5
R/W
1
Buck 1 Voltage Code[5]
0x23 (2.85V)
4
R/W
0
Buck 1 Voltage Code[4]
3
R/W
0
Buck 1 Voltage Code[3]
2
R/W
0
Buck 1 Voltage Code[2]
1
R/W
1
Buck 1 Voltage Code[1]
0
R/W
1
Buck 1 Voltage Code[0]
7
—
-
6
—
-
5
R/W
0
Buck 2 Voltage Code[5]
4
R/W
0
Buck 2 Voltage Code[4]
3
R/W
1
Buck 2 Voltage Code[3]
2
R/W
1
Buck 2 Voltage Code[2]
1
R/W
1
Buck 2 Voltage Code[1]
0
R/W
0
Buck 2 Voltage Code[0]
7
R
1
BK3EN
Reads Buck 3 enable status
6
—
-
5
—
-
4
R/W
(see notes)
BK1FPWM
Buck 1 forced PWM mode when high.
Default = 1 (LM10524), Default = 0
(LM10524-A).
3
R/W
1
BK2FPWM
Buck 2 forced PWM mode when high
2
R/W
1
BK3FPWM
Buck 3 forced PWM mode when high
1
R/W
1
BK1EN
Enables Buck 1 0-disabled, 1-enabled
0
R/W
1
BK2EN
Enables Buck 2 0-disabled, 1-enabled
7
R/W
0
Comp_hyst[0]
Doubles Comparator hysteresis
6
R/W
0
Comp_thres(5)
Programmable range of 2.0V to 4.0V, step
size = 31.75 mV
5
R/W
1
Comp_thres(4)
4
R/W
1
Comp_thres(3)
3
R/W
0
Comp_thres(2)
Comp_hyst=1 → min 80 mV hysteresis
2
R/W
0
Comp_thres(1)
Comp_hyst=0 → min 40 mV hysteresis
1
R/W
0
Comp_thres(0)
0
R/W
1
COMPEN
Range: 1.1V to 2.85V
Reset default:
0x0E (1.8V)
Range: 1.1V to 3.6V
Comparator Threshold reset default:
6h'18.
Comparator enable
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Ad
dr
0x0
C
0x0
D
Reg Name
Interrupt
Enable
Interrupt
Status
0x0
MISC Control
E
www.ti.com
Bit
R/W
Default
7
—
6
—
5
—
4
—
3
R/W
0
Buck 3 OK
2
R/W
0
Buck 2 OK
1
R/W
0
Buck 1 OK
0
R/W
1
Comparator
Interrupt comp event
7
—
6
—
5
—
4
R
3
R
Buck 3 OK
Buck 3 is greater than 90% of target
2
R
Buck 2 OK
Buck 2 is greater than 90% of target
1
R
Buck 1 OK
Buck 1 is greater than 90% of target
0
R
Comparator
Comparator output is high
7
—
6
—
5
—
4
—
3
—
2
—
1
—
0
R/W
Interrupt Polarity
Interrupt_polarity=0→Active low Interrupt
Interrupt_polarity=1→Active high Interrupt
0
Description
18
Notes
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SNVS986A – AUGUST 2013 – REVISED JANUARY 2014
ADDR 0x07& 0x08: Buck 1 and Buck 2 Voltage Code and VOUT Level Mapping
Voltage code
Voltage
Voltage code
Voltage
0x00
1.10
0x20
2.70
0x01
1.15
0x21
2.75
0x02
1.20
0x22
2.80
0x03
1.25
0x23
2.85
0x04
1.30
0x24
2.90
0x05
1.35
0x25
2.95
0x06
1.40
0x26
3.00
0x07
1.45
0x27
3.05
0x08
1.50
0x28
3.10
0x09
1.55
0x29
3.15
0x0A
1.60
0x2A
3.20
0x0B
1.65
0x2B
3.25
0x0C
1.70
0x2C
3.30
0x0D
1.75
0x2D
3.35
0x0E
1.80
0x2E
3.40
0x0F
1.85
0x2F
3.45
0x10
1.90
0x30
3.50
0x11
1.95
0x31
3.55
0x12
2.00
0x32
3.60
0x13
2.05
0x33
3.60
0x14
2.10
0x34
3.60
0x15
2.15
0x35
3.60
0x16
2.20
0x36
3.60
0x17
2.25
0x37
3.60
0x18
2.30
0x38
3.60
0x19
2.35
0x39
3.60
0x1A
2.40
0x3A
3.60
0x1B
2.45
0x3B
3.60
0x1C
2.50
0x3C
3.60
0x1D
2.55
0x3D
3.60
0x1E
2.60
0x3E
3.60
0x1F
2.65
0x3F
3.60
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ADDR 0x00 & 0x09: Buck 3 Voltage Code and VOUT Level Mapping
Voltage Code
Voltage
Voltage Code
Voltage
Voltage Code
Voltage
Voltage Code
Voltage
0x00
0.70
0x20
1.02
0x40
1.34
0x60
1.66
0x01
0.71
0x21
1.03
0x41
1.35
0x61
1.67
0x02
0.72
0x22
1.04
0x42
1.36
0x62
1.68
0x03
0.73
0x23
1.05
0x43
1.37
0x63
1.69
0x04
0.74
0x24
1.06
0x44
1.38
0x64
1.70
0x05
0.75
0x25
1.07
0x45
1.39
0x65
1.71
0x06
0.76
0x26
1.08
0x46
1.40
0x66
1.72
0x07
0.77
0x27
1.09
0x47
1.41
0x67
1.73
0x08
0.78
0x28
1.10
0x48
1.42
0x68
1.74
0x09
0.79
0x29
1.11
0x49
1.43
0x69
1.75
0x0A
0.80
0x2A
1.12
0x4A
1.44
0x6A
1.76
0x0B
0.81
0x2B
1.13
0x4B
1.45
0x6B
1.77
0x0C
0.82
0x2C
1.14
0x4C
1.46
0x6C
1.78
0x0D
0.83
0x2D
1.15
0x4D
1.47
0x6D
1.79
0x0E
0.84
0x2E
1.16
0x4E
1.48
0x6E
1.80
0x0F
0.85
0x2F
1.17
0x4F
1.49
0x6F
1.81
0x10
0.86
0x30
1.18
0x50
1.50
0x70
1.82
0x11
0.87
0x31
1.19
0x51
1.51
0x71
1.83
0x12
0.88
0x32
1.20
0x52
1.52
0x72
1.84
0x13
0.89
0x33
1.21
0x53
1.53
0x73
1.85
0x14
0.90
0x34
1.22
0x54
1.54
0x74
1.86
0x15
0.91
0x35
1.23
0x55
1.55
0x75
1.87
0x16
0.92
0x36
1.24
0x56
1.56
0x76
1.88
0x17
0.93
0x37
1.25
0x57
1.57
0x77
1.89
0x18
0.94
0x38
1.26
0x58
1.58
0x78
1.90
0x19
0.95
0x39
1.27
0x59
1.59
0x79
1.91
0x1A
0.96
0x3A
1.28
0x5A
1.60
0x7A
1.92
0x1B
0.97
0x3B
1.29
0x5B
1.61
0x7B
1.93
0x1C
0.98
0x3C
1.30
0x5C
1.62
0x7C
1.94
0x1D
0.99
0x3D
1.31
0x5D
1.63
0x7D
1.95
0x1E
1.00
0x3E
1.32
0x5E
1.64
0x1F
1.01
0x3F
1.33
0x5F
1.65
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ADDR 0x0B: Comparator Threshold Mapping
Voltage code
Voltage
Voltage code
Voltage
6h'00
2.000
6h'20
3.016
6h'01
2.032
6h'21
3.048
6h'02
2.064
6h'22
3.080
6h'03
2.095
6h'23
3.111
6h'04
2.127
6h'24
3.143
6h'05
2.159
6h'25
3.175
6h'06
2.191
6h'26
3.207
6h'07
2.222
6h'27
3.238
6h'08
2.254
6h'28
3.270
6h'09
2.286
6h'29
3.302
6h'0A
2.318
6h'2A
3.334
6h'0B
2.349
6h'2B
3.365
6h'0C
2.381
6h'2C
3.397
6h'0D
2.413
6h'2D
3.429
6h'0E
2.445
6h'2E
3.461
6h'0F
2.476
6h'2F
3.492
6h'10
2.508
6h'30
3.524
6h'11
2.540
6h'31
3.556
6h'12
2.572
6h'32
3.588
6h'13
2.603
6h'33
3.619
6h'14
2.635
6h'34
3.651
6h'15
2.667
6h'35
3.683
6h'16
2.699
6h'36
3.715
6h'17
2.730
6h'37
3.746
6h'18
2.762
6h'38
3.778
6h'19
2.794
6h'39
3.810
6h'1A
2.826
6h'3A
3.842
6h'1B
2.857
6h'3B
3.873
6h'1C
2.889
6h'3C
3.905
6h'1D
2.921
6h'3D
3.937
6h'1E
2.953
6h'3E
3.969
6h'1F
2.984
6h'3F
4.000
Buck Regulators Operation
A buck converter contains a control block, a switching PFET connected between input and output, a synchronous
rectifying NFET connected between the output and ground and a feedback path. The figure below shows the
block diagram of each of the three buck regulators integrated in the device.
G
FB
CONTROL
G
CIN
P
SW
D
D
N
S
L
COUT
PGND
VOUT
S
VIN
PVIN
U1
LM10524
GND
Figure 18. Buck Functional Diagram
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During the first portion of each switching cycle, the control block turns on the internal PFET switch. This allows
current to flow from the input through the inductor to the output filter capacitor and load. The inductor limits the
current to a ramp with a slope of (VVIN_Bx –VOUT)/L by storing energy in a magnetic field. During the second
portion of each cycle, the control block turns the PFET switch off, blocking current flow from the input, and then
turns the NFET synchronous rectifier on. The inductor draws current from ground through the NFET to the output
filter capacitor and load, which ramps the inductor current down with a slope of (–VOUT)/L.
The output filter stores charge when the inductor current is high, and releases it when low, smoothing the voltage
across the load. The output voltage is regulated by modulating the PFET switch on time to control the average
current sent to the load. The effect is identical to sending a duty-cycle modulated rectangular wave formed by the
switch and synchronous rectifier at the SW pin to a low-pass filter formed by the inductor and output filter
capacitor. The output voltage is equal to the average voltage at the SW pin.
Buck Regulators Description
The LM10524 incorporates three high efficiency synchronous switching buck regulators that deliver various
voltages from a single DC input voltage. They include many advanced features to achieve excellent voltage
regulation, high efficiency and fast transient response time. The bucks feature voltage mode architecture with
synchronous rectification.
Each of the switching regulators is specially designed for high efficiency operation throughout the load range.
With a 2MHz typical switching frequency, the external L-C filter can be small and still provide very low output
voltage ripple. The bucks are internally compensated to be stable with the recommended external inductors and
capacitors as detailed in the application diagram. Synchronous rectification yields high efficiency for low voltage
and high output currents.
All bucks can operate up to a 100% duty cycle allowing for the lowest possible input voltage that still maintains
the regulation of the output. The lowest input to output dropout voltage is achieved by keeping the PMOS switch
on.
Additional features include soft-start, under-voltage lock-out, and current and thermal overload protection. To
reduce the input current ripple, the device employs a control circuit that operates the three bucks at 120° phase.
These bucks are nearly identical in performance and mode of operation. They operate in FPWM (forced PWM) or
automatic mode (PWM/PFM).
PWM Operation
During PWM operation the converter operates as a voltage-mode controller with input voltage feed forward. This
allows the converter to achieve excellent load and line regulation. The DC gain of the power stage is proportional
to the input voltage. To eliminate this dependence, a feed forward voltage inversely proportional to the input
voltage is introduced.
In Forced PWM Mode the bucks always operate in PWM mode regardless of the output current.
In Automatic Mode, if the output current is less than 70 mA (typ.), the bucks automatically transition into PFM
(Pulse Frequency Modulation) operation to reduce the current consumption. At higher than 100 mA (typ.) they
operate in PWM mode. This increases the efficiency at lower output currents. The 30 mA (typ.) hysteresis is
designed in for stable Mode transition.
While in PWM mode, the output voltage is regulated by switching at a constant frequency and then modulating
the energy per cycle to control power to the load. At the beginning of each clock cycle the PFET switch is turned
on, and the inductor current ramps up until the comparator trips and the control logic turns off the switch. The
current limit comparator can also turn off the switch in case the current limit of the PFET is exceeded. In this
case the NFET switch is turned on and the inductor current ramps down. The next cycle is initiated by the clock
turning off the NFET and turning on the PFET.
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PWM Mode at
Moderate to
Heavy Loads
Vout
PFM Mode at Light Load
Load current
increases, draws
Vout towards Low2
PFM Threshold
High PFM
Threshold
~1.016*Vout
Low1 PFM
Threshold
~1.008*Vout
PFET on
until
LPFM
limit
reached
NFET on
drains
inductor
current
until
I inductor=0
High PFM
Voltage
Threshold
reached,
go into
Idle mode
Low PFM
Threshold,
turn on
PFET
Load
current
increases
Low2 PFM
Threshold,
switch back to
PWM mode
Low2 PFM
Threshold
Vout
Time
Figure 19. PFM vs PWM Operation
PFM Operation [BUCK 1, 2 & 3]
At very light loads, Buck 1, 2 and Buck 3 enter PFM mode and operate with reduced switching frequency and
supply current to maintain high efficiency.
Buck 1, 2 and 3 will automatically transition into PFM mode when either of two conditions occurs for a duration of
32 or more clock cycles:
1. The inductor current becomes discontinuous, or
2. The peak PMOS switch current drops below the IMODE level.
During PFM operation, the converter positions the output voltage slightly higher than the nominal output voltage
during PWM operation, allowing additional headroom for voltage drop during a load transient from light to heavy
load. The PFM comparators sense the output voltage via the feedback pin and control the switching of the output
FETs such that the output voltage ramps between 0.8% and 1.6% (typical) above the nominal PWM output
voltage. If the output voltage is below the ‘high’ PFM comparator threshold, the PMOS power switch is turned on.
It remains on until the output voltage exceeds the ‘high’ PFM threshold or the peak current exceeds the Ipfm level
set for PFM mode.
Once the PMOS power switch is turned off, the NMOS power switch is turned on until the inductor current ramps
to zero. When the NMOS zero-current condition is detected, the NMOS power switch is turned off. If the output
voltage is below the ‘high’ PFM comparator threshold (see Figure 19), the PMOS switch is again turned on and
the cycle is repeated until the output reaches the desired level. Once the output reaches the ‘high’ PFM
threshold, the NMOS switch is turned on briefly to ramp the inductor current to zero and then both output
switches are turned off and the part enters an extremely low power mode. Quiescent supply current during this
‘idle’ mode is less than 100uA, which allows the part to achieve high efficiencies under extremely light load
conditions. When the output drops below the ‘low’ PFM threshold, the cycle repeats to restore the output voltage
to ~1.6% above the nominal PWM output voltage.
If the load current should increase during PFM mode causing the output voltage to fall below the ‘low2’ PFM
threshold, the part will automatically transition into fixed-frequency PWM mode.
Soft Start
Each of the buck converters has an internal soft-start circuit that limits the in-rush current during start-up. This
allows the converters to gradually reach the steady state operating point, thus reducing start-up stresses and
surges. During start-up, the switch current limit is increased in steps.
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For Buck 1, 2 and 3 the soft start is implemented by increasing the switch current limit in steps that are gradually
goes higher. The start-up time depends on the output capacitor size, load current and output voltage. Typical
startup time with the recommended output capacitor of 10uF is 0.1-0.5ms. It is expected that in the final
application the load current condition will be more likely in the lower load current range during the start up.
Current Limiting
A current limit feature protects the device and any external components during overload conditions. In PWM
mode the current limiting is implemented by using an internal comparator that trips at current levels according to
the buck capability. If the output is shorted to ground the device enters a timed current limit mode where the
NFET is turned on for a longer duration until the inductor current falls below a low threshold, ensuring inductor
current has more time to decay, thereby preventing runaway.
Internal Synchronous Rectification
While in PWM mode, the bucks use an internal NFET as a synchronous rectifier to reduce the rectifier forward
voltage drop and the associated power loss. Synchronous rectification provides a significant improvement in
efficiency whenever the output voltage is relatively low compared to the voltage drop across an ordinary rectifier
diode.
Bypass-FET Operation on Buck 1
This is a factory programmable option, this is disabled on the LM10524 and the LM10524-A.
There is an additional bypass FET used on Buck 1. The FET is connected in parallel to High Side FET and
inductor. The bypass threshold will be 3.1V with an option of 3.5V (set by OTP). With standard setting if buck 1
input voltage is greater than 3.1V the bypass function is disabled. The determination of whether or not the Buck 1
is in bypass mode or standard switching regulation is constantly monitored while the regulator is enabled. If at
any time the input voltage goes above 3.1V while in by-pass mode, the regulator will transition to normal
operation.
When the bypass mode is enabled, the output voltage of the buck that is in bypass mode is not regulated, but
instead, the output voltage follows the input voltage minus the voltage drop seen across the FET and DCR of the
inductor. The voltage drop is a direct result of the current flowing across those resistive elements. When Buck 1
transitions into bypass mode, there is an extra FET used in parallel along with the high side FET for transmission
of the current to the load. This added FET will help reduce the resistance seen by the load and decrease the
voltage drop.
Equivalent Circuit of Bypass Operation of Buck 1
High Side FET
VIN_B1
DCR
100m
Max.
Ideal Inductor,
no resistance
VOUT Buck 1
SW_B1
Model of Inductor
FB_B1
Load
Resistance
Load
Capacitance
Bypass FET
Figure 20. Bypass Operation - Equivalent Circuits
Low Dropout Operation
The device can operate nearly at 100% duty cycle (no switching; PMOS switch completely on) for low drop out
support. In this way the output voltage will be controlled down to the lowest possible input voltage. When the
device operates near 100% duty cycle, output voltage ripple is approximately 25 mV.
The minimum input voltage needed to support the output voltage is:
VIN_MIN=VOUT+ILOAD*(RDSON_PFET+RIND)
Where:
•
ILOAD = Load Current
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•
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RDSON_PFET = Drain to source resistance of PFET (high side)
RIND = Inductor resistance
(1)
Device Operating Modes
Startup Sequence
The startup mode of the LM10524 will depend on the input voltage. Once VIN reaches the UVLO threshold, there
is a 15 msec delay before the LM10524 determines how to set up the buck regulators. If bypass mode is enabled
and if VIN is below 3.2V, then Buck 1 will be in bypass mode. See Bypass-FET Operation on Buck 1 for
functionality description. If the VIN voltage is greater than 3.2V buck 1 will start up as the standard regulators.
The 3 buck regulators are staggered during startup to avoid large inrush currents. There is a fixed delay of 2
msec between the startup of each regulator.
The Startup Sequence will be:
1. 15 msec (±30%) delay after VIN UVLO threshold
2. 2 ms delay
3. Buck 3 Startup
4. 2 ms delay
5. Buck 1 Startup
6. 2 ms delay
7. Buck 2 Startup
6. 05V
5.7V
3.1V
2.9V
VCOMP
2.6V
15ms
VIN
2ms
2ms
Buck3
2ms
If Bypass
is Enabled
2ms
Buck1
2ms
2ms
Buck2
2ms
2ms
PWR_OK
IRQ
STARTUP
Normal Operation
OVLO
STARTUP
Bypass
UVLO
IRQ UVLO
Figure 21. Normal Operating Modes
Power-On
The device is always enabled, unless outside of operating voltage range. There is no LM10524 Enable Pin. Once
VIN reaches a minimum required input Voltage, the power-up sequence will be started automatically and the
startup sequence will be initiated. Once the device is started, the output voltage of the Bucks 1 and 2 can be
individually disabled by accessing their corresponding BKEN register bits (BUCK CONTROL).
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Sleep Function
The Device can be put into Sleep mode where all the outputs and the internal oscillator are switched off. Sleep
mode is initiated by the DevSLP pin going high and the function is gated by the state of device pins
DevSLP_OVR1, DevSLP_OVR2, and PowerUp_Enable. DevSLP_CTRL and SLEEP_EN pins are used to
indicate the status of the device while DevSLP pin is high.
Device Power Up
During the device power up there is a 150ms period where all outputs will be low or tri-state. Following this the
PowerUp_Mode output will be high and SLEEP_EN output will be low. The DEVSLP_CTRL output will mirror the
state of the DEVSLP input. This initialization phase is complete when the PowerUp_Mode pin is externally pulled
low and the device latches this low state on the pin.
Normal Operation
When Sleep mode is initiated by the DEVSLP pin being pulled high, this is mirrored to the DEVSLP_CTRL pin.
The conditions for entry into Sleep mode are checked, DEVSLP_OVR1, DEVSLP_OVR2, and PowerUp_Mode
pins must be low. If these conditions are met the Ouput shutdown is started and the DEVSLP_CTRL pin is driven
low. The SLEEP_EN pin is driven high to indicate that Sleep mode is active. SLEEP_EN will remain high until all
outputs have discharged to zero and DEVSLP goes low. In the case where the DEVSLP input goes low prior to
full discharge, SLEEP_EN will remain high until all outputs have discharged. If any of the gating pins
DEVSLP_OVR1, DEVSLP_OVR2, and PowerUp_Mode go high while in sleep mode SLEEP_EN will go low and
DEVSLP_CTRL will go to the same state as DEVSLP pin.
19.2.3 DEVSLP Timing
Initialization phase:
VIN
OUTPUTS
FROM PMIC
t150mst
DEVSLP
DEVSLP_CTRL
DEVSLP_OVR1
DEVSLP_OVR2
POWERUP_MODE
Sleep mode is available after this edge
SLEEP_EN
Start up period.
All signals low or
tri-state.
Initialisation period for DevSLP circuit
Figure 22. Initialization
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After device power up the regulated outputs are on and at their specified outputs voltages indicated by the
‘Outputs from PMIC’ trace above. All DEVSLP signals are low or tri-state for a period of 150ms. Following this
150ms period the device will hold SLEEP_EN low and will allow the POWERUP_MODE pin to go high via a 1KΩ
pullup resistor referenced to VIN supply. The DEVSLP function is ready when the POWERUP_MODE pin is
pulled low externally, This negative edge on the POWERUP_MODE pin triggers the device to pulldown the
POWERUP_MODE pin and this output remains low until a device reset. During this Initialization phase the
DEVSLP_CTRL output mirrors the input at DEVSLP. The two signals DEVSLP_OVR1/2 are ignored by the
device during this phase.
Normal Operation, DEVSLP high period > Outputs discharge time:
VIN
t25mst
OUTPUTS
FROM PMIC
150ms
DEVSLP
DEVSLP_CTRL
2µs
DEVSLP_OVR1
DEVSLP_OVR2
150ms
POWERUP_MODE
SLEEP_EN
Figure 23. DEVSLP, Period Greater than Output Discharge Time
In normal operation when DEVSLP goes high, DEVSLP_CNTL will go high. The device checks the status of
DEVSLP_OVR1 and DEVSLP_OVR2 as well as POWERUP_MODE to ensure they are low to allow entry into
SLEEP mode. If these conditions are met then the device will power down all outputs in their time sequence and
the DEVSLP_CTRL pin is forced low. SLEEP_EN is forced high. Following the outputs discharging to zero
DEVSLP goes low, SLEEP_EN is driven low and the regulated outputs switch on in their determined time
sequence.
Normal Operation, DEVSLP high period < Outputs discharge time
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VIN
t14mst
OUTPUTS
FROM PMIC
150ms
DEVSLP
t10mst
DEVSLP_CTRL
2µs
DEVSLP_OVR1
DEVSLP_OVR2
150ms
POWERUP_MODE
*4ms + 10ms min sleep slot time
SLEEP_EN
* Time set by OTP
Figure 24. DEVSLP. Period less than Output Discharge Time
As above; in normal operation when DEVSLP goes high DEVSLP_CNTL will go high. The device checks the
status of DEVSLP_OVR1 and DEVSLP_OVR2 as well as POWERUP_MODE to ensure they are low to allow
entry into SLEEP mode. If these conditions are met then the device will power down all outputs in their time
sequence (4ms) and the DEVSLP_CTRL pin is forced low. SLEEP_EN is forced high. In this case DEVSLP goes
high prior to full output discharge to zero. SLEEP_EN will be forced low after a set time, (programmable) with
default set to10ms (+4ms) to ensure the device outputs discharge fully. This timing is important to ensure proper
discharge of the output capacitance (up to 100µF in a 7.5ms period. The device outputs will also be switched on
after this time period. To ensure all buck outputs are discharged a minimum sleep time exists, this time is
configured to 12ms (programmable set by OTP).In the case where DEVSLP is active for, 140°C). The
thermal shutdown (TSD) will force the device into the reset state. In reset, all circuitry is disabled. To prevent
unstable operation, the TSD has a hysteresis window of about 20°C. Once the temperature has decreased below
the TSD hysteresis, the device will initiate a powerup sequence and then enter the active state. In the active
state, the part will start up as if for the first time, all registers will be in their default state.
Comparator
The comparator on the LM10524 takes its inputs from the VCOMP pin and an internal threshold level which is
programmed by the user. The threshold level is programmable between 2.0 and 4.0V with a step of 31 mV and a
default comp code of 6h'18. The output of the comparator is the Interrupt pin. Its polarity can be changed using
Register 0x0E bit 0. If Interrupt polarity = 0 → Active low (default) is selected, then the output is low if VCOMP
value is greater than the threshold level. The output is high if the VCOMP value is less than the threshold level. If
Interrupt polarity = 1 → Active high is selected then the output is high if VCOMP value is greater than the threshold
level. The output is low if the VCOMP value is less than the threshold level. There is some hysteresis when VCOMP
transitions from high to low, typically 60 mV. There is a control bit in register 0x0B, comparator control, that can
double the hysteresis value.
Figure 26. Comparator Thresholds
Thermal Shutdown (TSD)
The temperature of the silicon die is monitored for an over-temperature condition, for which the operation of the
device cannot be ensured. The part will automatically be disabled if the temperature is too high. The thermal
shutdown (TSD) will force the device into the reset state. In reset, all circuitry is disabled. To prevent unstable
operation, the TSD has a hysteresis window of about 20°C. Once the temperature has decreased below the TSD
hysteresis, the device will initiate a power-up sequence and then enter the active state. In the active state, the
part will start up as if for the first time, all registers will be in their default state.
External Components Selection
All three switchers require an input capacitor and an output inductor-capacitor filter. These components are
critical to the performance of the device. All three switchers are internally compensated and do not require
external components to achieve stable operation. The output voltages of the bucks can be programmed through
the SPI pins.
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Output Inductors & Capacitors Selection
There are several design considerations related to the selection of output inductors and capacitors:
• Load transient response
• Stability
• Efficiency
• Output ripple voltage
• Over current ruggedness
The device has been optimized for use with nominal LC values as shown in the Typical Application Circuit.
Inductor Selection
The recommended inductor values are shown in Typical Application Diagram. It is important to ensure the
inductor core does not saturate during any foreseeable operational situation. The inductor should be rated to
handle the peak load current plus the ripple current.
Care should be taken when reviewing the different saturation current ratings that are specified by different
manufacturers. Saturation current ratings are typically specified at 25°C, so ratings at maximum ambient
temperature of the application should be requested from the manufacturer.
IL(MAX) ILOAD(MAX) 'IRIPPLE
ILOAD(MAX)
| ILOAD(MAX)
D
VOUT
, FS
VIN
D u (VIN VOUT )
2 u L u FS
D u (VIN VOUT )
(A typ.),
2 u 2.2 u 2.0
2 MHz, L
2.2 PH
(2)
There are two methods to choose the inductor saturation current rating:
Recommended Method for Inductor Selection:
The best way to ensure the inductor does not saturate is to choose an inductor that has saturation current rating
greater than the maximum device current limit, as specified in the Electrical Characteristics tables. In this case
the device will prevent inductor saturation by going into current limit before the saturation level is reached.
Alternate Method for Inductor Selection:
If the recommended approach cannot be used care must be taken to ensure that the saturation current is greater
than the peak inductor current:
ISAT ! ILPEAK
ILPEAK
IRIPPLE
D
IRIPPLE
2
D u (VIN VOUT )
L u FS
IOUTMAX
VOUT
VIN u EFF
Where:
•
•
•
•
•
ISAT: Inductor saturation current at operating temperature
ILPEAK: Peak inductor current during worst case conditions
IOUTMAX: Maximum average inductor current
IRIPPLE: Peak-to-Peak inductor current
VOUT: Output voltage
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•
•
•
•
•
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VIN: Input voltage
L: Inductor value in Henries at IOUTMAX
F: Switching frequency, Hertz
D: Estimated duty factor
EFF: Estimated power supply efficiency
(3)
ISAT may not be exceeded during any operation, including transients, startup, high temperature, worst-case
conditions, etc.
Suggested Inductors and Their Suppliers
The designer should choose the inductors that best match the system requirements. A very wide range of
inductors are available as regarding physical size, height, maximum current (thermally limited, and inductance
loss limited), series resistance, maximum operating frequency, losses, etc. In general, smaller physical size
inductors will have higher series resistance (DCR) and implicitly lower overall efficiency is achieved. Very lowprofile inductors may have even higher series resistance. The designer should try to find the best compromise
between system performance and cost.
Value
Manufacturer
Part Number
DCR
Current
Package
1.0 µH
Murata
LQH44PN1R0NP0
30 mΩ
2.95A
1616
1.0 µH
Murata
LQH32PN1R0NNC
45mΩ
2.5A
3225(1210)
1.0 µH
Coilcraft
XFL3012-102MEC
35 mΩ
2.5A
3012
1.0 µH
Coilcraft
LPS4012-102NL
70mΩ
3.0A
4012
2.2 µH
Coilcraft
XFL3012-222MEC
81 mΩ
1.6A
3012
2.2 µH
Murata
LQH55PN2R2NR0L
31 mΩ
2.5A
2220
Output and Input Capacitors Characteristics
Special attention should be paid when selecting these components. As shown in the following figure, the DC bias
of these capacitors can result in a capacitance value that falls below the minimum value given in the
recommended capacitor specifications table. Note that the graph shows the capacitance out of spec for the 0402
case size capacitor at higher bias voltages. It is therefore recommended that the capacitor manufacturers’
specifications for the nominal value capacitor are consulted for all conditions, as some capacitor sizes (e.g.0402)
may not be suitable in the actual application.
Figure 27. Typical Variation in Capacitance vs.
DC Bias
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The ceramic capacitor’s capacitance can vary with temperature. The capacitor type X7R, which operates over a
temperature range of −55°C to +125°C, will only vary the capacitance to within ±15%. The capacitor type X5R
has a similar tolerance over a reduced temperature range of −55°C to +85°C. Many large value ceramic
capacitors, larger than 1µF are manufactured with Z5U or Y5V temperature characteristics. Their capacitance
can drop by more than 50% as the temperature varies from 25°C to 85°C. Therefore X7R is recommended over
Z5U and Y5V in applications where the ambient temperature will change significantly above or below 25°C.
Tantalum capacitors are less desirable than ceramic for use as output capacitors because they are more
expensive when comparing equivalent capacitance and voltage ratings in the 0.47µF to 44µF range. Another
important consideration is that tantalum capacitors have higher ESR values than equivalent size ceramics. This
means that while it may be possible to find a tantalum capacitor with an ESR value within the stable range, it
would have to be larger in capacitance (which means bigger and more costly) than a ceramic capacitor with the
same ESR value. It should also be noted that the ESR of a typical tantalum will increase about 2:1 as the
temperature goes from 25°C down to −30°C, so some guard band must be allowed.
Output Capacitor Selection
The output capacitor of a switching converter absorbs the AC ripple current from the inductor and provides the
initial response to a load transient. The ripple voltage at the output of the converter is the product of the ripple
current flowing through the output capacitor and the impedance of the capacitor. The impedance of the capacitor
can be dominated by capacitive, resistive, or inductive elements within the capacitor, depending on the frequency
of the ripple current. Ceramic capacitors have very low ESR and remain capacitive up to high frequencies. Their
inductive component can usually be neglected at the frequency ranges at which the switcher operates.
Figure 28. Output Capacitor Equivalent Circuit
The output-filter capacitor smooths out the current flow from the inductor to the load and helps maintain a steady
output voltage during transient load changes. It also reduces output voltage ripple. These capacitors must be
selected with sufficient capacitance and low enough ESR to perform these functions.
Note that the output voltage ripple increases with the inductor current ripple and the Equivalent Series
Resistance of the output capacitor (ESRCOUT). Also note that the actual value of the capacitor’s ESRCOUT is
frequency and temperature dependent, as specified by its manufacturer. The ESR should be calculated at the
applicable switching frequency and ambient temperature.
VOUT RIPPLEPP
'IRIPPLE
where 'IRIPPLE
8 u FS u COUT
D u (VIN VOUT )
and D
2 u L u FS
VOUT
VIN
(4)
Output ripple can be estimated from the vector sum of the reactive (capacitance) voltage component and the real
(ESR) voltage component of the output capacitor where:
VOUT RIPPLEPP
V 2ROUT V 2COUT
(5)
where:
VROUT
IRIPPLE u ESRCOUT and VCOUT
IRIPPLE
8 u FS u COUT
Where:
•
•
•
VOUT-RIPPLE-PP: estimated output ripple,
VROUT: estimated real output ripple,
VCOUT: estimated reactive output ripple.
(6)
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The device is designed to be used with ceramic capacitors on the outputs of the buck regulators. The
recommended dielectric type of these capacitors is X5R, X7R, or of comparable material to maintain proper
tolerances over voltage and temperature. The recommended value for the output capacitors is 22μF, 6.3V with
an ESR of 2mΩ or less. The output capacitors need to be mounted as close as possible to the output/ground
pins of the device.
Model
Vendor Type
Vendor
Voltage Rating
Case Size
GRM155B03J225KE95
Ceramic, X5R
Murata
6.3V
603
GRM155R60J475ME47
Ceramic, X5R
Murata
6.3V
603
GRM188B03J226MEA0
Ceramic, X5R
Murata
6.3V
603
GRM21BB30J476ME15
Ceramic, X5R
Murata
6.3V
805
Input Capacitor Selection
There are 3 buck regulators in the LM10524 device. Each of these buck regulators has its own input capacitor
which should be located as close as possible to their corresponding SWx_VIN and SWx_GND pins, where x
designates Buck 1, 2 or 3. The 3 buck regulators operate at 120° out of phase, which means that they switch on
at equally spaced intervals, in order to reduce the input power rail ripple. It is recommended to connect all the
supply/ground pins of the buck regulators, SWx_VIN to two solid internal planes located under the device. In this
way, the 3 input capacitors work together and further reduce the input current ripple. A larger tantalum capacitor
can also be located in the proximity of the device.
The input capacitor supplies the AC switching current drawn from the switching action of the internal power
FETs. The in- put current of a buck converter is discontinuous, so the ripple current supplied by the input
capacitor is large. The input capacitor must be rated to handle both the RMS current and the dissipated power.
The input capacitor must be rated to handle this current:
IRMS _ CIN
IOUT
VOUT (VIN VOUT )
VIN
(7)
The power dissipated in the input capacitor is given by:
PD _ CIN
I2RMS _ CIN u RESR _ CIN
(8)
The device is designed to be used with ceramic capacitors on the inputs of the buck regulators. The
recommended dielectric type of these capacitors is X5R, X7R, or of comparable material to maintain proper
tolerances over voltage and temperature. The minimum recommended value for the input capacitor is 10 µF with
an ESR of 10mΩ or less. The input capacitors need to be mounted as close as possible to the power/ground
input pins of the device.
The input power source supplies the average current continuously. During the PFET switch on-time, however,
the demanded di/dt is higher than can be typically supplied by the input power source. This delta is supplied by
the input capacitor.
A simplified “worst case” assumption is that all of the PFET current is supplied by the input capacitor. This will
result in conservative estimates of input ripple voltage and capacitor RMS current.
Input ripple voltage is estimated as follows:
VPPIN
IOUT u D
IOUT u ESRCIN
CIN u FS
where:
•
•
•
•
VPPIN: estimated peak-to-peak input ripple voltage,
IOUT: output Current
CIN: input capacitor value
ESRCIN: input capacitor ESR.
(9)
This capacitor is exposed to significant RMS current, so it is important to select a capacitor with an adequate
RMS current rating. Capacitor RMS current estimated as follows:
34
Copyright © 2013–2014, Texas Instruments Incorporated
Product Folder Links: LM10524
LM10524
www.ti.com
SNVS986A – AUGUST 2013 – REVISED JANUARY 2014
IRMSCIN
•
§
I2
D u ¨ I2OUT RIPPLE
¨
12
©
·
¸
¸
¹
IRMSCIN: estimated input capacitor RMS current.
(10)
PCB Layout Considerations
PC board layout is an important part of DC-DC converter design. Poor board layout can disrupt the performance
of a DC- DC converter and surrounding circuitry by contributing to EMI, ground bounce, and resistive voltage loss
in the traces. These can send erroneous signals to the DC-DC converter resulting in poor regulation or instability.
Good layout can be implemented by following a few simple design rules.
LOOP 1
VIN
CIN
P S
G
D
N
D
G
SW Vin
CONTROL
LM10524
LOOP 2
L
S
COUT
PGND
Figure 29. Buck Schematic Showing Layout Sensitive Nodes
1. Minimize area of switched current loops. In a buck regulator there are two loops where currents are switched
rapidly. The first loop starts from the CIN input capacitor, to the regulator Vin pin, through to PGND and back
to the CIN input capacitor. The second loop starts from the output capacitor ground, to the regulator PGND
pins, to the inductor and then out to COUT and the load (see Figure 29). To minimize both loop areas the
input capacitor should be placed as close as possible to the PVIN pin. Grounding for both the input and
output capacitors should consist of a small localized top side plane that connects to PGND. The inductor
should be placed as close as possible to the SW pin and output capacitor.
2. Minimize the copper area of the switch node. The SW pins should be directly connected with a trace that
runs on top side directly to the inductor. To minimize IR losses this trace should be as short as possible and
with a sufficient width. However, a trace that is wider than 100 mils will increase the copper area and cause
too much capacitive loading on the SW pin. The inductors should be placed as close as possible to the SW
pins to further minimize the copper area of the switch node.
3. Have a single point ground for all device analog grounds. The ground connections for the feedback
components should be connected together then routed to the GND pin of the device. This prevents any
switched or load currents from flowing in the analog ground plane. If not properly handled, poor grounding
can result in degraded load regulation or erratic switching behavior.
4. Minimize trace length to the FB pin. The feedback trace should be routed away from the SW pin and inductor
to avoid contaminating the feedback signal with switch noise.
5. Make input and output bus connections as wide as possible. This reduces any voltage drops on the input or
output of the converter and can improve efficiency. If voltage accuracy at the load is important make sure
feedback voltage sense is made at the load. Doing so will correct for voltage drops at the load and provide
the best output accuracy.
PCB Layout Thermal Dissipation for Micro SMD Package
1. Position ground layer as close as possible to micro SMD package. Second PCB layer is usually good option.
2. Draw power traces as wide as possible. Bumps which carry high currents should be connected to wide
traces. This helps the silicon to cool down.
35
Copyright © 2013–2014, Texas Instruments Incorporated
Product Folder Links: LM10524
LM10524
SNVS986A – AUGUST 2013 – REVISED JANUARY 2014
www.ti.com
REVISION HISTORY
Changes from Original (August 2013) to Revision A
•
Page
Added Device Information Table .......................................................................................................................................... 6
36
Copyright © 2013–2014, Texas Instruments Incorporated
Product Folder Links: LM10524
PACKAGE OPTION ADDENDUM
www.ti.com
10-Dec-2020
PACKAGING INFORMATION
Orderable Device
Status
(1)
Package Type Package Pins Package
Drawing
Qty
Eco Plan
(2)
Lead finish/
Ball material
MSL Peak Temp
Op Temp (°C)
Device Marking
(3)
(4/5)
(6)
LM10524TME-A/NOPB
NRND
DSBGA
YFR
46
250
RoHS & Green
SNAGCU
Level-1-260C-UNLIM
0 to 0
V089
LM10524TME/NOPB
ACTIVE
DSBGA
YFR
46
250
RoHS & Green
SNAGCU
Level-1-260C-UNLIM
-30 to 85
V088
LM10524TMX-A/NOPB
ACTIVE
DSBGA
YFR
46
1000
RoHS & Green
SNAGCU
Level-1-260C-UNLIM
-30 to 85
V089
LM10524TMX/NOPB
NRND
DSBGA
YFR
46
1000
RoHS & Green
SNAGCU
Level-1-260C-UNLIM
0 to 0
V088
(1)
The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2)
RoHS: TI defines "RoHS" to mean semiconductor products that are compliant with the current EU RoHS requirements for all 10 RoHS substances, including the requirement that RoHS substance
do not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, "RoHS" products are suitable for use in specified lead-free processes. TI may
reference these types of products as "Pb-Free".
RoHS Exempt: TI defines "RoHS Exempt" to mean products that contain lead but are compliant with EU RoHS pursuant to a specific EU RoHS exemption.
Green: TI defines "Green" to mean the content of Chlorine (Cl) and Bromine (Br) based flame retardants meet JS709B low halogen requirements of
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