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LM5010MHX/NOPB

LM5010MHX/NOPB

  • 厂商:

    BURR-BROWN(德州仪器)

  • 封装:

    HTSSOP14_5X4.4MM_EP

  • 描述:

    NO降压型-40℃~+125℃@(TJ)1降压可调2.5V~70V 1A 8V~75V HTSSOP14_5X4.4MM_EP DC-DC转换器ROHS

  • 数据手册
  • 价格&库存
LM5010MHX/NOPB 数据手册
Sample & Buy Product Folder Technical Documents Support & Community Tools & Software LM5010 SNVS307G – SEPTEMBER 2004 – REVISED APRIL 2016 LM5010 High-Voltage 1-A Step-Down Switching Regulator 1 Features 3 Description • • • • • • • • The LM5010 step-down switching regulator features all the functions needed to implement a low-cost, efficient, buck bias regulator capable of supplying in excess of 1-A load current. This high-voltage regulator contains an N-Channel Buck Switch, and is available in thermally enhanced 10-pin WSON and 14-pin HTSSOP packages. The hysteretic regulation scheme requires no loop compensation, resulting in fast load transient response, and simplifies circuit implementation. The operating frequency remains constant with line and load variations due to the inverse relationship between the input voltage and the ON-time. The valley current limit detection is set at 1.25 A. Additional features include: VCC undervoltage lockout, thermal shutdown, gate drive undervoltage lockout, and maximum duty cycle limiter. 1 • • • • • Input Voltage Range: 8 V to 75 V Valley Current Limit At 1.25 A Switching Frequency Can Exceed 1 MHz Integrated N-Channel Buck Switch Integrated Start-Up Regulator No Loop Compensation Required Ultra-Fast Transient Response Operating Frequency Remains Constant With Load and Line Variations Maximum Duty Cycle Limited During Start-Up Adjustable Output Voltage Precision 2.5-V Feedback Reference Thermal Shutdown Exposed Thermal Pad for Improved Heat Dissipation Device Information(1) PART NUMBER 2 Applications • • • • High Efficiency Point-of-Load (POL) Regulator Non-Isolated Telecommunications Buck Regulator Secondary High Voltage Post Regulator Automotive Systems LM5010 PACKAGE BODY SIZE (NOM) WSON (10) 4.00 mm × 4.00 mm HTSSOP (14) 4.40 mm × 5.00 mm (1) For all available packages, see the orderable addendum at the end of the data sheet. Basic Step-Down Regulator 8V - 75V Input VCC VIN C3 C1 LM5010 RON BST C4 L1 RON / SD SHUTDOWN VOUT SW D1 SS R1 ISEN C2 C6 FB RTN SGND R2 Copyright © 2016, Texas Instruments Incorporated 1 An IMPORTANT NOTICE at the end of this data sheet addresses availability, warranty, changes, use in safety-critical applications, intellectual property matters and other important disclaimers. PRODUCTION DATA. LM5010 SNVS307G – SEPTEMBER 2004 – REVISED APRIL 2016 www.ti.com Table of Contents 1 2 3 4 5 6 7 Features .................................................................. Applications ........................................................... Description ............................................................. Revision History..................................................... Pin Configuration and Functions ......................... Specifications......................................................... 1 1 1 2 3 4 6.1 6.2 6.3 6.4 6.5 6.6 6.7 4 4 4 5 5 6 7 Absolute Maximum Ratings ...................................... ESD Ratings.............................................................. Recommended Operating Conditions....................... Thermal Information .................................................. Electrical Characteristics........................................... Switching Characteristics .......................................... Typical Characteristics .............................................. Detailed Description .............................................. 9 7.1 Overview ................................................................... 9 7.2 Functional Block Diagram ......................................... 9 7.3 Feature Description................................................... 9 7.4 Device Functional Modes........................................ 14 8 Application and Implementation ........................ 15 8.1 Application Information............................................ 15 8.2 Typical Application .................................................. 15 8.3 Do's and Don'ts ....................................................... 21 9 Power Supply Recommendations...................... 22 10 Layout................................................................... 22 10.1 Layout Guidelines ................................................. 22 10.2 Layout Example .................................................... 22 11 Device and Documentation Support ................. 23 11.1 11.2 11.3 11.4 Community Resources.......................................... Trademarks ........................................................... Electrostatic Discharge Caution ............................ Glossary ................................................................ 23 23 23 23 12 Mechanical, Packaging, and Orderable Information ........................................................... 23 4 Revision History NOTE: Page numbers for previous revisions may differ from page numbers in the current version. Changes from Revision F (February 2013) to Revision G • Added ESD Ratings table, Feature Description section, Device Functional Modes, Application and Implementation section, Power Supply Recommendations section, Layout section, Device and Documentation Support section, and Mechanical, Packaging, and Orderable Information section .................................................................................................. 1 Changes from Revision E (February 2013) to Revision F • 2 Page Page Changed layout of National Data Sheet to TI format ............................................................................................................. 1 Submit Documentation Feedback Copyright © 2004–2016, Texas Instruments Incorporated Product Folder Links: LM5010 LM5010 www.ti.com SNVS307G – SEPTEMBER 2004 – REVISED APRIL 2016 5 Pin Configuration and Functions DPR Package 10-Pin WSON Top View PWP Package 14-Pin HTSSOP Top View SW 1 10 VIN NC 1 14 NC BST 2 9 VCC SW 2 13 VIN I   SEN 3 8 R BST 3 12 VCC 4 7 SS I   SEN 4 11 R 5 6 FB 5 10 SS RTN 6 9 FB NC 7 8 NC S GND   RTN ExposedPad ON  /SD S GND   ExposedPad  /SD ON Pin Functions PIN I/O DESCRIPTION 3 I Boost pin for bootstrap capacitor: Connect a 0.022-µF capacitor from SW to this pin. The capacitor is charged from VCC through an internal diode during each OFF-time. — — — FB 6 9 I Feedback input from the regulated output: Internally connected to the regulation and overvoltage comparators. The regulation level is 2.5 V. ISEN 3 4 I Current sense: The recirculating current flows through the internal sense resistor, and out of this pin to the free-wheeling diode. Current limit is nominally set at 1.25 A. NC — 1, 7, 8, 14 — RON/SD 8 11 I RTN 5 6 — Circuit ground: Ground for all internal circuitry other than the current limit detection. SGND 4 5 — Sense ground: Recirculating current flows into this pin to the current sense resistor. SS 7 10 I Soft start: An internal 11.5-µA current source charges an external capacitor to 2.5 V, providing the soft start function. SW 1 2 O Switching node: Internally connected to the buck switch source. Connect to the inductor, free-wheeling diode, and bootstrap capacitor. VCC 9 12 I Output from the startup regulator: Nominally regulates at 7 V. An external voltage (7.5 V to 14 V) can be applied to this pin to reduce internal dissipation. An internal diode connects VCC to VIN. VIN 10 13 I Input supply: Nominal input range is 8 V to 75 V. NAME WSON HTSSOP BST 2 EP Exposed pad No connection ON-time control and shutdown: An external resistor from VIN to this pin sets the buck switch ON-time. Grounding this pin shuts down the regulator. Submit Documentation Feedback Copyright © 2004–2016, Texas Instruments Incorporated Product Folder Links: LM5010 3 LM5010 SNVS307G – SEPTEMBER 2004 – REVISED APRIL 2016 www.ti.com 6 Specifications 6.1 Absolute Maximum Ratings over operating free-air temperature range (unless otherwise noted) (1) MIN MAX UNIT 8 75 V VIN to GND 76 V BST to GND 90 V –1.5 V BST to VCC 76 V BST to SW 14 V VCC to GND 14 V VIN SW to GND (steady state) SGND to RTN –0.3 0.3 V SS to RTN –0.3 4 V 76 V 7 V VIN to SW All other inputs to GND Lead temperature (soldering, 4 s) –0.3 (2) 260 °C Junction temperature, TJ –40 150 °C Storage temperature, Tstg –55 150 °C (1) (2) Stresses beyond those listed under Absolute Maximum Ratings may cause permanent damage to the device. These are stress ratings only, which do not imply functional operation of the device at these or any other conditions beyond those indicated under Recommended Operating Conditions. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability. For detailed information on soldering plastic HTSSOP and WSON packages, see Mechanical, Packaging, and Orderable Information. 6.2 ESD Ratings VALUE V(ESD) (1) (2) Electrostatic discharge Human-body model (HBM), per ANSI/ESDA/JEDEC JS-001 (1) ±2000 Charged-device model (CDM), per JEDEC specification JESD22-C101 (2) UNIT V ±750 JEDEC document JEP155 states that 500-V HBM allows safe manufacturing with a standard ESD control process. JEDEC document JEP157 states that 250-V CDM allows safe manufacturing with a standard ESD control process. 6.3 Recommended Operating Conditions over operating free-air temperature range (unless otherwise noted) VIN Input voltage IO Output current Ext-VCC External bias voltage TJ Operating junction temperature 4 Submit Documentation Feedback MIN MAX 8 75 UNIT V 1 A 8 13 V –40 125 °C Copyright © 2004–2016, Texas Instruments Incorporated Product Folder Links: LM5010 LM5010 www.ti.com SNVS307G – SEPTEMBER 2004 – REVISED APRIL 2016 6.4 Thermal Information LM5010 THERMAL METRIC (1) DPR (WSON) PWP (HTSSOP) 10 PINS 14 PINS UNIT 36 41.1 °C/W RθJA Junction-to-ambient thermal resistance RθJC(top) Junction-to-case (top) thermal resistance 31.9 26.5 °C/W RθJB Junction-to-board thermal resistance 13.2 22.5 °C/W ψJT Junction-to-top characterization parameter 0.3 0.7 °C/W ψJB Junction-to-board characterization parameter 13.5 22.2 °C/W RθJC(bot) Junction-to-case (bottom) thermal resistance 3 3.3 °C/W (1) For more information about traditional and new thermal metrics, see the Semiconductor and IC Package Thermal Metrics application report, SPRA953. 6.5 Electrical Characteristics Typical values correspond to TJ = 25°C, minimum and maximum limits apply over TJ = –40°C to 125°C, VIN = 48 V, and RON = 200 kΩ (unless otherwise noted). (1) (2) PARAMETER TEST CONDITIONS MIN TYP MAX 6.6 7 7.4 UNIT VCC REGULATOR VCCReg VCC regulated output VIN - VCC VCC output impedance (0 mA ≤ ICC ≤ 5 mA) VCC current limit ICC = 0 mA, FS < 200 kHz, 7.5 V ≤ VIN ≤ 8 V 1.3 VIN = 8 V 140 VIN = 48 V 2.5 V V Ω VCC = 0 V 10 VCC increasing 5.8 V UVLOVCC hysteresis VCC decreasing 145 mV UVLOVCC filter delay 100-mV overdrive IIN operating current Non-switching, FB = 3 V IIN shutdown current RON/SD = 0 V UVLOVCC VCC undervoltage lockout threshold mA 3 µs 650 850 µA 95 200 µA SOFT-START PIN Pullup voltage Internal current source 2.5 V 11.5 µA CURRENT LIMIT ILIM Threshold Current out of ISEN 1 1.25 1.5 A Resistance from ISEN to SGND 130 mΩ Response time 150 ns RON/SD PIN Shutdown threshold Voltage at RON/SD rising Threshold hysteresis Voltage at RON/SD falling 0.35 0.65 1.1 40 V mV HIGH-SIDE FET RDS(ON) Buck switch ITEST = 200 mA UVLOGD Gate drive UVLO VBST - VSW Increasing 3 UVLOGD Hysteresis 0.35 0.8 Ω 4.3 5 V 440 mV REGULATION AND OVERVOLTAGE COMPARATORS (FB PIN) VREF FB regulation threshold SS pin = steady state FB overvoltage threshold FB bias current (1) (2) 2.45 2.5 2.55 V 2.9 V 1 nA All minimum and maximum limits are specified by correlating the electrical characteristics to process and temperature variations and applying statistical process control. The junction temperature (TJ in °C) is calculated from the ambient temperature (TA in °C) and power dissipation (PD in Watts) as follows: TJ = TA + (PD × RθJA) where RθJA (in °C/W) is the package thermal impedance provided in Thermal Information. Submit Documentation Feedback Copyright © 2004–2016, Texas Instruments Incorporated Product Folder Links: LM5010 5 LM5010 SNVS307G – SEPTEMBER 2004 – REVISED APRIL 2016 www.ti.com Electrical Characteristics (continued) Typical values correspond to TJ = 25°C, minimum and maximum limits apply over TJ = –40°C to 125°C, VIN = 48 V, and RON = 200 kΩ (unless otherwise noted).(1)(2) PARAMETER TEST CONDITIONS MIN TYP MAX UNIT THERMAL SHUTDOWN TSD Thermal shutdown temperature Thermal shutdown hysteresis 175 °C 20 °C 6.6 Switching Characteristics Typical values correspond to TJ = 25°C, minimum and maximum limits apply over TJ = –40°C to 125°C and VIN = 48 V (unless otherwise noted) (1) PARAMETER TEST CONDITIONS RDS(ON) Buck switch ITEST = 200 mA UVLOGD Gate drive UVLO VBST - VSW Increasing MIN 3 UVLOGD Hysteresis TYP MAX 0.35 0.8 4.3 5 UNIT Ω V 440 mV 265 ns OFF TIMER tOFF Minimum OFF-time ON TIMER tON - 1 ON-time VIN = 10 V, RON = 200 kΩ 2.1 2.75 3.4 µs tON - 2 ON-time VIN = 75 V, RON = 200 kΩ 290 390 490 ns (1) 6 All minimum and maximum limits are specified by correlating the electrical characteristics to process and temperature variations while applying statistical process control. Submit Documentation Feedback Copyright © 2004–2016, Texas Instruments Incorporated Product Folder Links: LM5010 LM5010 www.ti.com SNVS307G – SEPTEMBER 2004 – REVISED APRIL 2016 6.7 Typical Characteristics at TA = 25°C (unless otherwise noted) 7.5 8 VIN = 48V 7 7.0 6 FS = 100 kHz FS = 620 kHz VIN = 8V 5 VCC (V) VCC (V) 6.5 6.0 VIN = 9V 4 3 FS = 200 kHz 2 5.5 VCC Externally Loaded Load Current = 300 mA ICC = 0 mA 1 FS = 100 kHz 0 5.0 6.5 7.0 7.5 8.0 8.5 9.0 9.5 0 10 2 4 Figure 1. VCC vs VIN 10 Figure 2. VCC vs ICC 9 8.0 8 7.0 FS = 550 kHz RON = 500k 7 6.0 6 ON-TIME (Ps) ICC INPUT CURRENT(mA) 8 ICC (mA) VIN (V) 5.0 4.0 FS = 200 kHz 3.0 300k 5 4 3 2.0 100k 2 FS = 100 kHz 1.0 1 0 0 8 7 9 10 11 12 13 14 0 8 20 EXTERNALLY APPLIED VCC (V) 40 60 80 VIN (V) Figure 3. ICC vs Externally Applied VCC Figure 4. ON-Time vs VIN and RON 4.0 800 FB = 3V 700 RON = 50k 600 3.0 115k 500 IIN (PA) RON/SD PIN VOLTAGE (V) 6 301k 2.0 400 300 511k 200 1.0 RON/SD = 0V 100 0 0 0 8 20 40 60 80 0 8 20 40 60 80 VIN (V) VIN (V) Figure 5. Voltage at RON/SD Pin Figure 6. IIN vs VIN Submit Documentation Feedback Copyright © 2004–2016, Texas Instruments Incorporated Product Folder Links: LM5010 7 LM5010 SNVS307G – SEPTEMBER 2004 – REVISED APRIL 2016 www.ti.com Typical Characteristics (continued) at TA = 25°C (unless otherwise noted) VIN 7.0V UVLO VCC SW Pin Inductor Current 2.5V SS Pin VOUT t1 t2 Figure 7. Start-Up Sequence 8 Submit Documentation Feedback Copyright © 2004–2016, Texas Instruments Incorporated Product Folder Links: LM5010 LM5010 www.ti.com SNVS307G – SEPTEMBER 2004 – REVISED APRIL 2016 7 Detailed Description 7.1 Overview The LM5010 step-down switching regulator features all the functions needed to implement a low-cost, efficient, buck bias power converter. This high-voltage regulator contains a 75-V N-channel buck switch, is easy to implement, and is provided in HTSSOP and thermally-enhanced, WSON packages. The regulator is based on a control scheme using an ON-time inversely proportional to VIN. The control scheme requires no loop compensation. The functional block diagram of the LM5010 is shown in the Functional Block Diagram. The LM5010 can be applied in numerous applications to efficiently regulate down higher voltages. This regulator is well-suited for 48-V telecom and 42-V automotive power bus ranges. Additional features include: thermal shutdown, VCC undervoltage lockout, gate drive undervoltage lockout, maximum duty cycle limit timer, and the valley current limit functionality. 7.2 Functional Block Diagram INPUT 10 LM5010 7V START-UP REGULATOR VIN C5 VCC UVLO VCC 9 Thermal Shutdown C3 C1 RON ON TIMER 8 R ON /SD 7 RON START COMPLETE 2.5V 11.5 PA SS 265 ns OFF TIMER 0.7V START COMPLETE Gate Drive UVLO VIN C4 DRIVER LOGIC Driver C6 6 FB BST 2 LEVEL SHIFT L1 OVER-VOLTAGE COMPARATOR REGULATION COMPARATOR D1 CURRENT LIMIT COMPARATOR 62.5 mV 5 RTN VOUT1 SW 1 2.9V ISEN + 3 R SENSE 50 m: SGND R1 RCL 4 R2 R3 VOUT2 C2 GND Copyright © 2016, Texas Instruments Incorporated Pin numbers are for the WSON (10) package 7.3 Feature Description The LM5010 step-down switching regulator features all the functions needed to implement a low-cost, efficient buck bias power converter capable of supplying in excess of 1 A to the load. This high voltage regulator contains an N-Channel buck switch, is easy to implement, and is available in the thermally enhanced 10-pin WSON and 14-pin HTSSOP packages. The regulator’s operation is based on a constant ON-time control scheme, where the ON-time varies inversely with VIN. This feature results in the operating frequency remaining relatively constant with load and input voltage variations. The switching frequency can range from 100 kHz to > 1 MHz. The hysteretic control requires no loop compensation, resulting in very fast load transient response. The valley current limit detection circuit, internally set at 1.25 A, holds the buck switch off until the high current level subsides. The LM5010 can be applied in numerous applications to efficiently regulate down higher voltages. This regulator is well suited for 48-V telecom applications, as well as the new 42-V automotive power bus. Implemented as a point-of-load regulator following a highly-efficient intermediate bus converter can result in high overall system efficiency. Features include: Thermal shutdown, VCC undervoltage lockout, gate drive undervoltage lockout, and maximum duty cycle limit. Submit Documentation Feedback Copyright © 2004–2016, Texas Instruments Incorporated Product Folder Links: LM5010 9 LM5010 SNVS307G – SEPTEMBER 2004 – REVISED APRIL 2016 www.ti.com Feature Description (continued) 7.3.1 Control Circuit Overview The LM5010 buck DC-DC regulator employs a control scheme based on a comparator and a one-shot ON timer, with the output voltage feedback (FB) compared to an internal reference (2.5 V). If the FB voltage is below the reference the buck switch is turned on for a time period determined by the input voltage and a programming resistor (RON). Following the ON-time the switch remains off for 265 ns, or until the FB voltage falls below the reference, whichever is longer. The buck switch then turns on for another ON-time period. Typically when the load current increases suddenly, the OFF-times are temporarily at the minimum of 265 ns. Once regulation is established, the OFF-time resumes its normal value. The output voltage is set by two external resistors (R1, R2). The regulated output voltage is calculated with Equation 1. VOUT = 2.5 V × (R1 + R2) / R2 (1) Output voltage regulation is based on ripple voltage at the feedback input, requiring a minimum amount of ESR for the output capacitor C2. The LM5010 requires a minimum of 25-mV of ripple voltage at the FB pin. In cases where the capacitor’s ESR is insufficient, additional series resistance may be required (R3 in Functional Block Diagram). When in regulation, the LM5010 operates in continuous conduction mode at heavy load currents and discontinuous conduction mode at light load currents. In continuous conduction mode current always flows through the inductor, never reaching zero during the OFF-time. In this mode the operating frequency remains relatively constant with load and line variations. The minimum load current for continuous conduction mode is one-half the inductor’s ripple current amplitude. Calculate the approximate operating frequency with Equation 2. VOUT FS = 1.18 x 10-10 x RON (2) The buck switch duty cycle is approximately equal to Equation 3. VOUT tON DC = tON + tOFF = VIN (3) At low load current, the circuit operates in discontinuous conduction mode, during which the inductor current ramps up from zero to a peak during the ON-time, then ramps back to zero before the end of the OFF-time. The next ON-time period starts when the voltage at FB falls below the reference until then the inductor current remains zero, and the load current is supplied by the output capacitor (C2). In this mode the operating frequency is lower than in continuous conduction mode, and varies with load current. Conversion efficiency is maintained at light loads because the switching losses reduce with the reduction in load and frequency. Calculate the approximate discontinuous operating frequency with Equation 4. VOUT2 x L1 x 1.4 x 1020 FS = RL x (RON)2 where • RL = the load resistance (4) For applications where lower output voltage ripple is required, the output can be taken directly from a low ESR output capacitor as shown in Figure 8. However, R3 slightly degrades the load regulation. 10 Submit Documentation Feedback Copyright © 2004–2016, Texas Instruments Incorporated Product Folder Links: LM5010 LM5010 www.ti.com SNVS307G – SEPTEMBER 2004 – REVISED APRIL 2016 Feature Description (continued) L1 SW LM5010 R1 R3 FB V OUT2 C2 R2 Figure 8. Low Ripple Output Configuration 7.3.2 Start-Up Regulator (VCC) The start-up regulator is integral to the LM5010. The input pin (VIN) can be connected directly to line voltages up to 75 V. The VCC output is regulated at 7 V, ±6%, and is current-limited to 10 mA. Upon power up the regulator sources current into the external capacitor at VCC (C3). With a 0.1-µF capacitor at VCC, approximately 58 µs are required for the VCC voltage to reach the undervoltage lockout threshold (UVLO) of 5.8 V (t1 in Figure 7), at which time the buck switch is enabled, and the soft-start pin is released to allow the soft-start capacitor (C6) to charge up. VOUT then increases to its regulated value as the soft-start voltage increases (t2 in Figure 7). The minimum input operating voltage is determined by the regulator’s dropout voltage, the VCC UVLO falling threshold (≊5.65 V), and the frequency. When VCC falls below the falling threshold the VCC UVLO activates to shut off the buck switch and ground the soft-start pin. If VCC is externally loaded, the minimum input voltage increases since the output impedance at VCC is ≊140 Ω at low VIN. See Figure 1 and Figure 2. In applications involving a high value for VIN where power dissipation in the start-up regulator is a concern, an auxiliary voltage can be diode connected to the VCC pin (Figure 9). Setting the auxiliary voltage to between 7.5 V and 14 V shuts off the internal regulator, reducing internal power dissipation. Figure 3 shows the current required into the VCC pin. A diode connects VCC to VIN internally. VCC C3 BST C4 LM5010 L1 D2 SW VOUT1 D1 I SEN R1 R3 V OUT2 S GND R2 C2 FB Figure 9. Self Biased Configuration 7.3.3 Regulation Comparator The feedback voltage at FB is compared to the voltage at the soft-start pin (2.5 V, ±2%). In normal operation (the output voltage is regulated) an ON-time period is initiated when the voltage at FB falls below 2.5 V. The buck switch stays on for the ON-time causing the FB voltage to rise above 2.5 V. After the ON-time period the buck switch stays off until the FB voltage falls below 2.5 V. Bias current at the FB pin is less than 5 nA over temperature. Submit Documentation Feedback Copyright © 2004–2016, Texas Instruments Incorporated Product Folder Links: LM5010 11 LM5010 SNVS307G – SEPTEMBER 2004 – REVISED APRIL 2016 www.ti.com Feature Description (continued) 7.3.4 Overvoltage Comparator The feedback voltage at FB is compared to an internal 2.9-V reference. If the voltage at FB rises above 2.9 V, the ON-time is immediately terminated. This condition can occur if the input voltage or the output load changes suddenly. The buck switch will not turn on again until the voltage at FB falls below 2.5 V. 7.3.5 ON-Time Control The ON-time of the internal switch (see Figure 4) is determined by the RON resistor and the input voltage (VIN), calculated with Equation 5. 1.18 x 10-10 x (RON + 1.4k) tON = VIN - 1.4V + 67 ns (5) The inverse relationship of tON vs VIN results in a nearly constant frequency as VIN is varied. If the application requires a high frequency, the minimum value for tON, and consequently RON, is limited by the OFF-time (265 ns, ±15%) which limits the maximum duty cycle at minimum VIN. The tolerance for Equation 5 is ±25%. Frequencies in excess of 1 MHz are possible with the LM5010. 7.3.6 Current Limit Current limit detection occurs during the OFF-time by monitoring the recirculating current through the freewheeling diode (D1). The detection threshold is 1.25 A, ±0.25 A. Referring to Functional Block Diagram, when the buck switch is off the inductor current flows through the load, into SGND, through the sense resistor, out of ISEN and through D1. If that current exceeds the threshold the current limit comparator output switches to delay the start of the next ON-time period. The next ON-time starts when the current out of ISEN is below the threshold and the voltage at FB is below 2.5 V. If the overload condition persists causing the inductor current to exceed the threshold during each ON-time, that is detected at the beginning of each OFF-time. The operating frequency is lower due to longer-than-normal OFF-times. Figure 10 illustrates the inductor current waveform. During normal operation the load current is IO, the average of the ripple waveform. When the load resistance decreases the current ratchets up until the lower peak attempts to exceed the threshold. During the Current Limited portion of Figure 10, the current ramps down to the threshold during each OFF-time, initiating the next ON-time (assuming the voltage at FB is < 2.5 V). During each ON-time the current ramps up an amount equal to Equation 6. 'I = (VIN - VOUT) x tON L1 (6) During this time the LM5010 is in a constant current mode, with an average load current (IOCL) equal to the threshold + ΔI / 2. The valley current limit technique allows the load current to exceed the current limit threshold as long as the lower peak of the inductor current is less than the threshold. 12 Submit Documentation Feedback Copyright © 2004–2016, Texas Instruments Incorporated Product Folder Links: LM5010 LM5010 www.ti.com SNVS307G – SEPTEMBER 2004 – REVISED APRIL 2016 Feature Description (continued) IPK 'I IOCL Inductor Current Threshold IO Normal Operation Load Current Increases Current Limited Figure 10. Inductor Current, Current Limit Operation The current limit threshold can be increased by connecting an external resistor (RCL) between SGND and ISEN. The external resistor typically is less than 1 Ω, and its calculation is explained in Application and Implementation. The peak current out of SW and ISEN must not exceed 3.5 A. The average current out of SW must be less than 3 A, and the average current out of ISEN must be less than 2 A. 7.3.7 Soft Start The soft-start feature allows the converter to gradually reach a steady-state operating point, thereby reducing start-up stresses and current surges. Upon turnon, after VCC reaches the undervoltage threshold (t1 in Figure 7), an internal 11.5-µA current source charges the external capacitor at the soft-start pin to 2.5 V (t2 in Figure 7). The ramping voltage at SS (and at the non-inverting input of the regulation comparator) ramps up the output voltage in a controlled manner. This feature keeps the load current from going to current limit during start-up, thereby reducing inrush currents. An internal switch grounds the soft-start pin if VCC is below the undervoltage lockout threshold, if a thermal shutdown occurs, or if the circuit is shutdown using the RON/SD pin. 7.3.8 N-Channel Buck Switch and Driver The LM5010 integrates an N-Channel buck switch and associated floating high voltage gate driver. The peak current through the buck switch must not be allowed to exceed 3.5 A, and the average current must be less than 3 A. The gate driver circuit is powered by the external bootstrap capacitor between BST and SW (C4). During each OFF-time, the SW pin is at approximately –1 V, and C4 is recharged from VCC through the internal high voltage diode. The minimum OFF-time of 265 ns ensures a minimum time each cycle to recharge the bootstrap capacitor. TI recommends a 0.022-µF ceramic capacitor for C4. 7.3.9 Thermal Shutdown The LM5010 should be operated so the junction temperature does not exceed 125°C. If the junction temperature increases above that, an internal Thermal Shutdown circuit activates (typically) at 175°C, taking the controller to a low-power reset state by disabling the buck switch and the ON timer, and grounding the soft-start pin. This feature helps prevent catastrophic failures from accidental device overheating. When the junction temperature reduces below 155°C (typical hysteresis = 20°C), the softstart pin is released and normal operation resumes. Submit Documentation Feedback Copyright © 2004–2016, Texas Instruments Incorporated Product Folder Links: LM5010 13 LM5010 SNVS307G – SEPTEMBER 2004 – REVISED APRIL 2016 www.ti.com 7.4 Device Functional Modes 7.4.1 Shutdown The LM5010 can be remotely shut down by taking the RON/SD pin below 0.65 V. See Figure 11. In this mode the soft-start pin is internally grounded, the ON timer is disabled, and the input current at VIN is reduced (Figure 6). Releasing the RON/SD pin allows normal operation to resume. When the switch is open, the nominal voltage at RON/SD is shown in Figure 5. VIN Input Voltage RON LM5010 R ON /SD STOP RUN Figure 11. Shutdown Implementation 14 Submit Documentation Feedback Copyright © 2004–2016, Texas Instruments Incorporated Product Folder Links: LM5010 LM5010 www.ti.com SNVS307G – SEPTEMBER 2004 – REVISED APRIL 2016 8 Application and Implementation NOTE Information in the following applications sections is not part of the TI component specification, and TI does not warrant its accuracy or completeness. TI’s customers are responsible for determining suitability of components for their purposes. Customers should validate and test their design implementation to confirm system functionality. 8.1 Application Information The LM5010 is a non-synchronous buck regulator converter designed to operate over a wide input voltage and output current range. Spreadsheet-based calculator tools, available on the TI product website at Quick-Start Calculator, can be used to design a single output non-synchronous buck converter. Alternatively, online WEBENCH® software is available to create a complete buck design and generate the bill of materials, estimated efficiency, solution size, and cost of the complete solution. 8.2 Typical Application The final circuit is shown in Figure 12, and its performance is shown from Figure 14 to Figure 17. VCC VIN 15 - 75V Input C1 2.2 PF C3 0.1 PF C5 0.1 PF BST 137k RON LM5010 RON / SD C4 0.022 PF L1 100 PH 10V SW SHUTDOWN VOUT D1 SS ISEN C6 0.022 PF SGND FB R1 3.0k R3 2.8 R2 1.0k C2 15 PF GND RTN Copyright © 2016, Texas Instruments Incorporated Figure 12. LM5010 Example Circuit 8.2.1 Design Requirements Table 1 lists the operating parameters for Figure 12. Table 1. Design Parameters PARAMETER EXAMPLE VALUE Input voltage 15 V to 75 V Output voltage 10 V Load current 150 mA to 1 A Soft-start time 5 ms 8.2.2 Detailed Design Procedure The procedure for calculating the external components is illustrated with a design example. Configure the circuit in Figure 12 according to the components listed in Table 2. Submit Documentation Feedback Copyright © 2004–2016, Texas Instruments Incorporated Product Folder Links: LM5010 15 LM5010 SNVS307G – SEPTEMBER 2004 – REVISED APRIL 2016 www.ti.com Table 2. List of Components for LM5010 Example Circuit COMPONENT DESCRIPTION VALUE C1 Ceramic Capacitor 2.2 µF, 100 V C2 Ceramic Capacitor 15 µF, 25 V C3 Ceramic Capacitor 0.1 µF, 16 V C4, C6 Ceramic Capacitor 0.022 µF, 16 V C5 Ceramic Capacitor 0.1 µF, 100 V D1 Ultra-fast diode 100 V, 2 A L1 Inductor 100 µH R1 Resistor 3 kΩ R2 Resistor 1 kΩ R3 Resistor 2.8 Ω RON Resistor 137 kΩ U1 Switching regulator — 8.2.2.1 Component Selection 8.2.2.1.1 R1 and R2 Calculate the ratio of these resistors with Equation 7. R1 / R2 = (VOUT / 2.5 V) - 1 (7) R1 and R2 calculates to 3. The resistors should be chosen from standard value resistors in the range of 1 kΩ to 10 kΩ. Values of 3 kΩ for R1, and 1 kΩ for R2 are used. 8.2.2.1.2 RON, FS RON sets the ON-time, and can be chosen using Equation 2 to set a nominal frequency, or from Equation 5 if the ON-time at a particular VIN is important. A higher frequency generally means a smaller inductor and capacitors (value, size and cost), but higher switching losses. A lower frequency means a higher efficiency, but with larger components. If PC board space is tight, a higher frequency is better. The resulting ON-time and frequency have a ±25% tolerance, rearranging Equation 2 to Equation 8. RON = 10V 1.18 x 10-10 x 625 kHz = 136 k: (8) The next larger standard value (137 kΩ) is chosen for RON, yielding a nominal frequency of 618 kHz. 8.2.2.1.3 L1 The inductor value is determined based on the load current, ripple current, and the minimum and maximum input voltage (VIN(min), VIN(max)). See Figure 13. L1 Current IPK+ IO IOR IPK- 0 mA 1/Fs Figure 13. Inductor Current To keep the circuit in continuous conduction mode, the maximum allowed ripple current is twice the minimum load current, or 300 mAP-P. Using this value of ripple current, the inductor (L1) is calculated using Equation 9 and Equation 10. 16 Submit Documentation Feedback Copyright © 2004–2016, Texas Instruments Incorporated Product Folder Links: LM5010 LM5010 www.ti.com SNVS307G – SEPTEMBER 2004 – REVISED APRIL 2016 VOUT1 x (VIN(max) - VOUT1) L1 = IOR x FS(min) x VIN(max) where • FS(min) is the minimum frequency (FS - 25%) (9) 10V x (75V - 10V) L1 = = 63 PH 0.30A x 463 kHz x 75V (10) Equation 10 provides the minimum value for inductor L1. When selecting an inductor, use a higher standard value (100 uH). L1 must be rated for the peak current (IPK+) to prevent saturation. The peak current occurs at maximum load current with maximum ripple. The maximum ripple is calculated by rearranging Equation 9 using VIN(max), FS(min), and the minimum inductor value, based on the manufacturer’s tolerance. Assume for Equation 11, Equation 12, and Equation 13 that the inductor’s tolerance is ±20%. VOUT1 x (VIN(max) - VOUT1) IOR(max) = L1MIN x FS(min) x VIN(max) (11) 10V x (75V - 10V) IOR(max) = 80 PH x 463 kHz x 75V = 234 mAp-p (12) (13) IPK+ = 1 A + 0.234 A / 2 = 1.117 A 8.2.2.1.4 RCL Since it is obvious that the lower peak of the inductor current waveform does not exceed 1 A at maximum load current (see Figure 13), it is not necessary to increase the current limit threshold. Therefore RCL is not needed for this exercise. For applications where the lower peak exceeds 1 A, see Increasing The Current Limit Threshold. 8.2.2.1.5 C2 and R3 Since the LM5010 requires a minimum of 25 mVP-P of ripple at the FB pin for proper operation, the required ripple at VOUT1 is increased by R1 and R2. This necessary ripple is created by the inductor ripple current acting on C2’s ESR + R3. First, determine the minimum ripple current with Equation 14. VOUT1 x (VIN(min) - VOUT1) IOR(min) = = L1MAX x FS(max) x VIN(min) 10V x (15V - 10V) 120 PH x 772 kHz x 15V = 36 mA (14) The minimum ESR for C2 is then equal to Equation 15. ESR(min) = 25 mV x (R1 + R2) R2 x IOR(min) = 2.8: (15) If the capacitor used for C2 does not have sufficient ESR, R3 is added in series as shown in Figure 12. C2 should generally be no smaller than 3.3 µF, although that is dependent on the frequency and the allowable ripple amplitude at VOUT1. Experimentation is usually necessary to determine the minimum value for C2, as the nature of the load may require a larger value. A load which creates significant transients requires a larger value for C2 than a non-varying load. Submit Documentation Feedback Copyright © 2004–2016, Texas Instruments Incorporated Product Folder Links: LM5010 17 LM5010 SNVS307G – SEPTEMBER 2004 – REVISED APRIL 2016 www.ti.com 8.2.2.1.6 D1 The important parameters are reverse recovery time and forward voltage drop. The reverse recovery time determines how long the current surge lasts each time the buck switch is turned on. The forward voltage drop is significant in the event the output is short-circuited as it is mainly this diode’s voltage (plus the voltage across the current limit sense resistor) which forces the inductor current to decrease during the OFF-time. For this reason, a higher voltage is better, although that affects efficiency. A reverse recovery time of ≊30 ns, and a forward voltage drop of ≊0.75 V are preferred. The reverse leakage specification is important as that can significantly affect efficiency. Other types of diodes may have a lower forward voltage drop, but may have longer recovery times, or greater reverse leakage. D1 should be rated for the maximum VIN, and for the peak current when in current limit (IPK in Figure 11) which is equal to Equation 16. IPK = 1.5 A + IOR(max) = 1.734 A where • • 1.5 A is the maximum guaranteed current limit threshold the maximum ripple current was previously calculated as 234 mAP-P (16) This calculation is only valid when RCL is not required. 8.2.2.1.7 C1 Assuming the voltage supply feeding VIN has a source impedance greater than zero, this capacitor limits the ripple voltage at VIN while supplying most of the switch current during the ON-time. At maximum load current, when the buck switch turns on, the current into VIN increases to the lower peak of the output current waveform, ramps up to the peak value, then drops to zero at turnoff. The average current into VIN during this ON-time is the load current. For a worst case calculation, C1 must supply this average load current during the maximum ONtime. The maximum ON-time is calculated using Equation 5, with a 25% tolerance added in Equation 17. tON(max) = 1.18 x 10-10 x (137k + 1.4k) x 1.25 15V - 1.4V + 67 ns = 1.57 Ps (17) C1 is calculated with Equation 18. C1 = IO x tON 'V = 1.0A x 1.57 Ps 1V = 1.57 PF where • • IO is the load current ΔV is the allowable ripple voltage at VIN (1 V for this example) (18) TI recommends quality ceramic capacitors with a low ESR for C1. To allow for capacitor tolerances and voltage effects, use a 2.2-µF capacitor. 8.2.2.1.8 C3 The capacitor at the VCC pin provides not only noise filtering and stability, but also prevents false triggering of the VCC UVLO at the buck switch ON and OFF transitions. For this reason, C3 should be no smaller than 0.1 µF, and should be a good quality, low ESR, ceramic capacitor. This capacitor also determines the initial start-up delay (t1 in Figure 7). 8.2.2.1.9 C4 TI recommends a value of 0.022 µF for C4. TI recommends a high-quality ceramic capacitor with low ESR, because C4 supplies the surge current to charge the buck switch gate at turnon. A low ESR also ensures a complete recharge during each OFF-time. 8.2.2.1.10 C5 This capacitor suppresses transients and ringing due to long lead inductance at VIN. TI recommends a low ESR, 0.1-µF ceramic chip capacitor, placed physically close to the LM5010. 18 Submit Documentation Feedback Copyright © 2004–2016, Texas Instruments Incorporated Product Folder Links: LM5010 LM5010 www.ti.com SNVS307G – SEPTEMBER 2004 – REVISED APRIL 2016 8.2.2.1.11 C6 The capacitor at the SS pin determines the soft-start time (that is the time for the reference voltage at the regulation comparator and the output voltage), to reach their final value. Determine the time with Equation 19. tSS = C6 x 2.5V 11.5 PA (19) For a 5-ms soft-start time, C6 calculates to 0.022 µF. 8.2.2.2 Increasing The Current Limit Threshold The current limit threshold is nominally 1.25 A, with a minimum guaranteed value of 1 A. If, at maximum load current, the lower peak of the inductor current (IPK– in Figure 13) exceeds 1 A, resistor RCL must be added between SGND and ISEN to increase the current limit threshold to be equal or exceed that lower peak current. This resistor diverts some of the recirculating current from the internal sense resistor so that a higher current level is needed to switch the internal current limit comparator. Calculate IPK– with Equation 20. IPK- = IO(max) - IOR(min) 2 where • • IO(max) is the maximum load current IOR(min) is the minimum ripple current calculated using Equation 14 (20) RCL is calculated with Equation 21. RCL = 1.0A x 0.11: IPK- - 1.0A where • 0.11 Ω is the minimum value of the internal resistance from SGND to ISEN (21) The next smaller standard value resistor should be used for RCL. With the addition of RCL it is necessary to check the average and peak current values to ensure they do not exceed the LM5010 limits. At maximum load current the average current through the internal sense resistor is calculated with Equation 22. IO(max) x RCL x (VIN(max) - VOUT) IAVE = (RCL + 0.11: x VIN(max) (22) If IAVE is less than 2 A, no changes are necessary. If it exceeds 2 A, RCL must be reduced. The upper peak of the inductor current (IPK+), at maximum load current, is calculated using Equation 23. IOR(max) IPK+ = IO(max) + 2 where • IOR(max) is calculated using Equation 11 (23) If IPK+ exceeds 3.5 A , the inductor value must be increased to reduce the ripple amplitude. This necessitates recalculation of IOR(min), IPK–, and RCL. When the circuit is in current limit, the upper peak current out of the SW pin is calculated with Equation 24. 1.5A x (150 m: + RCL) IPK+(CL) = RCL + IOR(MAX) (24) The inductor L1 and diode D1 must be rated for this current. Submit Documentation Feedback Copyright © 2004–2016, Texas Instruments Incorporated Product Folder Links: LM5010 19 LM5010 SNVS307G – SEPTEMBER 2004 – REVISED APRIL 2016 www.ti.com 8.2.2.3 Ripple Configuration The LM5010 uses a constant-ON-time (COT) control scheme where the ON-time is terminated by a one-shot and the OFF-time is terminated by the feedback voltage (VFB) falling below the reference voltage. Therefore, for stable operation, the feedback voltage must decrease monotonically in phase with the inductor current during the OFF-time. Furthermore, this change in feedback voltage (VFB) during OFF-time must be large enough to dominate any noise present at the feedback node. Table 3 presents three different methods for generating appropriate voltage ripple at the feedback node. Type 1 and type 2 ripple circuits couple the ripple from the output of the converter to the feedback node (FB). The output voltage ripple has two components: 1. Capacitive ripple caused by the inductor current ripple charging or discharging the output capacitor. 2. Resistive ripple caused by the inductor current ripple flowing through the ESR of the output capacitor and R3. Table 3. Ripple Configuration TYPE 1 TYPE 2 Lowest cost TYPE 3 Reduced ripple Minimum ripple VOUT VOUT L1 VOUT L1 L1 R FB2 Cff R FB2 R3 To FB C OUT COUT R FB2 GND R FB1 GND 25 mV u VO VREF u 'IL1, min CA CB To FB R FB1 R3 t RA R3 C OUT To FB R FB1 GND Cff t 5 FSW u (RFB2 IIRFB1 ) R A CA d (25) R t 25 mV 3 'IL1, min (VIN, min VO ) u TON(@ VIN, min ) 25mV (27) (26) The capacitive ripple is out of phase with the inductor current. As a result, the capacitive ripple does not decrease monotonically during the OFF-time. The resistive ripple is in phase with the inductor current and decreases monotonically during the OFF-time. The resistive ripple must exceed the capacitive ripple at output (VOUT) for stable operation. If this condition is not satisfied, then unstable switching behavior is observed in COT converters with multiple ON-time bursts in close succession followed by a long OFF-time. The type 3 ripple method uses a ripple injection circuit with RA, CA, and the switch node (SW) voltage to generate a triangular ramp. This triangular ramp is then AC-coupled into the feedback node (FB) using the capacitor CB. This circuit is suited for applications where low output voltage ripple is imperative because this circuit does not use the output voltage ripple. See AN-1481 Controlling Output Ripple and Achieving ESR Independence in Constant ON-Time (COT) Regulator Designs, (SNVA166) for more details on each ripple generation method. 20 Submit Documentation Feedback Copyright © 2004–2016, Texas Instruments Incorporated Product Folder Links: LM5010 LM5010 www.ti.com SNVS307G – SEPTEMBER 2004 – REVISED APRIL 2016 8.2.3 Application Curves 100 100 80 80 EFFICIENCY (%) EFFICIENCY (%) _ 60 40 20 VIN = 15V 60 24V 48V 75V 40 20 IOUT = 300mA 0 0 0 20 40 60 0 80 VIN (V) 200 400 600 800 _ 1000 LOAD CURRENT (mA) Figure 14. Efficiency vs VIN Figure 15. Efficiency vs Load Current and VIN 700 350 600 250 FREQUENCY (kHz) OUTPUT RIPPLE (mVp-p) 300 200 150 100 500 400 50 0 300 0 20 40 60 80 VIN (V) 0 20 40 60 80 VIN (V) Figure 16. Output Voltage Ripple vs VIN Figure 17. Frequency vs VIN 8.3 Do's and Don'ts A minimum load current of 1 mA is required to maintain proper operation. If the load current falls below that level, the bootstrap capacitor can discharge during the long OFF-time and the circuit either shuts down or cycles ON and OFF at a low frequency. If the load current is expected to drop below 1 mA in the application, choose the feedback resistors to be low enough in value to provide the minimum required current at nominal VOUT. Submit Documentation Feedback Copyright © 2004–2016, Texas Instruments Incorporated Product Folder Links: LM5010 21 LM5010 SNVS307G – SEPTEMBER 2004 – REVISED APRIL 2016 www.ti.com 9 Power Supply Recommendations The LM5010 is designed to operate with an input power supply capable of supplying a voltage range from 8 V to 75 V. The input power supply must be well-regulated and capable of supplying sufficient current to the regulator during peak load operation. Also, like in all applications, the power-supply source impedance must be small compared to the module input impedance to maintain the stability of the converter. 10 Layout 10.1 Layout Guidelines The LM5010 regulation, overvoltage, and current limit comparators are very fast, and respond to short duration noise pulses. Therefore, layout considerations are critical for optimum performance. The layout must be as neat and compact as possible, and all the components must be as close as possible to their associated pins. The current loop formed by D1, L1 (LIND), C2 (COUT), and the SGND and ISEN pins should be as small as possible. The ground connection from C2 (COUT) to C1 (CIN) should be as short and direct as possible. If it is expected that the internal dissipation of the LM5010 will produce high junction temperatures during normal operation, good use of the PC board’s ground plane can help considerably to dissipate heat. The exposed pad on the IC package bottom can be soldered to a ground plane, and that plane should both extend from beneath the IC, and be connected to exposed ground plane on the board’s other side using as many vias as possible. The exposed pad is internally connected to the IC substrate. The use of wide PC board traces at the pins, where possible, can help conduct heat away from the IC. The four no connect pins on the HTSSOP package are not electrically connected to any part of the IC, and may be connected to ground plane to help dissipate heat from the package. Judicious positioning of the PC board within the end product, along with the use of any available air flow (forced or natural convection) can help reduce the junction temperature. 10.2 Layout Example VOUT CA COUT LIND GND RA Cbyp CIN SW CBST SW LM5010 VCC BST D1 ISEN GND VLINE VIN Exp Thermal Pad RON RON CVCC CSS SGND SS RTN FB FB RFB2 CB RFB1 Via to Ground Plane Figure 18. LM5010 Buck Layout Example With the WSON Package 22 Submit Documentation Feedback Copyright © 2004–2016, Texas Instruments Incorporated Product Folder Links: LM5010 LM5010 www.ti.com SNVS307G – SEPTEMBER 2004 – REVISED APRIL 2016 11 Device and Documentation Support 11.1 Community Resources The following links connect to TI community resources. Linked contents are provided "AS IS" by the respective contributors. They do not constitute TI specifications and do not necessarily reflect TI's views; see TI's Terms of Use. TI E2E™ Online Community TI's Engineer-to-Engineer (E2E) Community. Created to foster collaboration among engineers. At e2e.ti.com, you can ask questions, share knowledge, explore ideas and help solve problems with fellow engineers. Design Support TI's Design Support Quickly find helpful E2E forums along with design support tools and contact information for technical support. 11.2 Trademarks E2E is a trademark of Texas Instruments. All other trademarks are the property of their respective owners. 11.3 Electrostatic Discharge Caution These devices have limited built-in ESD protection. The leads should be shorted together or the device placed in conductive foam during storage or handling to prevent electrostatic damage to the MOS gates. 11.4 Glossary SLYZ022 — TI Glossary. This glossary lists and explains terms, acronyms, and definitions. 12 Mechanical, Packaging, and Orderable Information The following pages include mechanical, packaging, and orderable information. This information is the most current data available for the designated devices. This data is subject to change without notice and revision of this document. For browser-based versions of this data sheet, refer to the left-hand navigation. Submit Documentation Feedback Copyright © 2004–2016, Texas Instruments Incorporated Product Folder Links: LM5010 23 PACKAGE OPTION ADDENDUM www.ti.com 30-Sep-2021 PACKAGING INFORMATION Orderable Device Status (1) Package Type Package Pins Package Drawing Qty Eco Plan (2) Lead finish/ Ball material MSL Peak Temp Op Temp (°C) Device Marking (3) (4/5) (6) LM5010MH NRND HTSSOP PWP 14 94 Non-RoHS & Green Call TI Level-1-260C-UNLIM -40 to 125 L5010 MH LM5010MH/NOPB ACTIVE HTSSOP PWP 14 94 RoHS & Green SN Level-1-260C-UNLIM -40 to 125 L5010 MH LM5010MHX/NOPB ACTIVE HTSSOP PWP 14 2500 RoHS & Green SN Level-1-260C-UNLIM -40 to 125 L5010 MH LM5010SD/NOPB ACTIVE WSON DPR 10 1000 RoHS & Green NIPDAU | SN Level-1-260C-UNLIM -40 to 125 L00057B LM5010SDX/NOPB ACTIVE WSON DPR 10 4500 RoHS & Green NIPDAU | SN Level-1-260C-UNLIM -40 to 125 L00057B (1) The marketing status values are defined as follows: ACTIVE: Product device recommended for new designs. LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect. NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design. PREVIEW: Device has been announced but is not in production. Samples may or may not be available. OBSOLETE: TI has discontinued the production of the device. (2) RoHS: TI defines "RoHS" to mean semiconductor products that are compliant with the current EU RoHS requirements for all 10 RoHS substances, including the requirement that RoHS substance do not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, "RoHS" products are suitable for use in specified lead-free processes. TI may reference these types of products as "Pb-Free". RoHS Exempt: TI defines "RoHS Exempt" to mean products that contain lead but are compliant with EU RoHS pursuant to a specific EU RoHS exemption. Green: TI defines "Green" to mean the content of Chlorine (Cl) and Bromine (Br) based flame retardants meet JS709B low halogen requirements of
LM5010MHX/NOPB 价格&库存

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LM5010MHX/NOPB
  •  国内价格 香港价格
  • 1+33.947781+4.21121
  • 10+24.8903310+3.08764
  • 25+24.6550725+3.05845
  • 100+22.14957100+2.74765
  • 250+15.74855250+1.95360
  • 1000+15.739681000+1.95250

库存:2273

LM5010MHX/NOPB
  •  国内价格 香港价格
  • 1+29.467141+3.65539
  • 10+21.3592710+2.64961
  • 25+19.3365025+2.39869
  • 100+17.10951100+2.12243
  • 250+16.04610250+1.99051
  • 500+15.40548500+1.91105
  • 1000+14.877821000+1.84559

库存:3544

LM5010MHX/NOPB
  •  国内价格 香港价格
  • 2500+12.556282500+1.55760
  • 5000+11.385785000+1.41240

库存:22500