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LMH6624, LMH6626
SNOSA42G – NOVEMBER 2002 – REVISED DECEMBER 2014
LMH6624 and LMH6626 Single/Dual Ultra Low Noise Wideband Operational Amplifier
1 Features
3 Description
•
The LMH6624 and LMH6626 devices offer wide
bandwidth (1.5 GHz for single, 1.3 GHz for dual) with
very low input noise (0.92 nV/√Hz, 2.3 pA/√Hz) and
ultra-low dc errors (100 μV VOS, ±0.1 μV/°C drift)
providing very precise operational amplifiers with
wide dynamic range. This enables the user to
achieve closed-loop gains of greater than 10, in both
inverting and non-inverting configurations.
1
•
•
•
•
•
•
•
•
•
•
•
VS = ±6 V, TA = 25°C, AV = 20 (Typical Values
Unless Specified)
Gain Bandwidth (LMH6624) 1.5 GHz
Input Voltage Noise 0.92 nV/√Hz
Input Offset Voltage (limit over temp) 700 µV
Slew Rate 350 V/μs
Slew Rate (AV = 10) 400 V/μs
HD2 at f = 10 MHz, RL = 100 Ω −63 dBc
HD3 at f = 10 MHz, RL = 100 Ω −80 dBc
Supply Voltage Range (Dual Supply) 2.5 V to 6 V
Supply Voltage Range (Single Supply) 5 V to 12 V
Improved Replacement for the CLC425
(LMH6624)
Stable for Closed Loop |AV| ≥ 10
2 Applications
•
•
•
•
•
•
•
Instrumentation Sense Amplifiers
Ultrasound Pre-amps
Magnetic Tape & Disk Pre-amps
Wide Band Active Filters
Professional Audio Systems
Opto-electronics
Medical Diagnostic Systems
The LMH6624 (single) and LMH6626 (dual)
traditional voltage feedback topology provide the
following benefits: balanced inputs, low offset voltage
and offset current, very low offset drift, 81dB open
loop gain, 95dB common mode rejection ratio, and
88dB power supply rejection ratio.
The LMH6624 and LMH6626 devices operate from
±2.5 V to ±6 V in dual supply mode and from 5 V to
12 V in single supply configuration.
LMH6624 is offered in SOT-23-5 and SOIC-8
packages. The LMH6626 is offered in SOIC-8 and
VSSOP-8 packages.
Device Information(1)
PART NUMBER
LMH6624
LMH6626
PACKAGE
BODY SIZE (NOM)
SOT-23 (5)
2.90 mm × 1.60 mm
SOIC (8)
4.90 mm × 3.91 mm
SOIC (8)
4.90 mm × 3.91 mm
VSSOP (8)
3.00 mm × 3.00 mm
(1) For all available packages, see the orderable addendum at
the end of the datasheet.
Voltage Noise vs. Frequency
1
An IMPORTANT NOTICE at the end of this data sheet addresses availability, warranty, changes, use in safety-critical applications,
intellectual property matters and other important disclaimers. PRODUCTION DATA.
LMH6624, LMH6626
SNOSA42G – NOVEMBER 2002 – REVISED DECEMBER 2014
www.ti.com
Table of Contents
1
2
3
4
5
6
7
Features ..................................................................
Applications ...........................................................
Description .............................................................
Revision History.....................................................
Pin Configuration and Functions .........................
Specifications.........................................................
1
1
1
2
3
4
6.1
6.2
6.3
6.4
6.5
6.6
6.7
4
4
4
4
5
7
9
Absolute Maximum Ratings ......................................
ESD Ratings..............................................................
Recommended Operating Conditions.......................
Thermal Information ..................................................
Electrical Characteristics ±2.5 V ..............................
Electrical Characteristics ±6 V .................................
Typical Characteristics ..............................................
Detailed Description ............................................ 17
7.1 Overview ................................................................. 17
7.2 Feature Description................................................. 17
7.3 Device Functional Modes........................................ 22
8
Application and Implementation ........................ 23
8.1 Application Information............................................ 23
8.2 Typical Application .................................................. 23
9 Power Supply Recommendations...................... 26
10 Layout................................................................... 26
10.1 Layout Guidelines ................................................. 26
10.2 Layout Example .................................................... 27
11 Device and Documentation Support ................. 28
11.1
11.2
11.3
11.4
11.5
Documentation Support ........................................
Related Links ........................................................
Trademarks ...........................................................
Electrostatic Discharge Caution ............................
Glossary ................................................................
28
28
28
28
28
12 Mechanical, Packaging, and Orderable
Information ........................................................... 28
4 Revision History
NOTE: Page numbers for previous revisions may differ from page numbers in the current version.
Changes from Revision F (March 2013) to Revision G
Page
•
Added, updated, or renamed the following sections: Device Information Table, Pin Configuration and Functions,
Application and Implementation; Power Supply Recommendations; Layout; Device and Documentation Support;
Mechanical, Packaging, and Ordering Information ............................................................................................................... 1
•
Added Input Current parameter in Absolute Maximum Ratings ............................................................................................ 4
•
Added Operating supply voltage (V+ - V-) parameter in Recommended Operating Conditions............................................ 4
•
Revised paragraph beginning with "As seen in ..." in Total Input Noise vs. Source Resistance ........................................ 19
•
Changed from 33.5 Ω to 26 Ω in Total Input Noise vs. Source Resistance......................................................................... 19
•
Changed from 6.43 kΩ to 3.1 kΩ in Total Input Noise vs. Source Resistance .................................................................... 19
Changes from Revision E (March 2013) to Revision F
Page
•
Changed layout of National Data Sheet to TI format ............................................................................................................. 1
•
Changed from 464 Ω to 283 Ω ............................................................................................................................................. 19
2
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Copyright © 2002–2014, Texas Instruments Incorporated
Product Folder Links: LMH6624 LMH6626
LMH6624, LMH6626
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SNOSA42G – NOVEMBER 2002 – REVISED DECEMBER 2014
5 Pin Configuration and Functions
5-Pin SOT-23 (LMH6624)
Package DBV
Top View
1
5
OUT
V
N/C
+
-IN
V
-
1
2
8
-
7
+
6
N/C
V
+
2
+IN
3
-
+
+IN
8-Pin SOIC Package D and VSSOP
(LMH6626)
Package D or DGK
Top View
8-Pin SOIC (LMH6624)
Package D
Top View
4
3
-IN
V
-
4
5
OUT
N/C
Pin Functions
PIN
NUMBER
NAME
LMH6624
LMH6626
I/O
DESCRIPTION
DBV
D
DGK or D
-IN
4
2
–
I
Inverting Input
+IN
3
3
–
I
Non-inverting Input
IN A-
–
–
2
I
Inverting Input Channel A
IN B-
–
–
6
I
Inverting Input Channel B
IN A+
–
–
3
I
Non-inverting Input Channel A
IN B+
–
–
5
I
Non-inverting Input Channel B
N/C
–
1, 5, 8
–
––
No Connection
OUT
1
6
–
O
Output
OUT A
–
–
1
O
Output Channel A
OUT B
–
–
7
O
Output Channel B
V-
2
4
4
I
Negative Supply
V+
5
7
8
I
Positive Supply
Copyright © 2002–2014, Texas Instruments Incorporated
Product Folder Links: LMH6624 LMH6626
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LMH6624, LMH6626
SNOSA42G – NOVEMBER 2002 – REVISED DECEMBER 2014
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6 Specifications
6.1 Absolute Maximum Ratings
over operating free-air temperature range (unless otherwise noted) (1)
MIN
VIN Differential
+
−
Supply voltage (V - V )
Voltage at Input pins
Junction temperature
(2)
V
13.2
V
V
±10
mA
Infrared or convection (20 sec.)
235
°C
Wave soldering (10 sec.)
260
°C
150
°C
150
°C
(2)
Storage temperature
(1)
UNIT
±1.2
V+ +0.5,
V− −0.5
Input Current
Soldering information
MAX
-65
Absolute maximum ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for
which the device is intended to be functional, but specific performance is not ensured. For ensured specifications and the test
conditions, see the Electrical Characteristics.
Applies to both single-supply and split-supply operation. Continuous short circuit operation at elevated ambient temperature can result in
exceeding the maximum allowed junction temperature of 150°C.
6.2 ESD Ratings
VALUE
V(ESD)
(1)
(2)
Electrostatic discharge
Human-body model (HBM), per ANSI/ESDA/JEDEC JS-001 (1)
±2000
Machine model (2)
±200
UNIT
V
Human body model, 1.5 kΩ in series with 100 pF. JEDEC document JEP155 states that 2000-V HBM allows safe manufacturing with a
standard ESD control process. Manufacturing with less than 2000-V HBM is possible with the necessary precautions. Pins listed as
±2000 V may actually have higher performance.
Machine Model, 0 Ω in series with 200 pF. JEDEC document JEP157 states that 200-V MM allows safe manufacturing with a standard
ESD control process.
6.3 Recommended Operating Conditions
over operating free-air temperature range (unless otherwise noted) (1)
Operating temperature
(2)
Operating supply voltage (V+ - V-)
(1)
(2)
MIN
MAX
UNIT
−40
+125
°C
±2.25
±6.3
V
Absolute maximum ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for
which the device is intended to be functional, but specific performance is not ensured. For ensured specifications and the test
conditions, see the Electrical Characteristics.
Applies to both single-supply and split-supply operation. Continuous short circuit operation at elevated ambient temperature can result in
exceeding the maximum allowed junction temperature of 150°C.
6.4 Thermal Information
LMH6624
THERMAL METRIC
RθJA
(1)
(2)
4
(1)
Junction-to-ambient thermal resistance (2)
LMH6626
DBV
D
DGK
D
5 PINS
8 PINS
8 PINS
8 PINS
265
166
235
166
UNIT
°C/W
For more information about traditional and new thermal metrics, see the IC Package Thermal Metrics application report, SPRA953.
The maximum power dissipation is a function of TJ(MAX), RθJA, and TA. The maximum allowable power dissipation at any ambient
temperature is PD = (TJ(MAX) - TA)/ RθJA . All numbers apply for packages soldered directly onto a PC board.
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LMH6624, LMH6626
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SNOSA42G – NOVEMBER 2002 – REVISED DECEMBER 2014
6.5 Electrical Characteristics ±2.5 V
Unless otherwise specified, all limits ensured at TA = 25°C, V+ = 2.5 V, V− = −2.5 V, VCM = 0 V, AV = +20, RF = 500 Ω,
RL = 100 Ω. See (1).
PARAMETER
TEST CONDITIONS
MIN (2)
TYP (3)
MAX (2)
UNIT
DYNAMIC PERFORMANCE
−3dB BW
fCL
VO = 400 mVPP (LMH6624)
90
VO = 400 mVPP (LMH6626)
80
VO = 2 VPP, AV = +20 (LMH6624)
300
VO = 2 VPP, AV = +20 (LMH6626)
290
VO = 2 VPP, AV = +10 (LMH6624)
360
MHz
SR
Slew rate (4)
VO = 2 VPP, AV = +10 (LMH6626)
340
tr
Rise time
VO = 400 mV Step, 10% to 90%
4.1
ns
tf
Fall time
VO = 400 mV Step, 10% to 90%
4.1
ns
ts
Settling time 0.1%
VO = 2 VPP (Step)
20
ns
V/μs
DISTORTION and NOISE RESPONSE
f = 1 MHz (LMH6624)
0.92
f = 1 MHz (LMH6626)
1.0
f = 1 MHz (LMH6624)
2.3
f = 1 MHz (LMH6626)
1.8
2nd harmonic distortion
fC = 10 MHz, VO = 1 VPP, RL 100 Ω
−60
dBc
3rd harmonic distortion
fC = 10 MHz, VO = 1 VPP, RL 100 Ω
−76
dBc
en
Input referred voltage noise
in
Input referred current noise
HD2
HD3
nV/√Hz
pA/√Hz
INPUT CHARACTERISTICS
VOS
IOS
IB
Input offset voltage
VCM = 0 V
Average drift (5)
VCM = 0 V
Input offset current
VCM = 0 V
Average drift (5)
VCM = 0 V
+0.95
μV/°C
±0.25
−1.5
-40°C ≤ TJ ≤ 125°C
−0.05
−2.0
+1.5
+2.0
2
13
mV
μA
nA/°C
+20
μA
Average drift (5)
VCM = 0 V
12
nA/°C
Common Mode
6.6
MΩ
Differential Mode
4.6
kΩ
Common Mode
0.9
Differential Mode
2.0
Input capacitance (6)
CMRR
Common mode rejection
ratio
(2)
(3)
(4)
(5)
(6)
+0.75
VCM = 0 V
CIN
(1)
−0.25
−0.95
Input bias current
Input resistance (6)
RIN
−0.75
-40°C ≤ TJ ≤ 125°C
-40°C ≤ TJ ≤ 125°C
+25
Input Referred, VCM = −0.5 to +1.9 V
87
Input Referred,
VCM = −0.5 to +1.75 V
85
-40°C ≤ TJ ≤ 125°C
pF
90
dB
Electrical table values apply only for factory testing conditions at the temperature indicated. Factory testing conditions result in very
limited self-heating of the device such that TJ = TA. No ensured specification of parametric performance is indicated in the electrical
tables under conditions of internal self-heating where TJ > TA. Absolute maximum ratings indicate junction temperature limits beyond
which the device may be permanently degraded, either mechanically or electrically.
All limits are specified by testing or statistical analysis.
Typical Values represent the most likely parametric norm.
Slew rate is the slowest of the rising and falling slew rates.
Average drift is determined by dividing the change in parameter at temperature extremes into the total temperature change.
Simulation results.
Copyright © 2002–2014, Texas Instruments Incorporated
Product Folder Links: LMH6624 LMH6626
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Electrical Characteristics ±2.5 V (continued)
Unless otherwise specified, all limits ensured at TA = 25°C, V+ = 2.5 V, V− = −2.5 V, VCM = 0 V, AV = +20, RF = 500 Ω,
RL = 100 Ω. See (1).
PARAMETER
TEST CONDITIONS
MIN (2)
TYP (3)
75
79
MAX (2)
UNIT
TRANSFER CHARACTERISTICS
(LMH6624)
RL = 100 Ω, VO = −1 V to +1 V
AVOL
Large signal voltage gain
(LMH6626)
RL = 100 Ω, VO = −1 V to +1 V
Xt
Crosstalk rejection
-40°C ≤ TJ ≤ 125°C
70
72
-40°C ≤ TJ ≤ 125°C
dB
79
67
−75
f = 1 MHz (LMH6626)
dB
OUTPUT CHARACTERISTICS
RL = 100 Ω
VO
Output swing
No Load
RO
Output impedance
Output short circuit current
(LMH6624)
Sinking to Ground
ΔVIN = −200 mV (7) (8)
(LMH6626)
Sourcing to Ground
ΔVIN = 200 mV (7) (8)
(LMH6626)
Sinking to Ground
ΔVIN = −200 mV (7) (8)
IOUT
Output current
-40°C ≤ TJ ≤ 125°C
±1.4
-40°C ≤ TJ ≤ 125°C
±1.5
±1.0
V
±1.7
±1.25
f ≤ 100 KHz
(LMH6624)
Sourcing to Ground
ΔVIN = 200 mV (7) (8)
ISC
±1.1
10
90
-40°C ≤ TJ ≤ 125°C
75
90
-40°C ≤ TJ ≤ 125°C
mA
120
50
60
-40°C ≤ TJ ≤ 125°C
145
75
60
-40°C ≤ TJ ≤ 125°C
mΩ
145
120
50
(LMH6624)
Sourcing, VO = +0.8 V
Sinking, VO = −0.8 V
100
(LMH6626)
Sourcing, VO = +0.8 V
Sinking, VO = −0.8 V
75
mA
POWER SUPPLY
PSRR
Power supply rejection ratio
IS
Supply current (per channel) No Load
(7)
(8)
6
VS = ±2.0 V to ±3.0 V
82
-40°C ≤ TJ ≤ 125°C
90
11.4
-40°C ≤ TJ ≤ 125°C
dB
80
16
18
mA
Applies to both single-supply and split-supply operation. Continuous short circuit operation at elevated ambient temperature can result in
exceeding the maximum allowed junction temperature of 150°C.
Short circuit test is a momentary test. Output short circuit duration is 1.5 ms.
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SNOSA42G – NOVEMBER 2002 – REVISED DECEMBER 2014
6.6 Electrical Characteristics ±6 V
Unless otherwise specified, all limits ensured at TA = 25°C, V+ = 6 V, V− = −6 V, VCM = 0 V, AV = +20, RF = 500 Ω,
RL = 100 Ω. See (1).
PARAMETER
TEST CONDITIONS
MIN (2)
TYP (3)
MAX (2)
UNIT
DYNAMIC PERFORMANCE
−3dB BW
fCL
VO = 400 mVPP (LMH6624)
95
VO = 400 mVPP (LMH6626)
85
VO = 2 VPP, AV = +20 (LMH6624)
350
VO = 2 VPP, AV = +20 (LMH6626)
320
VO = 2 VPP, AV = +10 (LMH6624)
400
MHz
SR
Slew rate (4)
VO = 2 VPP, AV = +10 (LMH6626)
360
tr
Rise time
VO = 400 mV Step, 10% to 90%
3.7
ns
tf
Fall time
VO = 400 mV Step, 10% to 90%
3.7
ns
ts
Settling time 0.1%
VO = 2 VPP (Step)
18
ns
V/μs
DISTORTION and NOISE RESPONSE
f = 1 MHz (LMH6624)
0.92
f = 1 MHz (LMH6626)
1.0
f = 1 MHz (LMH6624)
2.3
f = 1 MHz (LMH6626)
1.8
2nd harmonic distortion
fC = 10 MHz, VO = 1 VPP, RL = 100 Ω
−63
dBc
3rd harmonic distortion
fC = 10 MHz, VO = 1 VPP, RL = 100 Ω
−80
dBc
en
Input referred voltage noise
in
Input referred current noise
HD2
HD3
nV/√Hz
pA/√Hz
INPUT CHARACTERISTICS
VOS
Input offset voltage
VCM = 0 V
Average drift (5)
VCM = 0 V
(LMH6624)
VCM = 0 V
Input offset current
IOS
(LMH6626)
VCM = 0 V
Average drift
IB
(5)
+0.5
+0.7
μV/°C
±0.2
−1.1
-40°C ≤ TJ ≤ 125°C
−2.0
-40°C ≤ TJ ≤ 125°C
0.05
−2.5
−2.5
VCM = 0 V
1.1
2.5
0.1
mV
2.0
μA
2.5
0.7
13
nA/°C
+20
μA
VCM = 0 V
Average drift (5)
VCM = 0 V
12
nA/°C
Common Mode
6.6
MΩ
Differential Mode
4.6
kΩ
Common Mode
0.9
Differential Mode
2.0
Input resistance (6)
CIN
Input capacitance (6)
CMRR
Common mode rejection
ratio
(2)
(3)
(4)
(5)
(6)
±0.10
−0.7
Input bias current
RIN
(1)
−0.5
-40°C ≤ TJ ≤ 125°C
-40°C ≤ TJ ≤ 125°C
+25
Input Referred, VCM = −4.5 to +5.25 V
90
Input Referred,
VCM = −4.5 to +5.0 V
87
-40°C ≤ TJ ≤ 125°C
pF
95
dB
Electrical table values apply only for factory testing conditions at the temperature indicated. Factory testing conditions result in very
limited self-heating of the device such that TJ = TA. No ensured specification of parametric performance is indicated in the electrical
tables under conditions of internal self-heating where TJ > TA. Absolute maximum ratings indicate junction temperature limits beyond
which the device may be permanently degraded, either mechanically or electrically.
All limits are specified by testing or statistical analysis.
Typical Values represent the most likely parametric norm.
Slew rate is the slowest of the rising and falling slew rates.
Average drift is determined by dividing the change in parameter at temperature extremes into the total temperature change.
Simulation results.
Copyright © 2002–2014, Texas Instruments Incorporated
Product Folder Links: LMH6624 LMH6626
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Electrical Characteristics ±6 V (continued)
Unless otherwise specified, all limits ensured at TA = 25°C, V+ = 6 V, V− = −6 V, VCM = 0 V, AV = +20, RF = 500 Ω,
RL = 100 Ω. See (1).
PARAMETER
TEST CONDITIONS
MIN (2)
TYP (3)
77
81
MAX (2)
UNIT
TRANSFER CHARACTERISTICS
(LMH6624)
RL = 100 Ω, VO = −3 V to +3 V
AVOL
Large signal voltage gain
(LMH6626)
RL = 100 Ω, VO = −3 V to +3 V
Xt
Crosstalk rejection
-40°C ≤ TJ ≤ 125°C
72
74
-40°C ≤ TJ ≤ 125°C
dB
80
70
−75
f = 1MHz (LMH6626)
dB
OUTPUT CHARACTERISTICS
VO
-40°C ≤ TJ ≤ 125°C
±4.3
(LMH6624)
No Load
-40°C ≤ TJ ≤ 125°C
±4.65
Output swing
(LMH6626)
RL = 100 Ω
(LMH6626)
No Load
RO
Output impedance
Output short circuit current
IOUT
Output current
±4.8
±4.3
-40°C ≤ TJ ≤ 125°C
±4.8
-40°C ≤ TJ ≤ 125°C
(LMH6624)
Sinking to Ground
ΔVIN = −200 mV (7) (8)
±4.9
±5.2
V
±4.8
±4.2
±5.2
±4.65
f ≤ 100 KHz
(LMH6624)
Sourcing to Ground
ΔVIN = 200 mV (7) (8)
ISC
±4.4
(LMH6624)
RL = 100 Ω
10
100
-40°C ≤ TJ ≤ 125°C
85
100
-40°C ≤ TJ ≤ 125°C
(LMH6626)
Sourcing to Ground
ΔVIN = 200 mV (7) (8)
-40°C ≤ TJ ≤ 125°C
(LMH6626)
Sinking to Ground
ΔVIN = −200 mV (7) (8)
-40°C ≤ TJ ≤ 125°C
mΩ
156
156
85
65
mA
120
55
65
120
55
(LMH6624)
Sourcing, VO = +4.3 V
Sinking, VO = −4.3 V
100
(LMH6626)
Sourcing, VO = +4.3 V
Sinking, VO = −4.3 V
80
mA
POWER SUPPLY
PSRR
Power supply rejection ratio
IS
Supply current (per channel) No Load
(7)
(8)
8
VS = ±5.4 V to ±6.6 V
82
-40°C ≤ TJ ≤ 125°C
88
12
-40°C ≤ TJ ≤ 125°C
dB
80
16
18
mA
Applies to both single-supply and split-supply operation. Continuous short circuit operation at elevated ambient temperature can result in
exceeding the maximum allowed junction temperature of 150°C.
Short circuit test is a momentary test. Output short circuit duration is 1.5 ms.
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SNOSA42G – NOVEMBER 2002 – REVISED DECEMBER 2014
6.7 Typical Characteristics
Figure 1. Voltage Noise vs. Frequency
5
4
4
3
3
AV = -10
Normalized Gain (dB)
Normalized Gain (dB)
Figure 2. Current Noise vs. Frequency
5
2
AV = -20
1
0
-1
AV = -40
-2
AV = -60
-3
AV = -80
-4
AV = -10
2
1
AV = -20
0
-1
AV = -40
-2
AV = -60
-3
AV = -80
-4
AV = -100
-5
AV = -100
-5
1k
1M
100k
10k
10M
100M
1k
1G
10k
Frequency (Hz)
1M
10M
100M
1G
Frequency (Hz)
VS = ±2.5 V
VIN = 5 mVpp
RL = 100 Ω
VS = ±6V
VIN = 5 mVpp
RL = 100 Ω
Figure 3. Inverting Frequency Response
Figure 4. Inverting Frequency Response
5
5
4
4
3
3
2
AV = +10
1
0
AV = +200
-1
AV = +100
-2
AV = +40
-3
Normalized Gain (dB)
Normalized Gain (dB)
100k
2
AV = +10
1
0
AV = +200
-1
AV = +100
-2
AV = +40
-3
AV = +30
AV = +30
-4
-4
AV = +20
AV = +20
-5
-5
1k
10k
100k
1M
10M
100M
1G
1k
Frequency (Hz)
10k
100k
1M
10M
100M
1G
Frequency (Hz)
VS = ±2.5 V
RF = 500 Ω
VO = 2 Vpp
VS = ±6 V
RF = 500 Ω
VO = 2 Vpp
Figure 5. Non-Inverting Frequency Response
Figure 6. Non-Inverting Frequency Response
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Typical Characteristics (continued)
70
Gain (dB)
60
0
-40°C
-45
25°C
PHASE
-90
125°C
-40°C
50
-135
125°C
GAIN
40
-180
25°C
30
-225
20
-270
10
-315
0
100k
1M
10M
100M
Phase (°)
80
-360
1G
Frequency (Hz)
VS = ±2.5 V
VS = ±6V
RL = 100 Ω
Figure 7. Open Loop Frequency Response
Over Temperature
Figure 8. Open Loop Frequency Response
Over Temperature
5
5
33 pF
4
3
10 pF
2
1
5 pF
0
33 pF
4
15 pF
Normalized Gain (dB)
Normalized Gain (dB)
3
0 pF
-1
-2
1
5 pF
0
0 pF
-1
-2
-3
-3
-4
-4
-5
-5
1M
10M
1G
100M
1M
Frequency (Hz)
VS = ±2.5V
AV = +10
RF = 250 Ω
RISO = 10 Ω
RL = 1 kΩ||CL
VS = ±6V
AV = +10
RF = 250 Ω
5
4
4
5 pF
1
0
-1
10 pF
-2
RISO = 10 Ω
RL = 1 kΩ||CL
3
Normalized Gain (dB)
Normalized Gain (dB)
0 pF
2
1G
100M
Figure 10. Frequency Response with Cap. Loading
5
3
10M
Frequency (Hz)
Figure 9. Frequency Response with Cap. Loading
15 pF
-3
0 pF
2
5 pF
1
0
-1
10 pF
-2
15 pF
-3
33 pF
-4
33 pF
-4
-5
-5
1M
10M
100M
1G
1M
Frequency (Hz)
VS = ±2.5 V
AV = +10
RF = 250 Ω
RISO = 100 Ω
RL = 1 kΩ||CL
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10M
100M
1G
Frequency (Hz)
VS = ±6 V
AV = +10
RF = 250 Ω
Figure 11. Frequency Response with Cap. Loading
10
15 pF
10 pF
2
RISO = 10 Ω
RL = 1 kΩ||CL
Figure 12. Frequency Response with Cap. Loading
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Typical Characteristics (continued)
5
5
4
4
3
VIN = 20 mV
1
0
-1
-2
VIN = 200 mV
Normalized Gain (dB)
Normalized Gain (dB)
3
2
-3
2
0
-1
-2
VIN = 200 mV
-3
-4
-4
-5
-5
100k
VIN = 20 mV
1
1M
10M
100M
100k
1G
1M
Frequency (Hz)
VS = ±-2.5 V
AV = +10
RF = 500 Ω
5
4
4
3
3
2
1
0
VIN = 20 mV
-1
-2
VIN = 200 mV
Normalized Gain (dB)
Normalized Gain (dB)
1G
Figure 14. Non-Inverting Frequency Response Varying VIN
5
2
1
VIN = 20 mV
0
-1
-2
-3
-4
VIN = 200 mV
-4
-5
-5
100k
1M
10M
100M
1G
100k
1M
Frequency (Hz)
1G
Figure 16. Non-Inverting Frequency Response Varying VIN
(LMH6626)
5
4
3
3
2
1
0
VIN = 20 mV
-1
-2
VIN = 200 mV
Normalized Gain (dB)
5
4
2
1
VIN = 20 mV
0
-1
-2
-3
-4
VIN = 200 mV
-4
-5
100k
100M
VS = ±2.5 V
AV = +20
RF = 500 Ω
Figure 15. Non-Inverting Frequency Response Varying VIN
(LMH6624)
-3
10M
Frequency (Hz)
VS = ±2.5 V
AV = +20
RF = 500 Ω
Normalized Gain (dB)
100M
VS = ±6 V
AV = +10
RF = 500 Ω
Figure 13. Non-Inverting Frequency Response Varying VIN
-3
10M
Frequency (Hz)
-5
1M
10M
100M
1G
100k
Frequency (Hz)
1M
10M
100M
1G
Frequency (Hz)
VS = ±6 V
AV = +20
RF = 500 Ω
VS = ±6 V
AV = +20
RF = 500 Ω
Figure 17. Non-Inverting Frequency Response Varying VIN
(LMH6624)
Figure 18. Non-Inverting Frequency Response Varying VIN
(LMH6626)
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Typical Characteristics (continued)
160
140
-40°C
-40°C
140
120
120
ISOURCE (mA)
ISOURCE (mA)
100
125°C
100
25°C
80
60
80
25°C
125°C
60
40
40
20
20
0
0
0
0.5
1
1.5
0
0.5
1
VOUT (V)
VS = ±2.5 V
VS = ±2.5 V
Figure 19. Sourcing Current vs. VOUT (LMH6624)
Figure 20. Sourcing Current vs. VOUT (LMH6626)
180
140
-40°C
-40°C
160
120
25°C
140
125°C
100
120
ISOURCE (mA)
ISOURCE (mA)
1.5
VOUT (V)
25°C
100
80
60
80
125°C
60
40
40
20
20
0
0
0
1
2
3
VOUT (V)
4
5
0
1
2
3
5
VS = ±6 V
VS = ±6 V
Figure 21. Sourcing Current vs. VOUT (LMH6624)
Figure 22. Sourcing Current vs. VOUT (LMH6626)
50
150
100
0
125°C
125°C
50
VOS (PV)
VOS (PV)
-50
25°C
-100
-150
-200
0
25°C
-50
-100
-150
-40°C
-40°C
-250
-200
-250
-300
4
5
6
7
8
9
10
11
12
4
VSUPPLY (V)
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6
7
8
9
10
11
12
VSUPPLY (V)
Figure 23. VOS vs. VSUPPLY (LMH6624)
12
4
VOUT (V)
Figure 24. VOS vs. VSUPPLY (LMH6626)
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Typical Characteristics (continued)
140
160
-40°C
-40°C
140
120
120
125°C
25°C
100
125°C
ISINK (mA)
ISINK (mA)
100
80
60
40
25°C
80
60
40
20
20
0
0
-20
0
0.5
1
0
1.5
0.5
VOUT (V)
1
1.5
VOUT (V)
VS = ±2.5 V
VS = ±2.5V
Figure 25. Sinking Current vs. VOUT (LMH6624)
Figure 26. Sinking Current vs. VOUT (LMH6626)
180
140
-40°C
-40°C
160
120
140
ISINK (mA)
125°C
ISINK (mA)
100
120
25°C
100
80
125°C
80
25°C
60
60
40
40
20
20
0
0
0
1
2
3
4
5
0
1
VOUT (V)
3
4
5
VOUT (V)
VS = ±6 V
VS = ±6 V
Figure 27. Sinking Current vs. VOUT (LMH6624)
Figure 28. Sinking Current vs. VOUT (LMH6626)
0.2
0
0.15
-20
0.1
-40
Crosstalk (dB)
IOS (PA)
2
25°C
0.05
125°C
0
-60
VS = ±2.5 V
-80
-0.05
-100
-0.1
-120
-40°C
CH 1 OUTPUT
CH 2 OUTPUT
VS = ±6 V
-140
-0.15
4
5
6
7
8
9
10
11
1k
12
10k
100k
1M
10M
100M
Frequency (Hz)
VSUPPLY (V)
VIN = 60 mVpp
AV = +20
RL = 100 Ω
Figure 29. IOS vs. VSUPPLY
Figure 30. Crosstalk Rejection vs. Frequency (LMH6626)
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Typical Characteristics (continued)
0
0
-20
-20
HD2
-60
Distortion (dBc)
Distortion (dBc)
-40
VS = ±6 V, VO = 2 VPP
-80
HD3
-100
-40
VS = ±6 V,
-60
HD2
VO = 2 VPP
-80
VS = ±2.5 V,
VO = 1 VPP
-100
-120
VS = ±2.5 V, VO = 1 VPP
-140
100k
1M
10M
HD3
-120
100k
100M
1M
Frequency (Hz)
100M
10M
Frequency (Hz)
AV = +10
RL = 100 Ω
AV = +20
RL = 100 Ω
Figure 31. Distortion vs. Frequency
Figure 32. Distortion vs. Frequency
0
-50
HD2
VS = ±6 V
-20
VO = 2 VPP
-60
HD2
VS = ±2.5 V,
-60
Distortion (dBc)
Distortion (dBc)
-40
VO = 1 VPP
-80
-70
-80
HD3
-100
VS = ±2.5 V
-90
HD3
VO = 1 VPP
-120
VS = ±6 V, VO = 2 VPP
-100
-140
100k
1M
10M
0
100M
20
40
Frequency (Hz)
60
80
AV = +20
RL = 500 Ω
VS = ±6 V
VO = 2 Vpp
Figure 33. Distortion vs. Frequency
Figure 34. Distortion vs. Gain
0
0
-20
-20
HD2
-40
Distortion (dBc)
Distortion (dBc)
fC = 10 MHz
HD2
-60
-80
fC = 10 MHz
-40
-60
-80
fC = 1 MHz
-100
HD3
fC = 1 MHz
-100
HD3
-120
-120
0
0.5
1
1.5
2
2.5
3
3.5
4
0
VOUT (V)
4
6
8
10
12
AV = +20
VS = ±6 V
RL = 100 Ω
Figure 35. Distortion vs. VOUT Peak to Peak
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VOUT (VPP)
AV = +20
AV = ±2.5V
RL = 100 Ω
14
100
Gain (V/V)
Figure 36. Distortion vs. VOUT Peak to Peak
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200 mV/DIV
200 mV/DIV
Typical Characteristics (continued)
10 ns/DIV
10 ns/DIV
RL = 100 Ω
VS = ±2.5 V
VO = 1 Vpp
AV = +10
RL = 100 Ω
VS = ±6 V
VO = 1 Vpp
AV = +20
Figure 38. Non-Inverting Large Signal Pulse Response
50 mV/DIV
100 mV/DIV
Figure 37. Non-Inverting Large Signal Pulse Response
10 ns/DIV
10 ns/DIV
RL = 100 Ω
VS = ±2.5 V
VO = 200 mv
AV = +10
Figure 39. Non-Inverting Small Signal Pulse Response
Figure 40. Non-Inverting Small Signal Pulse Response
0
0
+PSRR, AV +10
-10
-20
-20
+PSRR, AV +20
-50
-PSRR, AV +20
-70
PSRR (dB)
-40
-60
+PSRR, AV = +10
-40
-30
PSRR (dB)
RL = 100 Ω
VS = ±6 V
VO = 500 mv
AV = +20
-60 +PSRR, AV = +20
-80
-PSRR, AV = +10
-100
-80
-120
-90
-PSRR, AV = +20
-PSRR, AV +10
-100
1k
10k
100k
1M
10M
100M
1G
-140
1k
Frequency (Hz)
10k
100k
1M
10M
100M
1G
Frequency (Hz)
VS = ±2.5 V
VS = ±6 V
Figure 41. PSRR vs. Frequency
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Figure 42. PSRR vs. Frequency
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0
0
-10
-10
-20
-20
-30
-30
CMRR (dB)
CMRR (dB)
Typical Characteristics (continued)
-40
AV = +10
-50
-60
-40
-50
AV = +10
-60
-70
-70
AV = +20
-80
AV = +20
-80
-90
-90
1k
1M
100k
10k
10M
100M
1k
100k
10k
Frequency (Hz)
VS = ±2.5V
VIN = 5 mVpp
5
RF = 2 k:
RF = 1.5 k:
RF = 1.5 k:
3
RF = 1 k:
RF = 750 :
1
0
-1
RF = 2 k:
4
Normalized Gain (dB)
Normalized Gain (dB)
3
RF = 511 :
-2
RF = 1 k:
2
1
RF = 750 :
0
-1
RF = 511 :
-2
-3
-3
-4
-4
-5
10M
-5
100M
1G
10M
VS = ±2.5 V
AV = +10
RL = 100 Ω
1G
VS = ±6 V
AV = +10 V
RL = 100 Ω
Figure 45. Amplifier Peaking with Varying RF
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100M
Frequency (Hz)
Frequency (Hz)
16
100M
Figure 44. Input Referred CMRR vs. Frequency
5
2
10M
VS = ±6 V
VIN = 5 mVpp
Figure 43. Input Referred CMRR vs. Frequency
4
1M
Frequency (Hz)
Figure 46. Amplifier Peaking with Varying RF
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7 Detailed Description
7.1 Overview
The LMH6624 and LMH6626 devices are very wide gain bandwidth, ultra low noise voltage feedback operational
amplifiers. Their excellent performances enable applications such as medical diagnostic ultrasound, magnetic
tape & disk storage and fiber-optics to achieve maximum high frequency signal-to-noise ratios. The set of
characteristic plots in Typical Characteristics illustrates many of the performance trade-offs. The following
discussion will demonstrate the proper selection of external components to achieve optimum system
performance.
7.2 Feature Description
7.2.1 Bias Current Cancellation
To cancel the bias current errors of the non-inverting configuration, the parallel combination of the gain setting
(Rg) and feedback (Rf) resistors should equal the equivalent source resistance (Rseq) as defined in Figure 47.
Combining this constraint with the non-inverting gain equation also seen in Figure 47, allows both Rf and Rg to
be determined explicitly from the following equations:
Rf = AVRseq
Rg = Rf/(AV-1)
(1)
(2)
When driven from a 0-Ω source, such as the output of an op amp, the non-inverting input of the LMH6624 and
LMH6626 should be isolated with at least a 25-Ω series resistor.
As seen in Figure 48, bias current cancellation is accomplished for the inverting configuration by placing a
resistor (Rb) on the non-inverting input equal in value to the resistance seen by the inverting input (Rf||(Rg+Rs)).
Rb should to be no less than 25 Ω for optimum LMH6624 and LMH6626 performance. A shunt capacitor can
minimize the additional noise of Rb.
Figure 47. Non-Inverting Amplifier Configuration
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Feature Description (continued)
Figure 48. Inverting Amplifier Configuration
7.2.2 Total Input Noise vs. Source Resistance
To determine maximum signal-to-noise ratios from the LMH6624 and LMH6626, an understanding of the
interaction between the amplifier’s intrinsic noise sources and the noise arising from its external resistors is
necessary.
Figure 49 describes the noise model for the non-inverting amplifier configuration showing all noise sources. In
addition to the intrinsic input voltage noise (en) and current noise (in = in+ = in−) source, there is also thermal
voltage noise (et = √(4KTR)) associated with each of the external resistors. Equation 3 provides the general form
for total equivalent input voltage noise density (eni). Equation 4 is a simplification of Equation 3 that assumes
Rf||Rg = Rseq for bias current cancellation. Figure 50 illustrates the equivalent noise model using this assumption.
Figure 51 is a plot of eni against equivalent source resistance (Rseq) with all of the contributing voltage noise
sources of Equation 4. This plot gives the expected eni for a given (Rseq) which assumes Rf||Rg = Rseq for bias
current cancellation. The total equivalent output voltage noise (eno) is eni*AV.
Figure 49. Non-Inverting Amplifier Noise Model
(3)
18
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Feature Description (continued)
Figure 50. Noise Model with Rf||Rg = Rseq
(4)
As seen in Figure 51, eni is dominated by the intrinsic voltage noise (en) of the amplifier for equivalent source
resistances below 26 Ω. Between 26 Ω and 3.1 kΩ, eni is dominated by the thermal noise (et = √(4kT(2Rseq)) of
the equivalent source resistance Rseq. Above 3.1 kΩ, eni is dominated by the amplifier’s current noise (in = √2
inRseq). When Rseq = 283 Ω (that is, Rseq = en/√2 in) the contribution from voltage noise and current noise of
LMH6624 and LMH6626 is equal. For example, configured with a gain of +20V/V giving a −3 dB of 90 MHz and
driven from Rseq = Rf || Rg = 25 Ω (eni = 1.3 nV√Hz from Figure 51), the LMH6624 produces a total output noise
voltage (eni × 20 V/V × √(1.57 × 90 MHz)) of 309 μVrms.
VOLTAGE NOISE DENSITY (nV/ Hz)
100
et
10
eni
en
1
in
0.1
10
100
1k
10k
100k
RSEQ (:)
Figure 51. Voltage Noise Density vs. Source Resistance
If bias current cancellation is not a requirement, then Rf || Rg need not equal Rseq. In this case, according to
Equation 3, Rf || Rg should be as low as possible to minimize noise. Results similar to Equation 3 are obtained
for the inverting configuration of Figure 48 if Rseq is replaced by Rb and Rg is replaced by Rg + Rs. With these
substitutions, Equation 3 will yield an eni referred to the non-inverting input. Referring eni to the inverting input is
easily accomplished by multiplying eni by the ratio of non-inverting to inverting gains.
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Feature Description (continued)
7.2.3 Noise Figure
Noise Figure (NF) is a measure of the noise degradation caused by an amplifier.
(5)
The Noise Figure formula is shown in Equation 5. The addition of a terminating resistor RT, reduces the external
thermal noise but increases the resulting NF. The NF is increased because RT reduces the input signal amplitude
thus reducing the input SNR.
2
2
2 2
en + in (RSeq + (Rf||Rg) ) + 4KT (RSeq + (Rf||Rg))
NF = 10 LOG
4KT (RSeq + (Rf||Rg))
(6)
The noise figure is related to the equivalent source resistance (Rseq) and the parallel combination of Rf and Rg.
To minimize "Noise Figure":
• Minimize Rf || Rg
• Choose the Optimum RS (ROPT)
ROPT is the point at which the NF curve reaches a minimum and is approximated by:
ROPT »
en
in
(7)
7.2.4 Low Noise Integrator
The LMH6624 and LMH6626 devices implement a deBoo integrator shown in Figure 52. Positive feedback
maintains integration linearity. The low input offset voltage of the LMH6624 and LMH6626 devices and matched
inputs allow bias current cancellation and provide for very precise integration. Keeping RG and RS low helps
maintain dynamic stability.
VO #VIN
KO
KO = 1 +
;
sRSC
RF
RG
RB
VO
RS
+
VIN
C
R
-
50:
50:
RF
RF = RB
RG
RG = RS||R
Figure 52. Low Noise Integrator
20
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Feature Description (continued)
7.2.5 High-gain Sallen-key Active Filters
The LMH6624 and LMH6626 devices are well suited for high gain Sallen-Key type of active filters. Figure 53
shows the 2nd order Sallen-Key low pass filter topology. Using component predistortion methods discussed in
Application Note OA-21, Component Pre-Distortion for Sallen Key Filters (SNOA369) will enable the proper
selection of components for these high-frequency filters.
C1
R1
R2
+
C2
RF
RG
Figure 53. Sallen-Key Active Filter Topology
7.2.6 Low Noise Magnetic Media Equalizer
The LMH6624 and LMH6626 devices implement a high-performance low noise equalizer for such application as
magnetic tape channels as shown in Figure 54. The circuit combines an integrator with a bandpass filter to
produce the low noise equalization. The circuit’s simulated frequency response is illustrated in Figure 55.
Figure 54. Low Noise Magnetic Media Equalizer
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Feature Description (continued)
Figure 55. Equalizer Frequency Response
7.3 Device Functional Modes
7.3.1 Single Supply Operation
The LMH6624 and LMH6626 devices can be operated with single power supply as shown in Figure 56. Both the
input and output are capacitively coupled to set the DC operating point.
Figure 56. Single Supply Operation
22
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8 Application and Implementation
NOTE
Information in the following applications sections is not part of the TI component
specification, and TI does not warrant its accuracy or completeness. TI’s customers are
responsible for determining suitability of components for their purposes. Customers should
validate and test their design implementation to confirm system functionality.
8.1 Application Information
A Transimpedance amplifier is used to convert the small output current of a photodiode to a voltage, while
maintaining a near constant voltage across the photodiode to minimize non-linearity. Extracting the small signal
requires high gain and a low noise amplifier, and therefore, the LMH6624 and LMH6626 devices are ideal for
such an application in order to maximize SNR. Furthermore, because of the large gain (RF value) needed, the
device used must be high speed so that even with high noise gain (due to the interaction of the feedback resistor
and photodiode capacitance), bandwidth is not heavily impacted.
Figure 47 implements a high-speed, single supply, low-noise Transimpedance amplifier commonly used with
photo-diodes. The transimpedance gain is set by RF.
8.2 Typical Application
CF
1.1 pF
5 VDC
D1
CD = 10 pF
RF
1.2 k Ω
ID
5 VDC
–
R2
2k
5 VDC
LMH6624
+
RL
500 Ω
C1
0.1 µF
R1
3k
VOUT = 3 VDC - 1200 × I D
Figure 57. LMH6624 Application Schematic
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Product Folder Links: LMH6624 LMH6626
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Typical Application (continued)
8.2.1 Design Requirements
Figure 58 shows the Noise Gain (NG) and transfer function (I-V Gain). As with most Transimpedance amplifiers,
it is required to compensate for the additional phase lag (Noise Gain zero at fZ) created by the total input
capacitance: CD (diode capacitance) + CCM (LMH6624 CM input capacitance) + CDIFF (LMH6624 DIFF input
capacitance) looking into RF. This is accomplished by placing CF across RF to create enough phase lead (Noise
Gain pole at fP) to stabilize the loop.
OP AMP OPEN
LOOP GAIN
GAIN (dB)
I-V GAIN (:)
NOISE GAIN (NG)
1 + sRF (CIN + CF)
1 + sRFCF
1+
CIN
CF
0 dB
FREQUENCY
fz #
1
2SRFCIN
fP =
1
GBWP
2SRFCF
Figure 58. Transimpedance Amplifier Noise Gain and Transfer Function
8.2.2 Detailed Design Procedure
The optimum value of CF is given by Equation 8 resulting in the I-V -3dB bandwidth shown in Equation 9, or
around 124 MHz in this case, assuming GBWP = 1.5 GHz, CCM (LMH6624 CM input capacitance) = 0.9 pF, and
CDIFF (LMH6624 DIFF input capacitance) = 2 pF. This CF value is a “starting point” and CF needs to be tuned for
the particular application as it is often less than 1 pF and thus is easily affected by board parasitics.
Optimum CF Value:
CF =
CIN
2S(GBWP)RF
(8)
Resulting -3dB Bandwidth:
f - 3 dB #
GBWP
2 S R F C IN
(9)
Equation 10 provides the total input current noise density (ini) equation for the basic Transimpedance
configuration and is plotted against feedback resistance (RF) showing all contributing noise sources in Figure 59.
The plot indicates the expected total equivalent input current noise density (ini) for a given feedback resistance
(RF). This is depicted in the schematic of Figure 60 where total equivalent current noise density (ini) is shown at
the input of a noiseless amplifier and noiseless feedback resistor (RF). The total equivalent output voltage noise
density (eno) is ini*RF. Noise Equation for Transimpedance Amplifier:
(10)
24
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SNOSA42G – NOVEMBER 2002 – REVISED DECEMBER 2014
Typical Application (continued)
16
Current Noise Density (pA/ Hz)
14
ini
12
10
8
it
en/RF
6
in
4
2
0
100
1k
10k
Rf (:)
Figure 59. Current Noise Density vs. Feedback Resistance
+5VDC
D1
RF
(Noiseless)
CD = 10 pF
ID
ini
Noiseless Op Amp
Figure 60. Transimpedance Amplifier Equivalent Input Source Mode
From Figure 61, it is clear that with the LMH6624 extremely low-noise characteristics, for RF < 3 kΩ, the noise
performance is entirely dominated by RF thermal noise. Only above this RF threshold, the input noise current (in)
of LMH6624 becomes a factor and at no RF setting does the LMH6624 input noise voltage play a significant role.
This noise analysis has ignored the possible noise gain increase, due to photo-diode capacitance, at higher
frequencies.
8.2.3 Application Curve
CURRENT NOISE DENSITY (pA/ Hz)
16
14
ini
12
it
10
8
en/RF
6
4
2
in
0
100
1k
10k
FEEDBACK RESISTANCE, RF (:)
Figure 61. Current Noise Density vs. Feedback Resistance
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9 Power Supply Recommendations
The LMH6624 and LMH6626 devices can operate off a single supply or with dual supplies as long as the input
CM voltage range (CMIR) has the required headroom to either supply rail. Supplies should be decoupled with
low inductance, often ceramic, capacitors to ground less than 0.5 inches from the device pins. The use of ground
plane is recommended, and as in most high speed devices, it is advisable to remove ground plane close to
device sensitive pins such as the inputs.
10 Layout
10.1 Layout Guidelines
TI suggests the copper patterns on the evaluation boards shown in Figure 62 and Figure 63 as a guide for high
frequency layout. These boards are also useful as an aid in device testing and characterization. As is the case
with all high-speed amplifiers, accepted-practice RF design technique on the PCB layout is mandatory.
Generally, a good high frequency layout exhibits a separation of power supply and ground traces from the
inverting input and output pins as shown in Figure 62. Parasitic capacitances between these nodes and ground
may cause frequency response peaking and possible circuit oscillations. See Application Note OA-15, Frequent
Faux Pas in Applying Wideband Current Feedback Amplifiers (SNOA367) for more information. Use high quality
chip capacitors with values in the range of 1000 pF to 0.1 µF for power supply bypassing as shown in Figure 62.
One terminal of each chip capacitor is connected to the ground plane and the other terminal is connected to a
point that is as close as possible to each supply pin as allowed by the manufacturer’s design rules. In addition,
connect a tantalum capacitor with a value between 4.7 μF and 10 μF in parallel with the chip capacitor. Signal
lines connecting the feedback and gain resistors should be as short as possible to minimize inductance and
microstrip line effect as shown in Figure 63. Place input and output termination resistors as close as possible to
the input/output pins. Traces greater than 1 inch in length should be impedance matched to the corresponding
load termination.
Symmetry between the positive and negative paths in the layout of differential circuitry should be maintained to
minimize the imbalance of amplitude and phase of the differential signal.
Component value selection is another important parameter in working with high speed and high performance
amplifiers. Choosing external resistors that are large in value compared to the value of other critical components
will affect the closed loop behavior of the stage because of the interaction of these resistors with parasitic
capacitances. These parasitic capacitors could either be inherent to the device or be a by-product of the board
layout and component placement. Moreover, a large resistor will also add more thermal noise to the signal path.
Either way, keeping the resistor values low will diminish this interaction. On the other hand, choosing very low
value resistors could load down nodes and will contribute to higher overall power dissipation and high distortion.
26
DEVICE
PACKAGE
EVALUATION BOARD PART NUMBER
LMH6624MF
SOT-23–5
LMH730216
LMH6624MA
SOIC-8
LMH730227
LMH6626MA
SOIC-8
LMH730036
LMH6626MM
VSSOP-8
LMH730123
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LMH6624, LMH6626
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SNOSA42G – NOVEMBER 2002 – REVISED DECEMBER 2014
10.2 Layout Example
Figure 62. LMH6624 and LMH6626
EVM Board Layout Example
Figure 63. LMH6624 and LMH6626
EVM Board Layout Example
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Product Folder Links: LMH6624 LMH6626
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11 Device and Documentation Support
11.1 Documentation Support
11.1.1 Related Documentation
• Absolute Maximum Ratings for Soldering (SNOA549)
• Frequent Faux Pas in Applying Wideband Current Feedback Amplifiers, Application Note OA-15 (SNOA367)
• Semiconductor and IC Package Thermal Metrics (SPRA953)
11.2 Related Links
The table below lists quick access links. Categories include technical documents, support and community
resources, tools and software, and quick access to sample or buy.
Table 1. Related Links
PARTS
PRODUCT FOLDER
SAMPLE & BUY
TECHNICAL
DOCUMENTS
TOOLS &
SOFTWARE
SUPPORT &
COMMUNITY
LMH6624
Click here
Click here
Click here
Click here
Click here
LMH6626
Click here
Click here
Click here
Click here
Click here
11.3 Trademarks
All trademarks are the property of their respective owners.
11.4 Electrostatic Discharge Caution
These devices have limited built-in ESD protection. The leads should be shorted together or the device placed in conductive foam
during storage or handling to prevent electrostatic damage to the MOS gates.
11.5 Glossary
SLYZ022 — TI Glossary.
This glossary lists and explains terms, acronyms, and definitions.
12 Mechanical, Packaging, and Orderable Information
The following pages include mechanical, packaging, and orderable information. This information is the most
current data available for the designated devices. This data is subject to change without notice and revision of
this document. For browser-based versions of this data sheet, refer to the left-hand navigation.
28
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PACKAGE OPTION ADDENDUM
www.ti.com
30-Sep-2021
PACKAGING INFORMATION
Orderable Device
Status
(1)
Package Type Package Pins Package
Drawing
Qty
Eco Plan
(2)
Lead finish/
Ball material
MSL Peak Temp
Op Temp (°C)
Device Marking
(3)
(4/5)
(6)
LMH6624MA
NRND
SOIC
D
8
95
Non-RoHS
& Green
Call TI
Level-1-235C-UNLIM
-40 to 125
LMH66
24MA
LMH6624MA/NOPB
ACTIVE
SOIC
D
8
95
RoHS & Green
SN
Level-1-260C-UNLIM
-40 to 125
LMH66
24MA
LMH6624MAX/NOPB
ACTIVE
SOIC
D
8
2500
RoHS & Green
SN
Level-1-260C-UNLIM
-40 to 125
LMH66
24MA
LMH6624MF
NRND
SOT-23
DBV
5
1000
Non-RoHS
& Green
Call TI
Level-1-260C-UNLIM
-40 to 125
A94A
LMH6624MF/NOPB
ACTIVE
SOT-23
DBV
5
1000
RoHS & Green
SN
Level-1-260C-UNLIM
-40 to 125
A94A
LMH6624MFX/NOPB
ACTIVE
SOT-23
DBV
5
3000
RoHS & Green
SN
Level-1-260C-UNLIM
-40 to 125
A94A
LMH6626MA/NOPB
ACTIVE
SOIC
D
8
95
RoHS & Green
SN
Level-1-260C-UNLIM
-40 to 125
LMH66
26MA
LMH6626MAX/NOPB
ACTIVE
SOIC
D
8
2500
RoHS & Green
SN
Level-1-260C-UNLIM
-40 to 125
LMH66
26MA
LMH6626MM/NOPB
ACTIVE
VSSOP
DGK
8
1000
RoHS & Green
SN
Level-1-260C-UNLIM
-40 to 125
A98A
(1)
The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2)
RoHS: TI defines "RoHS" to mean semiconductor products that are compliant with the current EU RoHS requirements for all 10 RoHS substances, including the requirement that RoHS substance
do not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, "RoHS" products are suitable for use in specified lead-free processes. TI may
reference these types of products as "Pb-Free".
RoHS Exempt: TI defines "RoHS Exempt" to mean products that contain lead but are compliant with EU RoHS pursuant to a specific EU RoHS exemption.
Green: TI defines "Green" to mean the content of Chlorine (Cl) and Bromine (Br) based flame retardants meet JS709B low halogen requirements of
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