TL7660
CMOS VOLTAGE CONVERTER
www.ti.com
SCAS794 – JUNE 2006
FEATURES
APPLICATIONS
•
•
•
•
•
•
•
•
•
•
Simple Voltage Conversion, Including
– Negative Converter
– Voltage Doubler
Wide Operating Range…1.5 V to 10 V
Requires Only Two External (Noncritical)
Capacitors
No External Diode Over Full Temperature and
Voltage Range
Typical Open-Circuit Voltage Conversion
Efficiency…99.9%
Typical Power Efficiency…98%
Full Testing at 3 V
On-Board Negative Supplies
Data-Acquisition Systems
Portable Electronics
D, DGK, OR P PACKAGE
(TOP VIEW)
NC
CAP+
GND
CAP−
1
8
2
7
3
6
4
5
VCC
OSC
LV
VOUT
NC − No internal connection
DESCRIPTION/ORDERING INFORMATION
The TL7660 is a CMOS switched-capacitor voltage converter that perform supply-voltage conversions from
positive to negative. With only two noncritical external capacitors needed for the charge pump and charge
reservoir functions, an input voltage within the range from 1.5 V to 10 V is converted to a complementary
negative output voltage of –1.5 V to –10 V. The device can also be connected as a voltage doubler to generate
output voltages up to 18.6 V with a 10-V input.
The basic building blocks of the IC include a linear regulator, an RC oscillator, a voltage-level translator, and four
power MOS switches. To ensure latch-up-free operation, the circuitry automatically senses the most negative
voltage in the device and ensures that the N-channel switch source-substrate junctions are not forward biased.
The oscillator frequency runs at a nominal 10 kHz (for VCC = 5 V), but that frequency can be decreased by
adding an external capacitor to the oscillator (OSC) terminal or increased by overdriving OSC with an external
clock.
For low-voltage operation (VIN < 3.5 V), LV should be tied to GND to bypass the internal series regulator. Above
3.5 V, LV should be left floating to prevent device latchup.
The TL7660C is characterized for operation over a free-air temperature range of –40°C to 85°C. The TL7660I is
characterized for operation over a free-air temperature range of –40°C to 125°C.
ORDERING INFORMATION
PACKAGE (1)
TA
MSOP/VSSOP – DGK
–40°C to 85°C
PDIP – P
SOIC – D
MSOP/VSSOP – DGK
–40°C to 125°C
PDIP – P
SOIC – D
(1)
(2)
ORDERABLE PART NUMBER
Reel of 250
TL7660CDGKT
Reel of 2500
TL7660CDGKR
Tube of 50
TL7660CP
Tube of 75
TL7660CD
Reel of 2500
TL7660CDR
Reel of 250
TL7660IDGKT
Reel of 2500
TL7660IDGKR
Tube of 50
TL7660IP
Tube of 75
TL7660ID
Reel of 2500
TL7660IDR
TOP-SIDE MARKING (2)
TM_
TL7660CP
7660C
TN_
TL7660IP
7660I
Package drawings, standard packing quantities, thermal data, symbolization, and PCB design guidelines are available at
www.ti.com/sc/package.
DGK: The actual top-side marking has one additional character that indicates the assembly/test site.
Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of Texas
Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet.
PRODUCTION DATA information is current as of publication date.
Products conform to specifications per the terms of the Texas
Instruments standard warranty. Production processing does not
necessarily include testing of all parameters.
Copyright © 2006, Texas Instruments Incorporated
TL7660
CMOS VOLTAGE CONVERTER
www.ti.com
SCAS794 – JUNE 2006
FUNCTIONAL BLOCK DIAGRAM
VCC
CAP+
RC
Oscillator
OSC
Voltage-Level
Translator
¸2
CAP−
LV
VOUT
Voltage
Regulator
Logic
Network
Absolute Maximum Ratings (1)
over operating free-air temperature range (unless otherwise noted)
MIN
VCC
Supply voltage
TL7660
VI
OSC and LV input voltage range (2)
ILV
Current into LV (2)
VCC > 3.5 V
tOS
Output short-circuit duration
VSUPPLY ± 5.5 V
θJA
Package thermal impedance (3) (4)
Junction temperature
Storage temperature range
(1)
(2)
(3)
(4)
V
–0.3
VCC + 0.3
VCC > 5.5 V
VCC – 5.5
VCC + 0.3
20
V
µA
Continuous
97
DGK package
172
P package
Tstg
UNIT
10.5
VCC < 5.5 V
D package
TJ
MAX
°C/W
85
–55
150
°C
150
°C
Stresses beyond those listed under "absolute maximum ratings" may cause permanent damage to the device. These are stress ratings
only, and functional operation of the device at these or any other conditions beyond those indicated under "recommended operating
conditions" is not implied. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability.
Connecting any input terminal to voltages greater than VCC or less than GND may cause destructive latchup. It is recommended that no
inputs from sources operating from external supplies be applied prior to power up of the TL7660.
Maximum power dissipation is a function of TJ(max), θJA, and TA. The maximum allowable power dissipation at any allowable ambient
temperature is PD = (TJ(max) – TA)/θJA. Operating at the absolute maximum TJ of 150°C can affect reliability.
The package thermal impedance is calculated in accordance with JESD 51-7.
Recommended Operating Conditions
VCC
TA
2
Supply voltage
Operating free-air temperature
MIN
MAX
TL7660
1.5
10
TL7660C
–40
85
TL7660I
–40
125
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UNIT
V
°C
TL7660
CMOS VOLTAGE CONVERTER
www.ti.com
SCAS794 – JUNE 2006
Electrical Characteristics
VCC = 5 V, COSC = 0, LV = Open, TA = 25°C (unless otherwise noted) (see Figure 1)
PARAMETER
TEST CONDITIONS
TA (1)
MIN
25°C
TYP
MAX
45
110
UNIT
ICC
Supply current
RL = ∞
VCC,LOW
Supply voltage range (low)
RL = 10 kΩ, LV = GND
Full range
1.5
3.5
V
VCC,HIGH
Supply voltage range (high)
RL = 10 kΩ, LV Open
Full range
3
10
V
–40°C to 85°C
120
–40°C to 125°C
135
25°C
IO = 20 mA
ROUT
Output source resistance
VCC = 2 V, IO = 3 mA, LV = GND
45
Oscillator frequency
ηPOWER
Power efficiency
RL = 5 kΩ
ηVOUT
Voltage conversion efficiency
RL = ∞
ZOSC
Oscillator impedance
85
–40°C to 125°C
135
25°C
125
–40°C to 85°C
200
(1)
10
25°C
96
–40°C to 125°C
95
25°C
99
–40°C to 125°C
99
25°C
VCC = 5 V
Ω
250
25°C
VCC = 2 V
70
–40°C to 85°C
–40°C to 125°C
fOSC
µA
kHz
98
%
99.9
%
1
MΩ
100
kΩ
Full range is –40°C to 85°C for the TL7660C and –40°C to 125°C for the TL7660I.
Electrical Characteristics
VCC = 3 V, COSC = 0, LV = GND, (unless otherwise noted) (see Figure 1)
PARAMETER
TEST CONDITIONS
TA
MIN
25°C
Supply current (1)
ICC
RL = ∞
Output source resistance
IO = 10 mA
fOSC
Oscillator frequency
COSC = 0
ηPOWER
Power efficiency
RL = 5 kΩ
ηVOUT
Voltage conversion efficiency
RL = ∞
(1)
MAX
24
50
–40°C to 85°C
60
–40°C to 125°C
75
25°C
ROUT
TYP
60
110
–40°C to 125°C
120
5
–40°C to 125°C
3
25°C
96
–40°C to 125°C
95
25°C
99
–40°C to 125°C
99
9
98
µA
100
–40°C to 85°C
25°C
UNIT
Ω
kHz
%
%
Derate linearly above 50°C by 5.5 mW/°C.
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CMOS VOLTAGE CONVERTER
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SCAS794 – JUNE 2006
TYPICAL CHARACTERISTICS
OSCILLATOR FREQUENCY
vs
OSCILLATOR CAPACITANCE
OSCILLATOR FREQUENCY
vs
TEMPERATURE
10
21
VCC = 5 V
TA = 25°C
f OSC – Oscillator Frequency – kHz
f OSC – Oscillator Frequency – kHz
9
8
7
6
5
4
3
2
1
10
100
17
15
VCC = 10 V
13
11
VCC = 5 V
9
7
5
-40 -25 -10 5
0
1
19
1000
20 35 50 65 80 95 110 125
COSC – Oscillator Capacitance – pF
TA – Free-Air Temperature – °C
150
140
130
120
110
100
VCC = 2 V
90
IO = 3 mA
80
70
60
50
40
30
20
10
0
-40 -25 -10 5
SUPPLY VOLTAGE
vs
TEMPERATURE
10
9
8
VCC – Supply Voltage – V
ROUT – Output Source Resistance –
Ω
OUTPUT RESISTANCE
vs
TEMPERATURE
VCC = 5 V
IO = 20 mA
7
5
4
3
VCC = 10 V
2
IO = 20 mA
1
20 35 50 65 80 95 11 12
0 5
0
-40 -25 -10
TA – Free-Air Temperature – °C
4
Supply Voltage Range
(No Diode Required)
6
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5
20
35 50
65
80
TA – Free-Air Temperature – °C
95 110 125
TL7660
CMOS VOLTAGE CONVERTER
www.ti.com
SCAS794 – JUNE 2006
TYPICAL CHARACTERISTICS (continued)
OUTPUT RESISTANCE
vs
SUPPLY VOLTAGE
OUTPUT RESISTANCE
vs
OSCILLATOR FREQUENCY
600
VCC = 5 V
550
150
TA = 25°C
500
125
Output Resistance – W
Ω
ROUT – Output Source Resistance – Ω
175
TA = 125°C
100
TA = 25°C
75
TA = –40°C
50
25
IO = 10 mA
450
400
350
COSC = 1 µF
300
COSC = 10 µF
250
COSC = 100 µF
200
150
100
50
0
0
1
2
3
4
5
6
7
8
9
0
100
100
10
10k
10000
1k
1000
VCC – Supply Voltage – V
100k
100000
f OSC – Oscillator Frequency – Hz
OUTPUT VOLTAGE
vs
LOAD CURRENT
OUTPUT VOLTAGE
vs
LOAD CURRENT
0
0
VCC = 5 V
VCC = 2 V
-0.25
-0.5
TA = 25°C
TA = 25°C
VO – Output Voltage – V
VO – Output Voltage – V
-1
-0.5
-0.75
-1
-1.25
-1.5
-1.5
-2
-2.5
-3
-3.5
-4
-1.75
-4.5
-2
-5
0
1
2
3
4
5
6
7
8
9
0
IL – Load Current – mA
5
10
15
20
25
30
35
40
IL – Load Current – mA
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CMOS VOLTAGE CONVERTER
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SCAS794 – JUNE 2006
TYPICAL CHARACTERISTICS (continued)
EFFICIENCY AND SUPPLY CURRENT
vs
LOAD CURRENT
EFFICIENCY AND SUPPLY CURRENT
vs
LOAD CURRENT
18
90
80
16
70
14
60
12
50
10
40
8
ICC
30
6
20
4
VCC = 2 V
10
2
TA = 25°C
0
0
0
1
2
3
4
5
6
7
8
100
80
80
70
70
60
60
50
50
40
30
30
20
20
VCC = 5 V
10
0
9
0
0
5
10
15
100
ηPOWER – Power-Conversion Efficiency – %
ePOWER
20
25
30
IL – Load Current – mA
98
96
94
92
VCC = 5 V
TA = 25°C
IOUT = 1 mA
88
1k
1000
10
TA = 25°C
EFFICIENCY
vs
OSCILLATOR FREQUENCY
10k
10000
f OSC – Oscillator Frequency – Hz
6
40
ICC
IL – Load Current – mA
90
90
ηPOWER
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100k
100000
35
40
45
ICC – Supply Current – mA
ηPOWER
100
ePOWER Efficiency – %
ηPOWER – Power-Conversion
90
20
ICC – Supply Current – mA
ePOWER Efficiency – %
ηPOWER – Power-Conversion
100
TL7660
CMOS VOLTAGE CONVERTER
www.ti.com
SCAS794 – JUNE 2006
APPLICATION INFORMATION
IS
8
1
7
2
TL7660
C1 +
10 µF -
3
6
4
5
V+
(5 V)
IL
RL
COSC
(see
Note A)
–VOUT
C2 10 µF +
A.
In the circuit, there is no external capacitor applied to terminal 7. However when device is plugged into a test
socket,there is usually a very small but finite stray capacitance present on the order of 10 pF.
Figure 1. Test Circuit
The TL7660 contains all the necessary circuitry to complete a negative voltage converter, with the exception of
two external capacitors which may be inexpensive 10 µF polarized electrolytic types. The mode of operation of
the device may be best understood by considering Figure 2, which shows an idealized negative voltage
converter. Capacitor C1 is charged to a voltage, VCC, for the half cycle when switches S1 and S3 are closed.
(Note: Switches S2 and S4 are open during this half cycle.) During the second half cycle of operation, switches
S2 and S4 are closed, with S1 and S3 open, thereby shifting capacitor C1 negatively by VCC volts. Charge is then
transferred from C1 to C2 such that the voltage on C2 is exactly VCC, assuming ideal switches and no load on C2.
The TL7660 approaches this ideal situation more closely than existing non-mechanical circuits. In the TL7660,
the four switches of Figure 2 are MOS power switches: S1 is a p-channel device, and S2, S3, and S4 are
n-channel devices. The main difficulty with this design is that in integrating the switches, the substrates of S3
and S4 must always remain reverse biased with respect to their sources, but not so much as to degrade their
ON resistances. In addition, at circuit start up and under output short circuit conditions (VOUT = VCC), the output
voltage must be sensed and the substrate bias adjusted accordingly. Failure to accomplish this results in high
power losses and probable device latchup. This problem is eliminated in the TL7660 by a logic network which
senses the output voltage (VOUT) together with the level translators and switches the substrates of S3 and S4 to
the correct level to maintain necessary reverse bias.
The voltage regulator portion of the TL7660 is an integral part of the anti-latchup circuitry; however, its inherent
voltage drop can degrade operation at low voltages. Therefore, to improve low-voltage operation, the LV
terminal should be connected to GND, disabling the regulator. For supply voltages greater than 3.5 V, the LV
terminal must be left open to insure latchup proof operation and prevent device damage.
8
S2
2
S1
VIN
C1
3
S3
3
S4
C2
5
VOUT = –VIN
7
Figure 2. Idealized Negative-Voltage Converter
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CMOS VOLTAGE CONVERTER
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APPLICATION INFORMATION (continued)
Theoretical Power Efficiency Considerations
In
•
•
•
theory, a voltage converter can approach 100% efficiency if certain conditions are met.
The driver circuitry consumes minimal power.
The output switches have extremely low ON resistance and virtually no offset.
The impedances of the pump and reservoir capacitors are negligible at the pump frequency.
The TL7660 approaches these conditions for negative voltage conversion if large values of C1 and C2 are used.
Energy is only lost in the transfer of charge between capacitors if a change in voltage occurs. The energy lost is
defined by:
E = ½ C1(V12 – V22)
Where V1 and V2 are the voltages on C1 during the pump and transfer cycles. If the impedances of C1 and C2
are relatively high at the pump frequency (see Figure 2) compared to the value of RL, there is a substantial
difference in the voltages V1 and V2. Therefore, it is not only desirable to make C2 as large as possible to
eliminate output voltage ripple but also to employ a correspondingly large value for C1 in order to achieve
maximum efficiency of operation.
Do's and Don'ts
• Do not exceed maximum supply voltages.
• Do not connect LV terminal to GND for supply voltages greater than 3.5 V.
• Do not short circuit the output to VCC supply for supply voltages above 5.5 V for extended periods, however,
transient conditions including start-up are okay.
• When using polarized capacitors, the positive terminal of C1 must be connected to terminal 2 of the TL7660,
and the positive terminal of C2 must be connected to GND.
• If the voltage supply driving the TL7660 has a large source impedance (25 Ω – 30 Ω), then a 2.2-µF
capacitor from terminal 8 to ground may be required to limit rate of rise of input voltage to less than 2V/µs.
• Ensure that the output (terminal 5) does not go more positive than GND (terminal 3). Device latch up occurs
under these conditions. A 1N914 or similar diode placed in parallel with C2 prevents the device from latching
up under these conditions (anode to terminal 5, cathode to terminal 3).
8
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CMOS VOLTAGE CONVERTER
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APPLICATION INFORMATION (continued)
Typical Applications
Simple Negative Voltage Converter
The majority of applications will undoubtedly utilize the TL7660 for generation of negative supply voltages.
Figure 3 shows typical connections to provide a negative supply negative (GND) for supply voltages below
3.5 V.
V+
8
1
7
2
10 µF
+
-
3
TL7660
4
6
5
VOUT = –V+
10 µF
+
Figure 3. Simple Negative-Voltage Converter
The output characteristics of the circuit in Figure 3 can be approximated by an ideal voltage source in series with
a resistance. The voltage source has a value of –VCC. The output impedance (RO) is a function of the ON
resistance of the internal MOS switches (shown in Figure 2), the switching frequency, the value of C1 and C2,
and the ESR (equivalent series resistance) of C1 and C2. A good first order approximation for RO is:
RO ≈ 2(RSW1 + RSW3 + ESRC1) + 2(RSW2 + RSW4 + ESRC1)
RO ≈ 2(RSW1 + RSW3 + ESRC1) + 1/fPUMPC1 + ESRC2
Where fPUMP = fOSC/2 , RSWX = MOSFET switch resistance.
Combining the four RSWX terms as RSW, we see that:
RO ≈ 2 (RSW) + 1/fPUMPC1 + 4 (ESRC1) + ESRC2
RSW, the total switch resistance, is a function of supply voltage and temperature (See the Output Source
Resistance graphs). Careful selection of C1 and C2 reduces the remaining terms, minimizing the output
impedance. High value capacitors reduce the 1/fPUMPC1 component, and low ESR capacitors lower the ESR
term. Increasing the oscillator frequency reduces the 1/fPUMPC1 term but may have the side effect of a net
increase in output impedance when C1 > 10 µF and there is no longer enough time to fully charge the capacitors
every cycle. In a typical application where fOSC = 10 kHz and C = C1 = C2 = 10 µF:
RO ≈ 2(23) + 1/(5 × 103)(10–5) + 4(ESRC1) + ESRC2
RO ≈ 46 + 20 + 5 (ESRC)
Because the ESRs of the capacitors are reflected in the output impedance multiplied by a factor of 5, a high
value could potentially swamp out a low 1/fPUMPC1 term, rendering an increase in switching frequency or filter
capacitance ineffective. Typical electrolytic capacitors may have ESRs as high as 10 Ω.
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CMOS VOLTAGE CONVERTER
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APPLICATION INFORMATION (continued)
Output Ripple
ESR also affects the ripple voltage seen at the output. The total ripple is determined by two voltages, A and B,
as shown in Figure 4. Segment A is the voltage drop across the ESR of C2 at the instant it goes from being
charged by C1 (current flow into C2) to being discharged through the load (current flowing out of C2). The
magnitude of this current change is 2 × IOUT, hence the total drop is 2 × IOUT × eSRC2 V. Segment B is the
voltage change across C2 during time t2, the half of the cycle when C2 supplies current to the load. The drop at
B is IOUT × t2/C2 V. The peak-to-peak ripple voltage is the sum of these voltage drops:
VRIPPLE ≈ (1/(2fPUMPC2) + 2(ESRC2)) × IOUT
Again, a low ESR capacitor results in a higher performance output.
t2
t1
B
0
V
A
–V+
Figure 4. Output Ripple
Paralleling Devices
Any number of TL7660 voltage converters may be paralleled to reduce output resistance (see Figure 5). The
reservoir capacitor, C2, serves all devices, while each device requires its own pump capacitor, C1. The resultant
output resistance would be approximately:
ROUT = ROUT (of TL7660)/n (number of devices)
V+
1
2
+
C1
-
3
4
8
TL7660
"1"
7
1
6
5
2
C1
+
-
3
8
TL7660
"n"
4
RL
7
6
5
C2 +
Figure 5. Paralleling Devices
10
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CMOS VOLTAGE CONVERTER
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APPLICATION INFORMATION (continued)
Cascading Devices
The TL7660 may be cascaded as shown to produced larger negative multiplication of the initial supply voltage
(see Figure 6). However, due to the finite efficiency of each device, the practical limit is 10 devices for light
loads. The output voltage is defined by:
VOUT = –n (VIN)
Where n is an integer representing the number of devices cascaded. The resulting output resistance would be
approximately the weighted sum of the individual TL7660 ROUT values.
V+
8
1
2
+
10 µF
-
3
TL7660
"1"
7
5
4
8
1
6
2
+
10 µF
-
3
TL7660
"n"
7
6
5
4
10 µF +
VOUT = –nV+
10 µF +
Figure 6. Cascading Devices for Increased Output Voltage
Changing the TL7660 Oscillator Frequency
It may be desirable in some applications, due to noise or other considerations, to increase the oscillator
frequency. This is achieved by overdriving the oscillator from an external clock, as shown in Figure 7. To prevent
possible device latchup, a 1-kΩ resistor must be used in series with the clock output. When the external clock
frequency is generated using TTL logic, the addition of a 10-kΩ pullup resistor to VCC supply is required. Note
that the pump frequency with external clocking, as with internal clocking, will be 1/2 of the clock frequency.
Output transitions occur on the positive-going edge of the clock.
V+
8
1
CMOS
Gate
7
2
+
10 µF –
V+
TL7660
3
6
4
5
VOUT
–10 µF ++
Figure 7. External Clocking
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APPLICATION INFORMATION (continued)
It is also possible to increase the conversion efficiency of the TL7660 at low load levels by lowering the oscillator
frequency (see Figure 8). This reduces the switching losses. However, lowering the oscillator frequency causes
an undesirable increase in the impedance of the pump (C1) and reservoir (C2) capacitors; this is overcome by
increasing the values of C1 and C2 by the same factor that the frequency has been reduced. For example, the
addition of a 100-pF capacitor between terminal 7 (OSC) and VCC lowers the oscillator frequency to 1 kHz from
its nominal frequency of 10 kHz (a multiple of 10), and thereby necessitate a corresponding increase in the
value of C1 and C2 (from 10 µF to 100 µF).
V+
C1
1
8
2
7
TL7660
++
--
3
6
4
5
COSC
VOUT
-C2 +
+
Figure 8. Lowering Oscillator Frequency
Positive Voltage Doubling
The TL7660 may be used to achieve positive voltage doubling using the circuit shown in Figure 9. In this
application, the pump inverter switches of the TL7660 are used to charge C1 to a voltage level of VCC – VF
(where VCC is the supply voltage and VF is the forward voltage drop of diode D1). On the transfer cycle, the
voltage on C1 plus the supply voltage (VCC) is applied through diode D2 to capacitor C2. The voltage thus
created on C2 becomes (2VCC) – (2VF) or twice the supply voltage minus the combined forward voltage drops of
diodes D1 and D2.
The source impedance of the output (VOUT) depends on the output current.
V+
1
8
7
D1
3
6
D2
4
5
2
TL7660
VOUT = (2V+) – (2VF)
C2
C1
Figure 9. Positive-Voltage Doubler
12
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CMOS VOLTAGE CONVERTER
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APPLICATION INFORMATION (continued)
Combined Negative Voltage Conversion and Positive Supply Doubling
Figure 10 combines the functions shown in Figure 3 and Figure 9 to provide negative voltage conversion and
positive voltage doubling simultaneously. This approach would be, for example, suitable for generating +9 V and
–5 V from an existing 5-V supply. In this instance, capacitors C1 and C3 perform the pump and reservoir
functions, respectively, for the generation of the negative voltage, while capacitors C2 and C4 are pump and
reservoir, respectively, for the doubled positive voltage. There is a penalty in this configuration that combines
both functions, however, in that the source impedances of the generated supplies are somewhat higher, due to
the finite impedance of the common charge pump driver at terminal 2 of the device.
V+
VOUT = –(nVIN – VFDX)
8
1
7
2
+
C1
-
+ C3
TL7660
3
6
4
5
D1
D2
-
VOUT = (2V+) – (VFD1) – (VFD2)
+
C2
+
C4
-
Figure 10. Combined Negative-Voltage Converter and Positive-Voltage Doubler
Voltage Splitting
The bidirectional characteristics can also be used to split a higher supply in half (see Figure 11. The combined
load is evenly shared between the two sides. Because the switches share the load in parallel, the output
impedance is much lower than in the standard circuits, and higher currents can be drawn from the device. By
using this circuit and then the circuit of Figure 6, 15 V can be converted (via 7.5 V, and –7.5 V) to a nominal
–15 V, although with rather high series output resistance (~250 Ω).
V+
RL1
+
50 µF
VOUT = V+ V
2
8
1
7
2
TL7660
+
50 µF
RL2
50 µF
+
-
3
6
4
5
V–
Figure 11. Splitting a Supply in Half
Submit Documentation Feedback
13
PACKAGE OPTION ADDENDUM
www.ti.com
10-Dec-2020
PACKAGING INFORMATION
Orderable Device
Status
(1)
Package Type Package Pins Package
Drawing
Qty
Eco Plan
(2)
Lead finish/
Ball material
MSL Peak Temp
Op Temp (°C)
Device Marking
(3)
(4/5)
(6)
TL7660CD
ACTIVE
SOIC
D
8
75
RoHS & Green
NIPDAU
Level-1-260C-UNLIM
-40 to 85
7660C
TL7660CDGKR
ACTIVE
VSSOP
DGK
8
2500
RoHS & Green
NIPDAU
Level-1-260C-UNLIM
-40 to 85
TME
TL7660CDGKT
ACTIVE
VSSOP
DGK
8
250
RoHS & Green
NIPDAU
Level-1-260C-UNLIM
-40 to 85
TME
TL7660CDR
ACTIVE
SOIC
D
8
2500
RoHS & Green
NIPDAU
Level-1-260C-UNLIM
-40 to 85
7660C
TL7660CP
ACTIVE
PDIP
P
8
50
RoHS & Green
NIPDAU
N / A for Pkg Type
-40 to 85
TL7660CP
TL7660ID
ACTIVE
SOIC
D
8
75
RoHS & Green
NIPDAU
Level-1-260C-UNLIM
-40 to 125
7660I
TL7660IDGKR
ACTIVE
VSSOP
DGK
8
2500
RoHS & Green
NIPDAU
Level-1-260C-UNLIM
-40 to 125
TNE
TL7660IDGKT
ACTIVE
VSSOP
DGK
8
250
RoHS & Green
NIPDAU
Level-1-260C-UNLIM
-40 to 125
TNE
TL7660IDR
ACTIVE
SOIC
D
8
2500
RoHS & Green
NIPDAU
Level-1-260C-UNLIM
-40 to 125
7660I
TL7660IP
ACTIVE
PDIP
P
8
50
RoHS & Green
NIPDAU
N / A for Pkg Type
-40 to 125
TL7660IP
(1)
The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2)
RoHS: TI defines "RoHS" to mean semiconductor products that are compliant with the current EU RoHS requirements for all 10 RoHS substances, including the requirement that RoHS substance
do not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, "RoHS" products are suitable for use in specified lead-free processes. TI may
reference these types of products as "Pb-Free".
RoHS Exempt: TI defines "RoHS Exempt" to mean products that contain lead but are compliant with EU RoHS pursuant to a specific EU RoHS exemption.
Green: TI defines "Green" to mean the content of Chlorine (Cl) and Bromine (Br) based flame retardants meet JS709B low halogen requirements of
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