SL1461MPAS

SEPTEMBER 1993 PRELIMINARY INFORMATION D.S. 3754 1.6 SL1461 WIDEBAND PLL FM DEMODULATOR The SL1461 is a wideband PLL FM demodulator, intended primarily for application in satellite tuners. The device contains all elements necessary, with the exception of external oscillator sustaining network and loop feedback components, to form a complete PLL system operating at frequencies up to 800MHz. An AFC with window adjust is provided, whose output signal can be used to correct for any frequency drift at the head end local oscillator. AFC PUMP AFC WINDOW ADJUST V EE OSCILLATOR + OSCILLATOR – AGC BIAS 1 2 16 15 AFC OUTPUT V CC VIDEO FEEDBACK + VIDEO – VIDEO + VIDEO FEEDBACK – VIDEO OUTPUT RF INPUT 4 5 6 7 8 SL1461S 3 14 13 12 11 10 9 FEATURES J Single chip PLL system for wideband FM demodulation J Simple low component count application J Allows for application of threshold extension J Fully balanced low radiation design J High operating input sensitivity J AGC detect and bias adjust J 75W video output drive with low distortion levels J Dynamic self biasing analog AFC J Full ESD protection * * Normal ESD handling procedures should be observed AGC OUTPUT RF INPUT MP16 Fig. 1 Pin connections top view APPLICATIONS J Satellite receiver systems J Data communications systems ORDERING INFORMATION SL1461S/KG/MPAS AGC BIAS RF INPUTS AGC OUTPUT 6 8 9 7 14 12 13 11 VIDEO FEEDBACK + VIDEO + VIDEO – VIDEO FEEDBACK – VIDEO OUTPUT AFC PUMP AFC OUTPUT 10 1 LOCAL OSCILLATOR AFC WINDOW ADJUST 4 5 16 2 Fig. 2 SL1461 block diagram SL1461 Tamb=–20°C to )80°C, VCC=)4.5V to )5.5V. These characteristics are guaranteed by either production test or design. They apply within the specified ambient temperature and supply voltage unless otherwise stated. Value Characteristics Supply current Operating frequency Input sensitivity Input overload VCO sensitivity (dF/dV) VCO linearity Phase detector gain Loop amplifier input impedance Loop amplifier output impedance Loop amplifier open loop gain Loop amplifier gain bandwidth product Loop amplifier output swing Video drive output impedance Video drive; Luminance nonlinearity – differential gain – differential phase – intermodulation – Signal/noise –Tilt – baseline distortion AGC output current AGC bias current AFC window current AFC charge pump current AFC leakage current AFC output saturation voltage 10 0 0 50 10 0.4 66 72 0.3 0.4 3 2 400 250 400 1.9 0.5 1.0 5 2.5 3 –40 % % Degree dB dB % % mA mA mA mA mA V With charge pump disabled AFC output enabled 400 mA gives 1.5V deadband window 1KW load, See note 3 & 4 75W load, See note 3 & 4 75W load, See note 3 & 4 See notes 1+3 & 4 1KW load, See note 2 & 4 1KW load, See note 3 & 4 1KW load, See note 3 & 4 Maximum load voltage drop 2V 55 75 450 0 25 32 .25 0.5 0.25 570 25 38 240 1.2 95 700 39 300 –40 Min Typ 36 Max 40 800 Units mA MHz dBm dBm MHz/V % V/rad V/rad W W dB MHz Vp–p W Refer to application in Fig. 3a Refer to application in Fig. 3a; with 13.5MHz p–p deviation Differential loop filter Single ended loop filter Single ended Single ended Single ended Single ended Single ended Preamp limiting Conditions ELECTRICAL CHARACTERISTICS Note 1. Product of input modulation f1 at 4.43MHz, 13.5MHz p–p deviation and f2 at 6MHz p–p deviation, (PAL chroma and sound subcarriers). Note 2. Ratio of output video signal with input modulation at 1MHz, 13.5MHz p–p deviation, to output rms noise in 6MHz bandwidth with no input modulation. Note 3 Note 4 Input test signal pre–emphasised video 13.5MHz p–p deviation. Output voltage 600mV pk–pk. See page 3 2 SL1461 TEST CONFIGURATION BASE BAND VIDEO 1V p–p TV SAT TEST TX ROHDE & SCHWARZ SFZ VIDEO GENERATOR ROHDE & SCHWARZ SGPF RF CARRIER FREQ 479.5MHz FM MODULATION 13.5MHz P–P PRE–EMPHASISED VIDEO MONTFORD TEST OVEN SL1461 TEST APPLICATION BOARD See Fig. 3a for details PRE EMPHASISED BASE BAND VIDEO VIDEO AMPLIFIER/ DE EMPHASISED NETWORK DE EMPHASISED BASE BAND VIDEO 1V p–p VIDEO ANALYSER ROHDE & SCHWARZ UAF The video drive characteristics measurements were made using the above test configuration. The maximum figures recorded in the Electrical Characteristics Table coincide with high temperatures and extremes of supply voltage. No adjustment to the recorded figures has been made to compensate for the effects of temperature on the external components of the application test board, in particular the varactor diodes. If operation of the device at high ambient temperatures is envisaged then attention to temperature compensation of the external circuitry will result in performance figures closer to the stated typical figures. Note 4. ABSOLUTE MAXIMUM RATINGS All voltages are referred to VEE at 0V. Characteristic Supply voltage RF input voltage RF input DC offset Oscillator +&–DC offset Video +&–DC offset Video feedback +&–DC offset Video output DC offset AFC pump DC offset AFC disable DC offset AFC deadband DC offset AGC bias DC offset AGC output DC offset Storage temperature Junction temperature MP16 package thermal resistance, chip to ambient –0.3 –0.3 –0.3 –0.3 –0.3 –0.3 –0.3 –0.3 –0.3 –0.3 –55 Min –0.3 Max 7 2.5 VCC+0.3 VCC+0.3 VCC+0.3 VCC+0.3 VCC+0.3 VCC+0.3 VCC+0.3 VCC+0.3 VCC+0.3 VCC+0.3 125 150 111 Units V V p–p V V V V V V V V V V °C °C °C/W Conditions 3 SL1461 ABSOLUTE MAXIMUM RATINGS cont. All voltages are referred to VEE at 0V. MP16 package thermal resistance chip to case Power consumption at 5.5V ESD protection – pins 1 to 15 ESD protection – pin 16 2 1.7 41 250 °C/W mW kV kV Mil–std –883 method 3015 class1 Mil–std –883 method 3015 class1 V CC 2K AGC BIAS 50K AFC WINDOW ADJUST 100nF 27K 47mF 47nF 4K7 BB833 BB833 22pF 22pF 5K1 4n7 4K7 1nF 100nF 1 2 16 15 120pF 1K2 4 5 6 7 8 SL1461S 3 14 13 12 11 10 9 1K2 47mF 1nF 120pF VIDEO OUTPUT RF INPUT Fig.3. Standard application circuit with oscillator referenced to ground V CC 2K AGC BIAS 50K AFC WINDOW ADJUST 100nF 27K 47mF 47nF 4K7 220R BB833 BB833 100nF 1 2 16 15 82pF 1K2 620R 1K2 47mF 1nF 82pF 4 5 6 SL1461S 3 14 13 12 11 10 9 5K1 4n7 4K7 1nF 7 8 VIDEO OUTPUT RF INPUT Fig.3a Application circuit used for video drive characterisation measurements 4 SL1461 FUNCTIONAL DESCRIPTION The SL1461 is a wideband PLL FM demodulator, optimised for application in satellite receiver systems and requiring a minimum external component count. It contains all the elements required for construction of a phase locked loop circuit, with the exception of tuning components for the local oscillator, and an AFC detector circuit for generation of error signal to correct for any frequency drift in the outdoor unit local oscillator. A block diagram is contained in Fig. 2 and the typical application in Fig. 3. The internal pin connections are contained in Fig.6/6a. In normal applications the second satellite IF frequency of typically 402 or 479.5MHz is fed to the RF preamplifier, which has a working sensitivity of typically –40 dBm, depending on application and layout. The preamplifier contains an RF level detect circuit, which generates an AGC signal that can be used for controlling the gain of the IF amplifier stages, so maintaining a fixed level to the RF input of the SL1461, for optimum threshold performance. The bias point of the AGC circuit can be adjusted to cater for variation in AGC line voltage requirement and device input power. The typical AGC curves are shown in Fig. 9. The output of the preamplifier is fed to the mixer section which is of balanced design for low radiation. In this stage the RF signal is mixed with the local oscillator frequency, which is generated by an on–board oscillator. The oscillator block uses an external varactor tuned sustaining network and is optimised for high linearity over the normal deviation range. A typical frequency versus voltage characteristic for the oscillator is contained in Fig. 7. The loop output is designed to compensate for first order temperature variation effects; the typical stability is shown in Fig. 8 The output of the mixer is then fed to the loop amplifier around which feedback is applied to determine loop transfer characteristic . Feedback can be applied either in differential or single ended mode; if the appropriate phase detector gains are assumed in calculating loop filters, both modes should give the same loop response. The loop amplifier drives a 75W output impedance buffer amplifier, which can either be connected to a 75W load or used to drive a high input impedance stage giving greater linearity and approximately 6dB higher demodulated signal output level. DESIGN OF PLL LOOP PARAMETERS GAIN = KD VOLT/RAD RF INPUT R1 R2 C1 BASEBAND OUTPUT GAIN = K0 RAD SEC/VOLT VCO Fig. 4 The SL1461 is normally used as a type 1 second order loop and can be represented by the above diagram. For such a system the following parameters apply; where: K0 is the VCO gain in radian seconds per volt KD is the phase detector gain in volts per radian wn is the natural loop bandwidth z is the loop damping factor R1 is loop amplifier input impedance Note: KO is dependant on sensitivity of VCO used. KD = 0.25V/rad single ended, 0.5V/rad differential t1 + C1.R1 t2 + C1.R2 and t1 + K 0K D w2 n From these factors the loop 3dB bandwidth can be determined from the following expression; w 2 + w 2(2z2 ) 1) " w 2 (2z 2 ) 1)2 ) 1 n n 3dB Which approximates to w 3dB + 2w n when z + 1 2 2z t2 + w n 5 SL1461 AFC FACILITY The SL1461 contains an analog frequency error detect circuit, which generates DC voltage proportional to the integral of frequency error. If the incident RF is high then the AFC voltage increases, if low then the voltage decreases. The AFC voltage can then be converted by an ADC to be read by the micro controller for frequency fine tuning; if used in an I2C system it is recommended the device is used with either the SP5055 or SP5056 frequency synthesiser which contains an internal ADC readable via the I2C bus. The voltage corresponding to frequency alignment is arbitrary and user defined; if used with the SP5055 it is suggested the aligned voltage is 0.375 VCC, corresponding to the centre code of the ADC on port 6. The AFC detect circuit contains a deadband centred around the aligned frequency. The deadband can be adjusted from zero window to approximately 25MHz width assuming an oscillator dF/dV of 15MHz/V. If the incident RF is within this window the AFC voltage does not integrate, except by component leakage. With reference to Fig.5; in normal operation the demodulated video is fed to a dual comparator where it is compared with two reference voltages, corresponding to the extremes of the deadband, or window. These voltages are variable and set by the window adjust input. The comparators produce two digital outputs corresponding to voltages above or below the voltage window, or frequency above or below deadband. These digital control signals are used to control a complimentary current source pump. The current signals are then fed to the input of an amplifier which is arranged as an integrator, so integrating the pulses into a DC voltage. If the frequency is correctly aligned both the current source and sink are disabled, therefore the DC output voltage remains constant. There will be a small drift due to component leakage; the maximum drift can be calculated from; I dV + 2500.C dt where I + V CC , C + CEXT R EXT WINDOW ADJUST V HI V ALIGN V LO FREQ VCC VCC + – CEXT BASEBAND VIDEO + – V AFC REXT VEE Fig. 5 AFC system block diagram 6 SL1461 VCC AGC BIAS VREF; 2.7V VREF; 2V AGC OUTPUT AGC output AGC bias adjust VREF; 3V AFC WINDOW 2x1500 RF INPUTS VREF; 1.6V RF inputs AFC window adjust VCC AFC PUMP VIDEO + 10K AFC OUTPUT 330 330 VIDEO – 2mA 2mA AFC output stage Video amp outputs Fig.6 SL1461 I/O port internal circuitry 7 SL1461 VREF; 2.5V 2 x 5k OSCILLATOR + OSCILLATOR – Local oscillator FROM PHASE DETECTOR 2x570 VCC 68 VIDEO OUTPUT VIDEO FEEDBACK + VIDEO FEEDBACK – 105 4mA Video amp feedback inputs Fig. 6a SL1461 I/O port internal circuitry Video output drive FREQ MHz FREQ MHz 520 500 480 460 440 420 400 360 1 1.5 2 2.5 3 3.5 4 4.5 5 478 –20 20 TEMP/°C 80 DC VOLTAGE 479 480 481 482 Fig. 7 Typical VCO frequency vs DC control voltage Fig. 8 SL1461 VCO centre frequency uncompensated temperature stability. 8 SL1461 2.0 1.5 AGC OUTPUT 1.0 VOLTAGE AGC BIAS RESISTOR 5.1K AGC BIAS CURRENT 297mA AGC LOAD RESISTOR 3.9K AGC BIAS RESISTOR 10.5K AGC BIAS CURRENT 150mA AGC LOAD RESISTOR 4.7K AGC BIAS RESISTOR 32K AGC BIAS CURRENT 52mA AGC LOAD RESISTOR 10K 0.5 –70 –60 –50 –40 –30 –20 –10 0 VCC = 5.0 VOLTS RF INPUT LEVEL (dBm) UNMODULATED Fig.9 SL1461 AGC output voltage for differing values of AGC bias resistor APPLICATION NOTES Capture range Under conditions when there is no RF input signal present, the SL1461 may react to spurious radiation from the free running oscillator coupling into the RF inputs. Because of the constant phase error between the VCO input to the phase detector and the spuriously coupled signal via the RF input, the phase comparator will drive the control voltage to either the bottom or the top of the range. In such a case, the capture range will be asymmetrical about the VCO free running frequency, since any control voltage will only be able to tune the VCO in one direction if the tuning voltage is already at the max or min. This effect can be avoided by driving the RF input differentially or achieving good common mode rejection to the VCO signal. The lock range is independant of the above effects and will be symmetric about the centre of the phase detector S–curve provided the VCO is correctly aligned. EXAMPLE Loop out of lock Tuning voltage =4.3V (maximum) frequency =520MHz (maximum It is only possible to capture signals below this frequency since the VCO is already at its maximum frequency. Testing of capture range should be done with the device operating under normal conditions. An input signal of between –35dBm to –10dBm is suitable for such a measurement. S–curve. When the oscillator is sitting in the centre of the S–curve, the two video outputs will be at the same DC voltage. RF oscillator design The standard application circuit for the SL1461 is shown in Fig.3 The layout of the VCO tank should follow normal good RF techniques – ie as compact as possible. This will minimise parasitics, thus giving improved VCO linearity and stability. The PCB layout used for testing purpose is shown in Fig. 11. Setting up of oscillator The VCO should be set up so that the desired input RF frequency is at the centre of the lock range. This will coincide with the centre of the S–curve and the point at which the AFC toggles when set to zero deadband. The easiest way to centralise the VCO is to input an RF carrier which is being modulated by a low frequency squarewave. The tuning coil(s) should be adjusted until the AFC voltage toggles between 0.2V and VCC–0.7V. The smaller the FM deviation of the squarewave used, the more accurate the setting will be. A pre–emphasised video input containing black to white transitions can also be used for this setting, since the DC content in a pre–emphased video is much less than that in non pre–emphasised video. This is important as any dc content in the input waveform will introduce an offset in the AFC transition point. The setting can be confirmed by measuring the DC voltage on the two video outputs, the voltages should be the same when the oscillator is centred around the incoming frequency. This DC measurement must be carried out with an unmodulated carrier of the required frequency. Modulation must not be present, since by definition, the dc voltages would be changing, thus making accurate measurement difficult. Lock range Lock range should be symmetric about the centre of the 9 SL1461 NOTES Circuit schematic is shown in Fig. 3. TP1=VIDEO – TP2=VIDEO + TP3=AGC O/P TP4=AFC O/P All surface mount components mounted on underside of board Fig. 11 Layout of demo board with oscillator referenced to GND 10 SL1461 11 SL1461 PACKAGE DETAILS Dimensions are shown thus: mm (in). For further package information please contact your local Customer Service Centre. 9.80/10.01 (0.386/0.394) 0.69 (0.027) MAX AT 4 PLACES 3.80/4.00 (0.150/0.157) 16 LEAD MINIATURE PLASTIC MP16 PIN 1 PIN 1 IDENTIFICATION 1.27 (0.050) NOM PIN SPACING 1.35/1.91 (0.053/0.075) 0.25/0.51 (0.010/0.020) X45° 8°MAX 0.41/1.27 (0.016/0.050) 5.80/6.20 (0.228/0.244) 0.19/0.25 (0.007/0.010) 0.35/0.49 (0.014/0.019) 0.10/0.25 (0.004/0.010) HEADQUARTERS OPERATIONS GEC PLESSEY SEMICONDUCTORS Cheney Manor, Swindon, Wiltshire SN2 2QW, United Kingdom. Tel: (0793) 518000 Fax: (0793) 518411 GEC PLESSEY SEMICONDUCTORS P.O. box 660017 1500 Green Hills Road, Scotts Valley, California 95067–0017, United States of America. Tel: (408) 438 2900 Fax: (408) 438 5576 CUSTOMER SERVICE CENTRES F FRANCE & BENELUX Les Ulis Cedex Tel: (1) 64 46 23 45 Tx: 602858F Fax: (1) 64 46 06 07 F GERMANY Munich Tel: (089) 3609 06 0 Tx: 523980 Fax: (089) 3609 06 55 F ITALY Milan Tel: (02) 66040867 Fax: (02) 66040993 F JAPAN Tokyo Tel: (03) 3296–0281 Fax: (03) 3296–0228 F NORTH AMERICA Integrated Circuits and Microwave Products, Scotts Valley, USA Tel: (408) 438 2900 Fax: (408) 438 7023 Hybrid Products, Farmingdale, USA Tel: (516) 293 8686 Fax: (516) 293 0061 F SOUTH EAST ASIA Singapore Tel: (65) 3827708 Fax: (65) 3828872 F SWEDEN Stockholm Tel: 46 8 7029770 Fax: 46 8 6404736 F UNITED KINGDOM & SCANDINAVIA Swindon Tel: (0793) 518510 Tx: 444410 Fax: (0793) 518582 These are supported by Agents and Distributors in major countries world–wide. E GEC Plessey Semiconductors 1993 Publication No. D.S. 3754 Issue No. 1.6 September 1993 This publication is issued to provide outline information only, which (unless agreed by the Company in writing) may not be used, applied or reproduced for any purpose nor form part of any order or contract nor to be regarded as a representation relating to the products or services concerned. No warranty or guarantee express or implied is made regarding the capability, performance or suitability of any product or service. The Company reserves the right to alter without notice the specification, design, price of any product or service. Information concerning possible methods of use is provided as a guide only and does not constitute any guarantee that such methods of use will be satisfactory in a specific piece of equipment. It is the user ’s responsibility to fully determine the performance and suitability of any equipment using such information and to ensure that any publication of data used is up to date and has not been superseded. These products are not suitable for use in any medical products whose failure to perform may result in significant injury or death to the user. All products and materials are sold and services provided subject to the Company’s conditions of sale, which are available on request. 12 h ttp://www.zarlink.com World Headquarters - Canada Tel: +1 (613) 592 0200 Fax: +1 (613) 592 1010 North America - West Coast Tel: (858) 675-3400 Fax: (858) 675-3450 North America - East Coast Tel: (978) 322-4800 Fax: (978) 322-4888 Asia/Pacific Tel: +65 333 6193 Fax: +65 333 6192 Europe, Middle East, and Africa (EMEA) Tel: +44 (0) 1793 518528 Fax: +44 (0) 1793 518581 Information relating to products and services furnished herein by Zarlink Semiconductor Inc. trading as Zarlink Semiconductor or its subsidiaries (collectively “Zarlink”) is believed to be reliable. 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Manufacturing does not necessarily include testing of all functions or parameters. These products are not suitable for use in any medical products whose failure to perform may result in significant injury or death to the user. All products and materials are sold and services provided subject to Zarlink Semiconductor’s conditions of sale which are available on request. Purchase of Zarlink’s I2C components conveys a licence under the Philips I2C Patent rights to use these components in an I2C System, provided that the system conforms to the I2C Standard Specification as defined by Philips Zarlink and the Zarlink Semiconductor logo are trademarks of Zarlink Semiconductor Inc. Copyright 2001, Zarlink Semiconductor Inc. All rights reserved. TECHNICAL DOCUMENTATION - NOT FOR RESALE