EUP6514DIR1

EUP6514 5V/12V Synchronous Buck PWM Controller DESCRIPTION The EUP6514 is a high efficiency, fixed 300kHz frequency, voltage mode, synchronous PWM controller. The device drives two low cost N-channel MOSFETs and is designed to work with 5V to 12V supply voltage, providing excellent regulation for load transients. The EUP6514 includes soft-start, frequency compensation networks nd integrates all of the controls, output adjustments, monitoring and protection functions into a single package. A power-on-reset (POR) circuit monitors the power supply to prevent wrong logic controls. The built-in soft-start with fixed soft-start internal prevents the output voltage from overshoot as well as limiting the input current. Adjustable over-current protection monitors the voltage drop across the RDS(ON) of the lower MOSFET, with no current sense resistor required. The EUP6514 is available in 8-pins SOP package. Pulling and holding the voltage on OPS pin below 0.1V with an open drain device shuts down the controller. FEATURES Operating with 5~12V Supply Voltage 300 kHz Fixed Frequency Oscillator Built-In Feedback Compensation -Voltage-mode PWM Control with 0 to 100% Duty Ratio Fast Transient Response -High-Speed GM Amplifier Drives All Low Cost N-Channel MOSFETs -Adaptive Shoot-Through Protection Adjustable Over-Current Protection -Using RDS(ON) of the Low-side MOSFET Built-In Soft-Start Shutdown Control using an External Available in SOP-8 RoHS Compliant and 100% Lead (Pb)-Free APPLICATIONS Motherboard Graphics Card High Current, up to 20A, DC-DC Converter Telecomm Equipments IA Equipments Typical Application Circuit Figure 1. DS6514 Ver 1.1 Aug. 2008 1 EUP6514 Pin Configurations Package Type Pin Configurations SOP-8 Pin Description PIN PIN DESCRIPTION 1 BOOT 2 UGATE 3 GND 4 5 6 LGATE VCC FB Bootstrap supply pin for the upper gate driver. Connect the bootstrap capacitor between BOOT pin and the PHASE pin. The bootstrap capacitor provides the charge to turn on the upper MOSFET. Upper gate driver output. Connect to the gate of high-side power N-Channel MOSEFT. This pin is monitored by the adaptive shoot-through protection circuitry to determine when the upper MOSFET has turned off. Both signal and power ground for the IC. All voltage levels are measured with respect to this pin. Ties the pin directly to the low-side MOSFET source and ground plane with the lowest impedance. Lower gate drive output. Connect to the gate of low-side power N-Channel MOSFET. This pin is monitored by the adaptive shoot-through protection circuitry to determine when the lower MOSFET has turned off. Connect this pin to a well-decoupled 5V or 12V bias supply. It is also the positive supply for the lower gate driver, LGATE. Switcher feedback voltage. This pin is the inverting input of the error amplifier. FB senses the switcher output through an external resistor divider network. This pin provides multi-function of the over-current setting, UGATE turn-on POR sensing, and shut-down features. Connecting a resistor (ROCSET) between OPS and PHASE pins sets the over-current trip point. Pulling the pin to ground resets the device and all external MOSFETs are turned off allowing the output voltage power rails to float. This pin is also used to detect VIN in power on stage and issues an internal POR signal. Connect this pin to the source of the upper MOSEFT and the drain of the lower MOSFET. 7 OPS 8 PHASE DS6514 Ver 1.1 Aug. 2008 2 EUP6514 Block Diagram Figure 2. DS6514 Ver 1.1 Aug. 2008 3 EUP6514 Ordering Information Order Number Package Type Marking Operating Temperature Range EUP6514DIR1 SOP-8 xxxxx P6514 -40 °C to 85°C EUP6514 □□□□ Lead Free Code 1: Lead Free 0: Lead Packing R: Tape& Reel Operating temperature range I: Industry Standard Package Type D: SOP DS6514 Ver 1.1 Aug. 2008 4 EUP6514 Absolute Maximum Ratings Supply Voltage (VCC) -------------------------------------------------------------------------- 16V BOOT, VBOOT-VPHASE --------------------------------------------------------------------------- 16V PHASE to GND DC ----------------------------------------------------------------------------------------- -1V to 15V BOOT to PHASE -------------------------------------------------------------------------------- 15V BOOT to GND DC -------------------------------------------------------------------------------- -0.3V to VCC+15V UGATE ------------------------------------------------------------- VPHASE -0.3V to VBOOT +0.3V LGATE ---------------------------------------------------------------- GND -0.3V to VVCC +0.3V Input, Output or I/O Voltage --------------------------------------------------- GND -0.3V to 7V Package Thermal Resistance SOP-8, θJA --------------------------------------------------------------------------------- 67.9°C /W Junction Temperature ------------------------------------------------------------------------ 150°C Storage Temperature (Solding, 10sec.) ----------------------------------------------------- 260°C ESD Susceptibility HBM (Human Body Mode) -------------------------------------------------------------------- 2kV Recommended Operating Conditions Supply Voltage, VCC ---------------------------------------------------------- 5V±5%, 12V±10% Ambient Temperature Range ------------------------------------------------------ -40°C to 85°C Junction Temperature Range ---------------------------------------------------- -40°C to 125°C Electrical Characteristics Symbol Parameter Conditions UGATE and LGATE open Min. EUP6514 Typ. Max. 2 1.2 4.2 400 0.8 300 1.5 80 1 1 400 0.1 VCC=12V, IUGATE=10mA VUGATE=1V, IUGATE=10mA VCC=12V, ILGATE=10mA VLGATE=1V, IUGATE=10mA FB Falling VPHASE=0 68 35 5 3 5 3 50 73 40 0.4 Falling VOPS 0.08 4 0.1 0.13 8 6 8 6 5 2.5 4.5 Unit mA mA V mV V kHz VP-P dB Hz kHz kHz µA Ω Ω Ω Ω ns % µA V mS V VCC Supply Current ICC Norminal Supply Current ICCS Shutdown Supply Current Power-on Reset VCCRTH POR Threshold VCCHYS Hysteresis Switcher Reference VREF Reference Voltage Oscillator fOSC Free Running Trequency Ramp ∆VOSC Amplitude Error Amplifier DC Gain FP1 First Pole Frequency FZ Zero Frequency FP2 Second Pole Frequency FB Input Current PWM Controller Gate Drivers RUGATE_H UGATE source Rdson RUGATE_L UGATE sink Rdson RLGATE_H LGATE source Rdson RLGATE_L LGATE sink Rdson TDT Dead Time Protection UVP Under Voltage Level IOC OC Current Source Over-current Reference Voltage TSS Soft-Start Interval VOPS_SHUT OPS Shutdown Threshold DS6514 Ver 1.1 Aug. 2008 VCC Rising 200 VCC=12V VCC=12V VCC=12V 0.784 250 0.816 360 78 45 5 EUP6514 Typical Operating Characteristics DS6514 Ver 1.1 Aug. 2008 6 EUP6514 Typical Operating Characteristics (continued) DS6514 Ver 1.1 Aug. 2008 7 EUP6514 Typical Operating Characteristics (continued) DS6514 Ver 1.1 Aug. 2008 8 EUP6514 Application Information Inductor Selection The selection of output inductor is based on the considerations of efficiency, output power and operating frequency. Low inductance value has smaller size, but results in low efficiency, large ripple current and high output ripple voltage. Generally, an inductor that limits the ripple current (∆IL) between 20% and 50% of output current is appropriate. Figure 3 shows the typical topology of synchronous step-down converter and its related waveforms. According to Figure 1 the ripple current of inductor can be calculated as follows : VIN − VOUT = L D V ∆IL ; ∆t = ; D = OUT ∆t fs VIN VOUT VIN × fs × ∆IL L = (VIN − VOUT ) × Where: VIN = Maximum input voltage VOUT = Output Voltage ∆t = S1 turn in time ∆IL = Inductor current ripple fs = Switching frequency D = Duty Cycle rC = Equivalent series resistor of output capacitor Output Capacitor The selection of output capacitor depends on the output ripple voltage requirement. Practically, the output ripple voltage is a function of both capacitance value and the equivalent series resistance (ESR) rC. Figure 4 shows the related waveforms of output capacitor. Figure 3.The waveforms of synchronous step-down converter DS6514 Ver 1.1 Aug. 2008 Figure 4.The related waveforms of output capacitor 9 EUP6514 The AC impedance of output capacitor at operating flows mainly through output capacitor. The output ripple voltage is described as: ∆ V OUT = ∆V OR + ∆ V OC + V OC ∆ V OUT 1 = ∆IL × rc + CO (2) (3) (4) Below Figures say those effects. And test conditions are Rocset=15kΩ (over-current trip point=20.6A), Low-side MOSFET is IR3707. 2. VIN_POR ∫ t2 t1 ic dt ∆ V OUT = ∆IL × ∆IL × rc + 1 V OUT (1 − D )TS2 8 C OL Where △VOR is by ESR and ΔVOC by capacitance. For electrolytic capacitor application, typically 90 to 95% of the output voltage ripple is contributed by the ESR of output capacitor. So Equation (4) could be simplified as : ∆ V OUT = ∆IL × rc (5) UGATE will continuously generate a 10kHz clock with 1% duty cycle before VIN is recognized ready by detecting VOPS crossing 1.5V four times (rising & falling). ROCSET must be kept lower than 37.5kΩ for large ROCSET will keep VOPS always higher than 1.5V. Figure 6 shows the detail actions of OCP and POR. It is highly recommend-ed that ROCSET be lower than 30kΩ. Users could connect capacitors in parallel to get calculated ESR. Output Capacitor The selection of input capacitor is mainly based on its maximum ripple current capability. The buck converter draws pulsewise current from the input capacitor during the on time of S1 as shown in Figure 3. The RMS value of ripple current flowing through the input capacitor is described as: Irms = IOUT D (1 − D ) (A ) (6) The input capacitor must be cable of handling this ripple current. Sometime, for higher efficiency the low ESR capacitor is necessarily. OPS (Over Current Setting, VIN_POR and Shutdown) 1.OCP Figure 5. UV_FB trigger VIN power sensing 3. Shutdown Pulling low the OPS pin by a small single transistor can shutdown the EUP6514 PWM controller as shown in typical application circuit. Soft Start A built-in soft-start is used to prevent surge current from power supply input during power on. The soft-start voltage is controlled by an internal digital counter. It clamps the ramping of reference voltage at the input of error amplifier and the pulse-width of the output driver slowly. The typical soft-start duration is 3ms. Sense the low-side MOSFET’s RDS(ON) to set over-current trip point. Connecting a resistor (ROCSET) from this pin to the source of the upper MOSFET and the drain of the lower MOSFET sets the over-current trip point. ROCSET, an internal 40µA current source, and the lower MOSFET on resistance, RDS(ON), set the converter over-current trip point (IOCSET) according to the following equation : IOCSET = 40 µA × R OCSET − 0.4 V R DS ( ON ) of the lower MOSFET OPS pin function is similar to RC charging or charging or discharging circuit, so the over-current trip point is very sensitive to parasitic capacitance (ex. Shut-down MOSFET) and the duty ratio. DS6514 Ver 1.1 Aug. 2008 10 EUP6514 Under Voltage Protection The voltage at FB pin is monitored and protected against UV (under voltage). The UV threshold is the FB or FBL under 80%. UV detection has 15µs triggered delay. A hiccup restart sequence will be operating until UV state is exited. output inductor and output capacitors between the MOSEFTs and the load. Also locate the PWM controller near by MOSFETs. A multi-layer printed circuit board is recommended. Figure 6. PWM Layout Considerations MOSFETs switch very fast and efficiently. The speed with which the current transitions form one device to another causes voltage spikes across the interconnecting impedances and parasitic circuit elements. The voltage spikes can degrade efficiency and radiate noise, that results in over-voltage stress on devices. Careful component placement layout and printed circuit design can minimize the voltage spikes induced in the converter. Consider, as an example, the turn-off, the upper MOSFET was carrying the full load current. During turn-off, current stops flowing in the upper MOSFET and is picked up by the low side MOSFET or schottky diode. Any inductance in the switched current path generates a large voltage spike during the switching interval. Careful component selections, layout of the critical components, and use shorter and wider PCB traces help in minimizing the magnitude of voltage spikes. There are two sets of critical components in a DC-DC converter using the EUP6514. The switching power components are most critical because they switch large amounts of energy, and as such, they tend to generate equally large amounts of noise. The critical small signal components are those connected to sensitive nodes or those supplying critical bypass current. The power components and the PWM controller should be placed firstly. Place the input capacitors, especially the high-frequency ceramic decoupling capacitors, close to the power switches. Place the DS6514 Ver 1.1 Aug. 2008 11 EUP6514 Packaging Information SOP-8 SYMBOL S A A1 D E E1 L b e MILLIMETERS MIN. MAX. 1.35 1.75 0.10 0.25 4.90 5.80 6.20 3.90 0.40 1.27 0.31 0.51 1.27 INCHES MIN. 0.053 0.004 0.193 0.228 0.153 0.016 0.012 0.050 MAX. 0.069 0.010 0.244 0.050 0.020 DS6514 Ver 1.1 Aug. 2008 12