AD7533

® AD7533 Data Sheet June 2004 FN3105.3 10-Bit Multiplying D/A Converter The AD7533 is a monolithic, low cost, high performance, 10-bit accurate, multiplying digital-to-analog converter (DAC), in a 16 pin DIP. Intersil’s thin film resistors on CMOS circuitry provide 10-bit resolution (8-bit accuracy), with TTL/CMOS compatible operation. The AD7533’s accurate four quadrant multiplication, full input protection from damage due to static discharge by clamps to V+ and GND, and very low power dissipation make them very versatile converters. Low noise audio gain controls, motor speed controls, digitally controlled gain and digital attenuators are a few of the wide range of applications of the AD7533. Features • 8-Bit Linearity • Low Gain and Linearity Temperature Coefficients • Full Temperature Range Operation • Static Discharge Input Protection • TTL/CMOS Compatible • Supply Range. . . . . . . . . . . . . . . . . . . . . . . . . +5V to +15V • Fast Settling Time at 25oC . . . . . . . . . . . . . . 150ns (Max) • Four Quadrant Multiplication • AD7533 Direct AD7520 Equivalent Pinout AD7533 (PDIP) TOP VIEW IOUT1 1 IOUT2 2 GND 3 16 RFEEDBACK 15 VREF IN 14 V+ 13 BIT 10 12 BIT 9 11 BIT 8 10 BIT 7 9 BIT 6 Functional Block Diagram VREF IN (15) 20kΩ 20kΩ 20kΩ 20kΩ 20kΩ 20kΩ (3) 10kΩ 10kΩ 10kΩ 10kΩ BIT 1 (MSB) 4 BIT 2 5 BIT 3 6 SPDT NMOS SWITCHES 10kΩ MSB (4) BIT 2 (5) BIT 3 (6) IOUT2 (2) IOUT1 (1) BIT 4 7 BIT 5 8 RFEEDBACK (16) NOTE: Switches shown for digital inputs “High” Ordering Information PART NUMBER AD7533JN NUMBER OF BITS 10 LINEARITY (INL, DNL) 0.2% (8-Bit) TEMP. RANGE (oC) 0 to 70 PACKAGE 16 Ld PDIP PKG. NO. E16.3 1 CAUTION: These devices are sensitive to electrostatic discharge; follow proper IC Handling Procedures. 1-888-INTERSIL or 321-724-7143 | Intersil (and design) is a registered trademark of Intersil Americas Inc. Copyright © Intersil Americas Inc. 2004. All Rights Reserved All other trademarks mentioned are the property of their respective owners. AD7533 Absolute Maximum Ratings Supply Voltage (V+ to GND) . . . . . . . . . . . . . . . . . . . . . . . . . . .+17V VREF . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . ±25V Digital Input Voltage Range . . . . . . . . . . . . . . . . . . . . . . . V+ to GND Output Voltage Compliance . . . . . . . . . . . . . . . . . . . . . -100mV to V+ Thermal Information Thermal Resistance (Typical, Note 1) θJA (oC/W) PDIP Package . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 90 Maximum Junction Temperature (Plastic Package) . . . . . . . .150oC Maximum Storage Temperature. . . . . . . . . . . . . . . . -65oC to 150oC Maximum Lead Temperature (Soldering 10s) . . . . . . . . . . . . .300oC Operating Conditions Temperature Range . . . . . . . . . . . . . . . . . . . . . . . . . . . . 0oC to 70oC CAUTION: Stresses above those listed in “Absolute Maximum Ratings” may cause permanent damage to the device. This is a stress only rating and operation of the device at these or any other conditions above those indicated in the operational sections of this specification is not implied. NOTE: 1. θJA is measured with the component mounted on a low effective thermal conductivity test board in free air. See Tech Brief TB379 for details. Electrical Specifications V+ = +15V, VREF = +10V, VOUT1 = VOUT2 = 0V, Unless Otherwise Specified TA 25oC TA MIN-MAX MIN MAX UNITS PARAMETER SYSTEM PERFORMANCE Resolution Nonlinearity TEST CONDITIONS MIN MAX 10 -10V ≤ VREF ≤ +10V, VOUT1 = VOUT2 = 0V (Notes 2, 3, 6) - ±0.2 10 - ±0.2 Bits % of FSR Monotonicity Gain Error All Digital Inputs High (Note 3) -10V ≤ VREF ≤ + 10V (Notes 3, 4) - Guaranteed ±1.4 ±2 ±10 ±50 ±1.8 ±2 ±10 ±200 % of FSR ppm of FSR/oC ppm of FSR/oC nA Nonlinearity Tempco - - Gain Error Tempco - - Output Leakage Current (Either Output) DYNAMIC CHARACTERISTICS Power Supply Rejection VOUT1 = VOUT2 = 0 - - V+ = 14.0V to 15.0V (Note 3) - ±0.005 - ±0.008 % of FSR/% of ∆V+ ns Output Current Settling Time To 0.2% of FSR, RL = 100Ω (Note 4) VREF = 20VP-P , 200kHz Sine Wave, All Digital Inputs Low (Note 4) - 600 ±0.05 - 800 ±0.1 Feedthrough Error - - LSB REFERENCE INPUTS Input Resistance (Pin 15) All Digital Inputs High IOUT1 at Ground (Note 4) 5 Temperature Coefficient 20 -300 5 20 -300 kΩ kΩ ppm/οC 2 AD7533 Electrical Specifications V+ = +15V, VREF = +10V, VOUT1 = VOUT2 = 0V, Unless Otherwise Specified (Continued) TA 25oC PARAMETER ANALOG OUTPUT Output Capacitance COUT1 All Digital Inputs High (Note 4) COUT2 COUT1 All Digital Inputs Low (Note 4) COUT2 DIGITAL INPUTS Low State Threshold, VIL High State Threshold, VIH Input Current (Low or High), IIL, IIH Input Coding Input Capacitance VIN = 0V or + 15V See Tables 1 through 3 (Note 4) 2.4 0.8 ±1 2.4 0.8 ±1 V V µA 100 35 35 100 100 35 35 100 pF pF pF pF TEST CONDITIONS MIN MAX TA MIN-MAX MIN MAX UNITS Binary/Offset Binary 4 4 pF POWER SUPPLY CHARACTERISTICS Power Supply Voltage Range I+ (Note 6) All Digital Inputs High or Low (Excluding Ladder Network) +5 to +16 2 2.5 V mA NOTES: 2. Full Scale Range (FSR) is 10V for unipolar and ±10V for bipolar modes. 3. Using internal feedback resistor, RFEEDBACK . 4. Guaranteed by design or characterization and not production tested. 5. Accuracy not guaranteed unless outputs at ground potential. 6. Accuracy is tested and guaranteed at V+ = +15V, only. Definition of Terms Nonlinearity: Error contributed by deviation of the DAC transfer function from a “best straight line” through the actual plot of transfer function. Normally expressed as a percentage of full scale range or in (sub)multiples of 1 LSB. Resolution: It is addressing the smallest distinct analog output change that a D/A converter can produce. It is commonly expressed as the number of converter bits. A converter with resolution of n bits can resolve output changes of 2-N of the full-scale range, e.g., 2-N VREF for a unipolar conversion. Resolution by no means implies linearity. Settling Time: Time required for the output of a DAC to settle to within specified error band around its final value (e.g., 1/2 LSB) for a given digital input change, i.e., all digital inputs LOW to HIGH and HIGH to LOW. Gain Error: The difference between actual and ideal analog output values at full-scale range, i.e., all digital inputs at HIGH state. It is expressed as a percentage of full scale range or in (sub)multiples of 1 LSB. Feedthrough Error: Error caused by capacitive coupling from VREF to IOUT1 with all digital inputs LOW. Output Capacitance: Capacitance from IOUT1 , and IOUT2 terminals to ground. Output Leakage Current: Current which appears on IOUT1 , terminal when all digital inputs are LOW or on IOUT2 terminal when all digital inputs are HIGH. For further information on the use of this device, see the following Application Notes: Application Notes NOTE # AN002 AN018 AN042 DESCRIPTION “Principles of Data Acquisition and Conversion” “Do’s and Don’ts of Applying A/D Converters” “Interpretation of Data Conversion Accuracy Specifications” Detailed Description The AD7533 is a monolithic multiplying D/A converter. A highly stable thin film R-2R resistor ladder network and NMOS SPDT switches form the basis of the converter circuit, CMOS level shifters permit low power TTL/CMOS 3 AD7533 compatible operation. An external voltage or current reference and an operational amplifier are all that is required for most voltage output applications. A simplified equivalent circuit of the DAC is shown in the Functional Diagram. The NMOS SPDT switches steer the ladder leg currents between IOUT1 and IOUT2 buses which must be held at ground potential. This configuration maintains a constant current in each ladder leg independent of the input code. Converter errors are further reduced by using separate metal interconnections between the major bits and the outputs. Use of high threshold switches reduce offset (leakage) errors to a negligible level. The level shifter circuits are comprised of three inverters with positive feedback from the output of the second to the first, see Figure 1. This configuration results in TTL/CMOS compatible operation over the full military temperature range. With the ladder SPDT switches driven by the level shifter, each switch is binarily weighted for an ON resistance proportional to the respective ladder leg current. This assures a constant voltage drop across each switch, creating equipotential terminations for the 2R ladder resistors and high accurate leg currents. Typical Applications ±10V +15V VREF R1 MSB 4 DATA INPUTS LSB 14 RFEEDBACK 16 OUT1 AD7533 1 15 3 2 OUT2 CR1 R2 6 + VOUT 11 GND NOTES: 7. R1 and R2 used only if gain adjustment is required. 8. CR1 protects AD7533 against negative transients. FIGURE 2. UNIPOLAR BINARY OPERATION Unipolar Binary Operation - (10-Bit DAC) The circuit configuration for operating the AD7533 in unipolar mode is shown in Figure 2. With positive and negative VREF values the circuit is capable of 2-Quadrant multiplication. The “Digital Input Code/Analog Output Value” table for unipolar mode is given in Table 1. TABLE 1. UNlPOLAR BINARY CODE - AD7533 DIGITAL INPUT MSB LSB (NOTE 9) NOMINAL ANALOG OUTPUT 1023 – V REF  ------------   1024 513 – V REF  ------------   1024 V REF 512 – V REF  ------------  = – ------------- 1024 2 511 – V REF  ------------   1024 1 – V REF  ------------   1024 0 – V REF  ------------  = 0  1024 V+ 13 4 6 TO LADDER 1111111111 1000000001 1000000000 8 9 TTL/ CMOS INPUT 2 5 7 IOUT2 IOUT1 0111111111 0000000001 0000000000 NOTES: 9. VOUT as shown in Figure 2. FIGURE 1. CMOS SWITCH 10. Nominal Full Scale for the circuit of Figure 2 is given by: 1023 FS = – V REF  ------------  .  1024 11. Nominal LSB magnitude for the circuit of Figure 2 is given by: 1 LSB = V REF  ------------  .  1024 Zero Offset Adjustment 1. Connect all digital inputs to GND. 2. Adjust the offset zero adjust trimpot of the output operational amplifier for 0V ±1mV (Max) at VOUT. Gain Adjustment 1. Connect all digital inputs to V+. 4 AD7533 2. Monitor VOUT for a -VREF (1 - 1/210) reading. 3. To increase VOUT, connect a series resistor, R2, (0Ω to 250Ω) in the IOUT1 amplifier feedback loop. 4. To decrease VOUT, connect a series resistor, R1, (0Ω to 250Ω) between the reference voltage and the VREF terminal. A “Logic 1” input at any digital input forces the corresponding ladder switch to steer the bit current to IOUT1 bus. A “Logic 0” input forces the bit current to IOUT2 bus. For any code the IOUT1 and IOUT2 bus currents are complements of one another. The current amplifier at IOUT2 changes the polarity of IOUT2 current and the transconductance amplifier at IOUT1 output sums the two currents. This configuration doubles the output range. The difference current resulting at zero offset binary code, (MSB = “Logic 1”, all other bits = “Logic 0”), is corrected by using an external resistor, (10MΩ), from VREF to IOUT2 . Bipolar (Offset Binary) Operation The circuit configuration for operating the AD7533 in the bipolar mode is given in Figure 3. Using offset binary digital input codes and positive and negative reference voltage values, 4-Quadrant multiplication can be realized. The “Digital Input Code/Analog Output Value” table for bipolar mode is given in Table 2. ±10V +15V VREF R1 MSB 4 DATA INPUTS LSB R6 10MΩ CR2 AD7533 13 3 15 14 16 1 2 R2 RFEEDBACK IOUT1 IOUT2 R4 5K R3 5K CR1 6 + VOUT 6 + FIGURE 3. BIPOLAR OPERATION (4-QUADRANT MULTIPLICATION) Offset Adjustment TABLE 2. UNlPOLAR BINARY CODE - AD7533 DIGITAL INPUT MSB LSB 1111111111 (NOTE 2) NOMINAL ANALOG OUTPUT 511 -V REF  ---------  512 1 -V REF  ---------  512 0 1 +V REF  ---------  512 511 +V REF  ---------  512 512 +V REF  ---------  512 1000000001 1000000000 0111111111 0000000001 5. Adjust VREF to approximately +10V. 6. Connect all digital inputs to “Logic 1”. 7. Adjust IOUT2 amplifier offset adjust trimpot for 0V ±1mV at IOUT2 amplifier output. 8. Connect MSB (Bit 1) to “Logic 1” and all other bits to “Logic 0”. 9. Adjust IOUT1 amplifier offset adjust trimpot for 0V ±1mV at VOUT. Gain Adjustment 1. Connect all digital inputs to V+. 2. Monitor VOUT for a -VREF (1 - 2-9) volts reading. 3. To increase VOUT, connect a series resistor (R2) of up to 250Ω between VOUT and RFEEDBACK . 4. To decrease VOUT, connect a series resistor (R1) of up to 250Ω between the reference voltage and the VREF terminal. 0000000000 NOTES: 12. VOUT as shown in Figure 3. 13. Nominal Full Scale for the circuit of Figure 3 is given by: 1023 FSR = V REF  ------------  .  512  14. Nominal LSB magnitude for the circuit of Figure 3 is given by: 1LSB = V REF  --------- .  512 5 AD7533 ±10V BIPOLAR ANALOG INPUT V+ VREF MSB 4 MAGNITUDE BITS DIGITAL INPUT LSB GND SIGN BIT AD7533 13 3 15 14 16 1 2 RFEEDBACK OUT1 OUT2 10K 10K 6 + 5K 6 + VOUT 1/ IH5140 2 FIGURE 4. 10-BIT AND SIGN MULTIPLYING DAC CALIBRATE 10K 4.7K 6.8V (2) +15V VDD NC 1K A2 6 + 10K 1% 10K 1% SQUARE WAVE MSB DIGITAL FREQUENCY CONTROL WORD LSB 15 4 14 16 C1 1 2 OUT1 OUT2 AD7533 13 3 A1 6 + TRIANGULAR WAVE FIGURE 5. PROGRAMMABLE FUNCTION GENERATOR +15V VIN RFB 16 2 14 4 BIT 1 MSB LSB DIGITAL INPUT “D” +15V R1 VREF OUT2 AD7533 OUT1 1 3 13 15 VREF 6 + R2 VOUT BIT 1 MSB DIGITAL INPUT “D” BIT 10 15 4 14 16 AD7533 LSB 13 1 2 6 + 6 + VOUT BIT 10 3 VOUT = -VIN/D Where: Bit 8 Bit 1 Bit 2 D = ------------- + ------------- + … ------------2 1 2 2 2 2 255  0 ≤ D ≤ ---------  256 FIGURE 6. DIVIDER (DIGITALLY CONTROLLED GAIN)  R2   R1 D  V OUT = V REF  --------------------- –  ---------------------  R 1 + R 2  R 1 + R 2 Bit 8 Bit 1 Bit 2 Where D = ----------- + ----------- + … ----------8 1 2 2 2 2  0 ≤ D ≤ 255 -------- 256 FIGURE 7. MODIFIED SCALE FACTOR AND OFFSET 6 AD7533 Die Characteristics DIE DIMENSIONS 101 mils x 103 mils (2565µm x 2616µm) METALLIZATION Type: Pure Aluminum Thickness: 10 ±1kÅ PASSIVATION Type: PSG/Nitride PSG: 7 ±1.4kÅ Nitride: 8 ±1.2kÅ PROCESS CMOS Metal Gate Metallization Mask Layout AD7533 PIN 7 BIT 4 PIN 6 BIT 3 PIN 5 BIT 2 PIN 4 BIT 1 (MSB) PIN 3 GND PIN 8 BIT 5 PIN 2 IOUT2 PIN 1 IOUT1 PIN 9 BIT 6 PIN 10 BIT 7 PIN 16 RFEEDBACK PIN 11 BIT 8 (LSB) PIN 15 VREF NC (PIN 12, BIT 9, AD7533) NC NC (PIN 13, BIT 10, AD7533) NC PIN 14 V+ 7 AD7533 Dual-In-Line Plastic Packages (PDIP) N E1 INDEX AREA 12 3 N/2 E16.3 (JEDEC MS-001-BB ISSUE D) 16 LEAD DUAL-IN-LINE PLASTIC PACKAGE INCHES SYMBOL -B- MILLIMETERS MIN 0.39 2.93 0.356 1.15 0.204 18.66 0.13 7.62 6.10 MAX 5.33 4.95 0.558 1.77 0.355 19.68 8.25 7.11 NOTES 4 4 8, 10 5 5 6 5 6 7 4 9 Rev. 0 12/93 MIN 0.015 0.115 0.014 0.045 0.008 0.735 0.005 0.300 0.240 MAX 0.210 0.195 0.022 0.070 0.014 0.775 0.325 0.280 A E A2 L A C L -AD BASE PLANE SEATING PLANE D1 B1 B 0.010 (0.25) M D1 A1 A1 A2 -C- B B1 C D D1 E eA eC C e C A BS eB NOTES: 1. Controlling Dimensions: INCH. In case of conflict between English and Metric dimensions, the inch dimensions control. 2. Dimensioning and tolerancing per ANSI Y14.5M-1982. 3. Symbols are defined in the “MO Series Symbol List” in Section 2.2 of Publication No. 95. 4. Dimensions A, A1 and L are measured with the package seated in JEDEC seating plane gauge GS-3. 5. D, D1, and E1 dimensions do not include mold flash or protrusions. Mold flash or protrusions shall not exceed 0.010 inch (0.25mm). 6. E and eA are measured with the leads constrained to be perpendicular to datum -C- . 7. eB and eC are measured at the lead tips with the leads unconstrained. eC must be zero or greater. 8. B1 maximum dimensions do not include dambar protrusions. Dambar protrusions shall not exceed 0.010 inch (0.25mm). 9. N is the maximum number of terminal positions. 10. Corner leads (1, N, N/2 and N/2 + 1) for E8.3, E16.3, E18.3, E28.3, E42.6 will have a B1 dimension of 0.030 - 0.045 inch (0.76 - 1.14mm). E1 e eA eB L N 0.100 BSC 0.300 BSC 0.115 16 0.430 0.150 2.54 BSC 7.62 BSC 2.93 16 10.92 3.81 All Intersil U.S. products are manufactured, assembled and tested utilizing ISO9000 quality systems. Intersil Corporation’s quality certifications can be viewed at www.intersil.com/design/quality Intersil products are sold by description only. Intersil Corporation reserves the right to make changes in circuit design, software and/or specifications at any time without notice. Accordingly, the reader is cautioned to verify that data sheets are current before placing orders. Information furnished by Intersil is believed to be accurate and reliable. However, no responsibility is assumed by Intersil or its subsidiaries for its use; nor for any infringements of patents or other rights of third parties which may result from its use. No license is granted by implication or otherwise under any patent or patent rights of Intersil or its subsidiaries. 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