MP9403EN-LF

MP9403 3A, 4.3V to7V Input, 250kHz Integrated Synchronous Step-Down Converter The Future of Analog IC Technology DESCRIPTION FEATURES The MP9403 is a monolithic synchronous buck regulator. The device integrates a 150mΩ high-side MOSFET and a 100mΩ low-side MOSFET that provides 3A continuous load current over input voltage of 4.3V to 7V. Current mode control provides fast transient response and cycle-by-cycle current limit. • • • • • • • • • • • An adjustable soft-start prevents inrush current at turn-on. In shutdown mode, the supply current drops to 1μA. This device, available in an 8-pin SOIC package with exposed pad, provides a very compact system solution with minimal reliance on external components. 3A Output Current 4.3V to 7V Operating Input Range Integrated MOSFET Switches Output Adjustable from 0.80V to 5.50V Up to 93% Efficiency Programmable Soft-Start Stable with Low ESR Ceramic Output Capacitors Fixed 250kHz Frequency Cycle-by-Cycle Over Current Protection Input Under Voltage Lockout Thermally Enhanced 8-Pin SOIC Package APPLICATIONS • • • Distributed Power Systems Pre-Regulator for Linear Regulators Notebook Computers “MPS” and “The Future of Analog IC Technology” are Registered Trademarks of Monolithic Power Systems, Inc. TYPICAL APPLICATION Efficiency vs. Load Current VOUT=2.5V 100 INPUT 4.3V to 7V 90 V IN=4.3V 8 1 BS 3 SW MP9403 SS GND FB COMP 4 6 C6 (optional) OUTPUT 2.5V 3A 5 D1 B320 (optional) EFFICIENCY (%) 80 2 IN 7 EN 70 60 V IN=5V 50 40 V IN=7V 30 20 10 0 0.01 0.1 1 10 LOAD CURRENT (A) MP9403 Rev.0.9 4/12/2016 www.MonolithicPower.com MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited. © 2016 MPS. All Rights Reserved. 1 MP9403 – 3A, 7V, 250kHz INTEGRATED SYNCHRONOUS STEP-DOWN CONVERTER ORDERING INFORMATION Part Number* MP9403EN Package SOIC8E Top Marking Free Air Temperature (TA) MP9403EN –20° to +85°C * For Tape & Reel, add suffix –Z (e.g. MP9403EN–Z); For RoHS Compliant Packaging, add suffix –LF (e.g. MP9403 EN –LF–Z) PACKAGE REFERENCE TOP VIEW BS 1 8 SS IN 2 7 EN SW 3 6 COMP GND 4 5 FB CONNECT EXPOSED PAD AND GND PIN TO A CERTAIN GROUND PLANE ABSOLUTE MAXIMUM RATINGS (1) Recommended Operating Conditions Supply Voltage VIN .........................–0.3V to +8V Switch Voltage VSW ................. –1V to VIN + 0.3V Boost Voltage VBS ..........VSW – 0.3V to VSW + 6V All Other Pins .................................–0.3V to +6V (2) Continuous Power Dissipation (TA = +25°C) ............................................................. 2.5W Junction Temperature ...............................150°C Lead Temperature ....................................260°C Storage Temperature ............. –65°C to +150°C Supply Voltage VIN ............................. 4.3V to 7V Output Voltage VOUT ....................... 0.8V to 5.5V Operating Junct. Temp. (TJ)......... –20°C to +125°C MP9403 Rev.0.9 4/12/2016 Thermal Resistance (4) θJA (3) θJC SOIC8E .................................. 50 ...... 10... °C/W Notes: 1) Exceeding these ratings may damage the device. 2) The maximum allowable power dissipation is a function of the maximum junction temperature TJ(MAX), the junction-toambient thermal resistance θJA, and the ambient temperature TA. The maximum allowable continuous power dissipation at any ambient temperature is calculated by PD(MAX)=(TJ(MAX)TA)/ θJA. Exceeding the maximum allowable power dissipation will cause excessive die temperature, and the regulator will go into thermal shutdown. Internal thermal shutdown circuitry protects the device from permanent damage. 3) The device is not guaranteed to function outside of its operating conditions. 4) Measured on JESD51-7 4-layer board. www.MonolithicPower.com MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited. © 2016 MPS. All Rights Reserved. 2 MP9403 – 3A, 7V, 250kHz INTEGRATED SYNCHRONOUS STEP-DOWN CONVERTER ELECTRICAL CHARACTERISTICS (5) VIN = 5V, TA = +25°C, unless otherwise noted. Parameter Shutdown Supply Current Supply Current Feedback Voltage OVP Threshold Voltage Error Amplifier Voltage Gain Error Amplifier Transconductance High-Side Switch-On Resistance Low-Side Switch-On Resistance High-Side Switch Leakage Current Upper Switch Current Limit Lower Switch Current Limit COMP to Current Sense Transconductance Oscillation Frequency Short Circuit Oscillation Frequency Maximum Duty Cycle Minimum On Time EN Shutdown Threshold Voltage EN Threshold Voltage Hysteresis Input Under Voltage Lockout Threshold Input Under Voltage Lockout Threshold Hysterisis Soft-Start Current Thermal Shutdown Symbol Condition VEN = 0V VEN = 2.7V, VFB = 1.0V 4.3V ≤ VIN ≤ 7V, VFB TA = +25°C AEA GEA ΔIC = ±10μA Min 1.45 Max 1.0 1.6 Units μA mA 0.780 0.800 0.820 V 0.90 0.95 400 820 150 100 1.00 4.3 1.25 V V/V μA/V mΩ mΩ μA A A 7 A/V 550 RDS(ON)1 RDS(ON)2 VEN = 0V, VSW = 0V Duty Cycle = 60% From Drain to Source UVLO 3.4 TA = +25°C VFB = 0V VFB = 0.7V 215 VEN Rising 1.0 VIN rising, TA = +25°C 3.3 VSS = 0V 1100 1.0 GCS Fosc1 Fosc2 DMAX Typ (5) 85 250 55 90 180 1.3 205 285 3.65 4.0 1.6 kHz kHz % ns V mV V 45 mV 6 160 μA °C Notes: 5) 100% production test at +25°C. Specifications over the temperature range are guaranteed by design and characterization. MP9403 Rev.0.9 4/12/2016 www.MonolithicPower.com MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited. © 2016 MPS. All Rights Reserved. 3 MP9403 – 3A, 7V, 250kHz INTEGRATED SYNCHRONOUS STEP-DOWN CONVERTER PIN FUNCTIONS Pin # Name 1 BS 2 IN 3 SW 4 5 6 7 8 Description High-Side Gate Drive Boost Input. BS supplies the drive for the high-side N-Channel MOSFET switch. Connect a 0.01μF or greater capacitor from SW to BS to power the high side switch. Power Input. IN supplies the power to the IC, as well as the step-down converter switches. Drive IN with a 4.3V to 7V power source. Bypass IN to GND with a suitably large capacitor to eliminate noise on the input to the IC. See Input Capacitor. Power Switching Output. SW is the switching node that supplies power to the output. Connect the output LC filter from SW to the output load. Note that a capacitor is required from SW to BS to power the high-side switch. GND, Ground. The Exposed Pad and GND pin must be connected to the same ground plane. Exposed Pad Feedback Input. FB senses the output voltage to regulate that voltage. Drive FB with a FB resistive voltage divider from the output voltage. The feedback threshold is 0.80V. See Setting the Output Voltage. Compensation Node. COMP is used to compensate the regulation control loop. Connect a series RC network from COMP to GND to compensate the regulation control COMP loop. In some cases, an additional capacitor from COMP to GND is required. See Compensation Components. Enable Input. EN is a digital input that turns the regulator on or off. Drive EN high to EN turn on the regulator, drive it low to turn it off. Pull up with 100kΩ resistor to IN for automatic startup. Soft-start Control Input. SS controls the soft-start period. Connect a capacitor from SS SS to GND to set the soft-start period. A 0.1μF capacitor sets the soft-start period to 15ms. To disable the soft-start feature, leave SS unconnected. MP9403 Rev.0.9 4/12/2016 www.MonolithicPower.com MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited. © 2016 MPS. All Rights Reserved. 4 MP9403 – 3A, 7V, 250kHz INTEGRATED SYNCHRONOUS STEP-DOWN CONVERTER TYPICAL PERFORMANCE CURVES VIN=5V, VOUT=2.5V, CIN=10μF×2, COUT=22uF×2, L=6.8μH, CSS=0.1μF, TA=25°C, unless otherwise noted. Efficiency vs. Load Current 100 90 Efficiency vs. Load Current VOUT=1.8V 100 90 VIN=4.3V VIN=5V 80 80 70 VIN=7V 60 EFFICIENCY EFFICIENCY VOUT=3.3V VIN=5V 50 40 30 70 50 40 30 20 20 10 0 0.01 10 0 0.1 1 10 VIN=7V 60 0.01 0.1 1 10 LOAD CURRENT(A) LOAD CURRENT(A) Output Ripple Voltage Output Ripple Voltage Enable Startup IO=0A IO=3A IO=0A VO/AC 10mV/div. VO/AC 10mV/div. VSW 5V/div. VSW 5V/div. Iinductor 0.5A/div. VO 1V/div. VEN 5V/div. VSW 5V/div. Iinductor 1A/div. Iinductor 2A/div. Enable Startup Enable Shutdown Enable Shutdown IO=3A IO=0A IO=3A VO 1V/div. VEN 5V/div. VO 1V/div. VEN 5V/div. VSW 5V/div. VSW 5V/div. VO 1V/div. VEN 5V/div. VSW 5V/div. Iinductor 2A/div. Iinductor 1A/div. Iinductor 2A/div. MP9403 Rev.0.9 4/12/2016 www.MonolithicPower.com MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited. © 2016 MPS. All Rights Reserved. 5 MP9403 – 3A, 7V, 250kHz INTEGRATED SYNCHRONOUS STEP-DOWN CONVERTER BLOCK DIAGRAM IN + VOUT CURRENT SENSE AMPLIFIER OVP 0.95V -OSCILLATOR FB + 250kHz 0.3V RAMP BS ---- + 0.8V 5V -- CLK + SS + VIN + ERROR AMPLIFIER S Q R Q SW CURRENT COMPARATOR VOUT COMP GND EN OVP 1.2V IN < 3.65V IN -- 1.3 V + INTERNAL REGULATORS SHUTDOWN COMPARATOR Figure 1—Function Block Diagram OPERATION FUNCTIONAL DESCRIPTION The MP9403 is a fully-integrated synchronous current-mode step-down regulator. It regulates input voltages from 4.3V to 7V down to an output voltage as low as 0.80V, and supplies up to 3A of load current. The MP9403 uses current-mode control to regulate the output voltage. The output voltage is measured at FB through a resistive voltage divider and amplified through the internal transconductance error amplifier. The voltage at COMP pin is compared with the switch current measured internally to control the output voltage. MP9403 Rev.0.9 4/12/2016 The converter uses internal N-Channel MOSFET switches to step-down the input voltage to the regulated output voltage. Since the high side MOSFET requires a gate voltage greater than the input voltage, a boost capacitor connected between SW and BS is needed to drive the high-side gate. The boost capacitor is charged from the internal 5V rail when SW is low. When the MP9403 FB pin exceeds 20% of the nominal regulation voltage of 0.80V, the over voltage comparator is tripped and latched; the COMP pin and the SS pin are discharged to GND, forcing the high-side switch off. www.MonolithicPower.com MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited. © 2016 MPS. All Rights Reserved. 6 MP9403 – 3A, 7V, 250kHz INTEGRATED SYNCHRONOUS STEP-DOWN CONVERTER APPLICATIONS INFORMATION COMPONENT SELECTION Setting the Output Voltage The output voltage is set using a resistive voltage divider from the output voltage to FB pin. The voltage divider divides the output voltage down to the feedback voltage by the ratio: VFB = VOUT R2 R1 + R2 larger value inductor will have a larger physical size, higher series resistance, and/or lower saturation current. A good rule for determining the inductance value is to allow the peak-to-peak ripple current in the inductor to be approximately 30% of the maximum switching current limit. Also, make sure that the peak inductor current is below the maximum switch current limit. The inductance value can be calculated by: L= Thus the output voltage is: VOUT = 0.80 × R1 + R2 R2 Where VFB is the feedback voltage and VOUT is the output voltage. R2 can be as high as 100kΩ, but a typical value is 10kΩ. Using that value, R1 is determined by: ⎞ V VOUT ⎛ × ⎜1 − OUT ⎟⎟ fS × ΔI ⎜⎝ VIN ⎠ Where VIN is the input voltage, fS is the 250kHz switching frequency, and ΔIL is the peak-to-peak inductor ripple current. Choose an inductor that will not saturate under the maximum inductor peak current. The peak inductor current can be calculated by: ⎛ V VOUT × ⎜⎜1 − OUT VIN 2 × fS × L ⎝ R1 = 12.5 × ( VOUT − 0.80)(kΩ) ILP = ILOAD + For example, for a 3.3V output voltage, R2 is 10kΩ, and R1 is 31.6kΩ. Where ILOAD is the load current. Inductor The inductor is required to supply constant current to the output load while being driven by the switched input voltage. A larger value inductor will result in less ripple current that will result in lower output ripple voltage. However, the ⎞ ⎟⎟ ⎠ Table 1 lists a number of suitable inductors from various manufacturers. The choice of which style inductor to use mainly depends on the price vs. size requirements and any EMI requirement. Table 1—Inductor Selection Guide Inductance (µH) Max DCR (Ω) Current Rating (A) Dimensions L x W x H (mm3) 744777004 4.7 0.040 4.0 7.3x7.3x4.5 7440650068 6.8 0.033 3.6 10x10x2.8 744066100 10 0.035 3.6 10x10x3.8 VLF10040T-4R7N5R4 4.7 0.015 5.4 10x9.7x4 VLF10040T-6R8N4R5 6.8 0.023 4.5 10x9.7x4 VLF10040T-100M3R8 10 0.033 3.8 10x9.7x4 Part Number Wurth Electronics TDK Toko 1010ASW-4R7M 4.7 0.015 4.4 12.3x12.3x4.5 B992AS-6R8N 6.8 0.028 3.8 8.3x8.3x6.8 1010ASW-100M 10 0.022 3.6 12.3x12.3x4.5 MP9403 Rev.0.9 4/12/2016 www.MonolithicPower.com MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited. © 2016 MPS. All Rights Reserved. 7 MP9403 – 3A, 7V, 250kHz INTEGRATED SYNCHRONOUS STEP-DOWN CONVERTER Optional Schottky Diode During the transition between high-side switch and low-side switch, the body diode of the lowside power MOSFET conducts the inductor current. The forward voltage of this body diode is high. An optional Schottky diode may be paralleled between the SW pin and GND pin to improve overall efficiency. Table 2 lists example Schottky diodes and their Manufacturers. Table 2—Diode Selection Guide Voltage/Current Part Number Rating B320 20V, 3A B320A 20V, 3A SS32 20V, 3A Vendor Diodes, Inc. Diodes, Inc. Vishay, Inc. Input Capacitor The input current to the step-down converter is discontinuous, therefore a capacitor is required to supply the AC current to the step-down converter while maintaining the DC input voltage. Use low ESR capacitors for the best performance. Ceramic capacitors are preferred, but low-ESR electrolytic capacitors may also suffice. Choose X5R or X7R dielectrics when using ceramic capacitors. Since the input capacitor (C1) absorbs the input switching current it requires an adequate ripple current rating. The RMS current in the input capacitor can be estimated by: IC1 = ILOAD × VOUT V × (1 − OUT ) VIN VIN The worst-case condition occurs at VIN = 2VOUT, where: I C1 = ILOAD 2 For simplification, choose an input capacitor with an RMS current rating greater than half of the maximum load current. The input capacitor can be electrolytic, tantalum or ceramic. When using electrolytic or tantalum capacitors, a small, high quality ceramic capacitor (i.e. 0.1μF), should be placed as close to the IC as possible. When using ceramic capacitors, make sure that they have enough capacitance to provide sufficient charge to prevent excessive voltage ripple at input. The input voltage ripple caused by capacitance can be estimated by: MP9403 Rev.0.9 4/12/2016 ΔVIN = ⎛ ILOAD V V × OUT × ⎜⎜1 − OUT f S × C1 VIN VIN ⎝ ⎞ ⎟⎟ ⎠ Output Capacitor The output capacitor is required to maintain the DC output voltage. Ceramic, tantalum, or low ESR electrolytic capacitors are recommended. Low ESR capacitors are preferred to keep the output voltage ripple low. The output voltage ripple can be estimated by: ΔVOUT = VOUT ⎛ V × ⎜⎜1 − OUT fS × L ⎝ VIN ⎞ ⎞ ⎛ 1 ⎟ ⎟⎟ × ⎜ R ESR + ⎜ 8 × f S × C2 ⎟⎠ ⎠ ⎝ Where C2 is the output capacitance value and RESR is the equivalent series resistance (ESR) value of the output capacitor. In the case of ceramic capacitors, the impedance at the switching frequency is dominated by the capacitance. The output voltage ripple is mainly caused by the capacitance. For simplification, the output voltage ripple can be estimated by: ΔVOUT = ⎛ V × ⎜⎜1 − OUT VIN × L × C2 ⎝ VOUT 8 × fS 2 ⎞ ⎟⎟ ⎠ In the case of tantalum or electrolytic capacitors, the ESR dominates the impedance at the switching frequency. For simplification, the output ripple can be approximated to: ΔVOUT = VOUT ⎛ V ⎞ × ⎜1 − OUT ⎟⎟ × R ESR f S × L ⎜⎝ VIN ⎠ The characteristics of the output capacitor also affect the stability of the regulation system. The MP9403 can be optimized for a wide range of capacitance and ESR values. Compensation Components MP9403 employs current mode control for easy compensation and fast transient response. The system stability and transient response are controlled through the COMP pin. COMP pin is the output of the internal transconductance error amplifier. A series capacitor-resistor combination sets a pole-zero combination to control the characteristics of the control system. The DC gain of the voltage feedback loop is given by: A VDC = R LOAD × G CS × A VEA × www.MonolithicPower.com MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited. © 2016 MPS. All Rights Reserved. VFB VOUT 8 MP9403 – 3A, 7V, 250kHz INTEGRATED SYNCHRONOUS STEP-DOWN CONVERTER Where AVEA is the error amplifier voltage gain, 400V/V; GCS is the current sense transconductance, 7.0A/V; RLOAD is the load resistor value. The system has 2 poles of importance. One is due to the compensation capacitor (C3) and the output resistor of error amplifier, and the other is due to the output capacitor and the load resistor. These poles are located at: fP1 = GEA 2π × C3 × A VEA fP2 = 1 2π × C2 × R LOAD Where GEA is the error amplifier transconductance, 820μA/V, and RLOAD is the load resistor value. The system has one zero of importance, due to the compensation capacitor (C3) and the compensation resistor (R3). This zero is located at: f Z1 1 = 2π × C3 × R3 The system may have another zero of importance, if the output capacitor has a large capacitance and/or a high ESR value. The zero, due to the ESR and capacitance of the output capacitor, is located at: fESR = 1 2π × C2 × R ESR In this case, a third pole set by the compensation capacitor (C6) and the compensation resistor (R3) is used to compensate the effect of the ESR zero on the loop gain. This pole is located at: fP 3 = 1 2π × C6 × R3 The goal of compensation design is to shape the converter transfer function to get a desired loop gain. The system crossover frequency where the feedback loop has the unity gain is important. Lower crossover frequencies result in slower line and load transient responses, while higher crossover frequencies could cause system unstable. A good rule of thumb is to set the crossover frequency to approximately one-tenth of the switching frequency. Switching frequency for the MP9403 is 250kHz, so the desired crossover frequency is 25kHz. Table 3 lists the typical values of compensation components for some standard output voltages with various output capacitors and inductors. The values of the compensation components have been optimized for fast transient responses and good stability at given conditions. To optimize the compensation components for conditions not listed in Table 3, the following procedure can be used. 1. Choose the compensation resistor (R3) to set the desired crossover frequency. Determine the R3 value by the following equation: R3 = 2π × C2 × f C VOUT × G EA × G CS VFB Where fC is the desired crossover frequency, 25kHz. 2. Choose the compensation capacitor (C3) to achieve the desired phase margin. For applications with typical inductor values, setting the compensation zero, fZ1, below one forth of the crossover frequency provides sufficient phase margin. Determine the C3 value by the following equation: C3 > 4 2π × R3 × f C Table 3—Compensation Values for Typical Output Voltage/Capacitor Combinations VOUT L 1.2V 4.7uH 1.8V 6.8μH 2.5V 6.8μH 3.3V 6.8μH C2 22μFx2 Ceramic 22μFx2 Ceramic 22μFx2 Ceramic 22μFx2 Ceramic R3 C3 C6 2.4kΩ 6.8nF None 4.3kΩ 6.8nF None 6.8kΩ 4.7nF None 8.2kΩ 2.2nF None 3. Determine if the second compensation capacitor (C6) is required. It is required if the ESR zero of the output capacitor is located at less than half of the 250kHz switching frequency, or the following relationship is valid: f 1 < S 2π × C2 × R ESR 2 MP9403 Rev. 0.9 4/12/2016 www.MonolithicPower.com MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited. © 2016 MPS. All Rights Reserved. 9 MP9403 – 3A, 7V, 250kHz INTEGRATED SYNCHRONOUS STEP-DOWN CONVERTER If this is the case, then add the second compensation capacitor (C6) to set the pole fP3 at the location of the ESR zero. Determine the C6 value by the equation: C6 = C2 × R ESR R3 External Bootstrap Diode An external bootstrap diode may enhance the efficiency of the regulator, the applicable conditions of external BST diode are: z VOUT is 5V or 3.3V; and z Duty cycle is high: D= MP9403 Rev.0.9 4/12/2016 VOUT >65% VIN In these cases, an external BST diode is recommended from the output of the voltage regulator to BST pin, as shown in Fig.2 MP9403 Figure 2—Add Optional External Bootstrap Diode to Enhance Efficiency The recommended external BST diode is IN4148. www.MonolithicPower.com MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited. © 2016 MPS. All Rights Reserved. 10 MP9403 – 3A, 7V, 250kHz INTEGRATED SYNCHRONOUS STEP-DOWN CONVERTER TYPICAL APPLICATION CIRCUITS INPUT 4.3V to 7V 7 8 2 IN EN 1 BS 3 SW MP9403 SS GND FB COMP 4 OUTPUT 1.8V 3A 5 D1 B320 (optional) 6 C6 (optional) Figure 3—MP9403 with 1.8V Output Typical Application Schematic INPUT 5V to 7V 7 8 2 IN EN 1 BS 3 SW MP9403 SS GND FB COMP 4 6 C6 (optional) OUTPUT 3.3V 3A 5 D1 B320 (optional) Figure 4—MP9403 with 3.3V Output Typical Application Schematic MP9403 Rev. 0.9 4/12/2016 www.MonolithicPower.com MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited. © 2016 MPS. All Rights Reserved. 11 MP9403 – 3A, 7V, 250kHz INTEGRATED SYNCHRONOUS STEP-DOWN CONVERTER PCB Layout Guide 2) PCB layout is very important to achieve stable operation. It is highly recommended to duplicate EVB layout for optimum performance. Bypass ceramic capacitors are suggested to be put close to the Vin Pin. 3) Ensure all feedback connections are short and direct. Place the feedback resistors and compensation components as close to the chip as possible. 4) Rout SW away from sensitive analog areas such as FB. 5) Connect IN, SW, and especially GND respectively to a large copper area to cool the chip to improve thermal performance and long-term reliability. If change is necessary, please follow these guidelines and take Figure 5 for reference. 1) Keep the path of switching current short and minimize the loop area formed by Input cap, high-side MOSFET and low-side MOSFET. C5 INPUT R4 2 7 8 C1 1 IN BS SW EN MP9403 SS GND 4 FB COMP OUTPUT R1 5 6 C3 C4 L1 3 D1 (optional) R2 C2 R3 MP9403 Typical Application Circuit R3 COMP 6 3 SW FB 5 EN 7 C3 2 IN C4 SS 8 R4 PGND R1 R2 SGND R1 C5 4 GND 1 BS PGND D1 C2 C1 L1 Top Layer Bottom Layer Figure 5—MP9403 Typical Application Circuit and PCB Layout Guide MP9403 Rev.0.9 4/12/2016 www.MonolithicPower.com MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited. © 2016 MPS. All Rights Reserved. 12 MP9403 – 3A, 7V, 250kHz INTEGRATED SYNCHRONOUS STEP-DOWN CONVERTER PACKAGE INFORMATION SOIC8E 0.189(4.80) 0.197(5.00) 8 0.124(3.15) 0.136(3.45) 5 0.150(3.80) 0.157(4.00) PIN 1 ID 1 0.228(5.80) 0.244(6.20) 0.089(2.26) 0.101(2.56) 4 TOP VIEW BOTTOM VIEW SEE DETAIL "A" 0.013(0.33) 0.020(0.51) 0.051(1.30) 0.067(1.70) SEATING PLANE 0.000(0.00) 0.006(0.15) 0.0075(0.19) 0.0098(0.25) SIDE VIEW 0.050(1.27) BSC FRONT VIEW 0.010(0.25) x 45o 0.020(0.50) GAUGE PLANE 0.010(0.25) BSC 0.050(1.27) 0.024(0.61) 0o-8o 0.016(0.41) 0.050(1.27) 0.063(1.60) DETAIL "A" 0.103(2.62) 0.138(3.51) RECOMMENDED LAND PATTERN 0.213(5.40) NOTE: 1) CONTROL DIMENSION IS IN INCHES. DIMENSION IN BRACKET IS IN MILLIMETERS. 2) PACKAGE LENGTH DOES NOT INCLUDE MOLD FLASH, PROTRUSIONS OR GATE BURRS. 3) PACKAGE WIDTH DOES NOT INCLUDE INTERLEAD FLASH OR PROTRUSIONS. 4) LEAD COPLANARITY (BOTTOM OF LEADS AFTER FORMING) SHALL BE 0.004" INCHES MAX. 5) DRAWING CONFORMS TO JEDEC MS-012, VARIATION BA. 6) DRAWING IS NOT TO SCALE. NOTICE: The information in this document is subject to change without notice. Please contact MPS for current specifications. Users should warrant and guarantee that third party Intellectual Property rights are not infringed upon when integrating MPS products into any application. MPS will not assume any legal responsibility for any said applications. MP9403 Rev.0.9 4/12/2016 www.MonolithicPower.com MPS Proprietary Information. Unauthorized Photocopy and Duplication Prohibited. © 2016 MPS. All Rights Reserved. 13