ADC11DL066CIVS

ADC11DL066 Dual 11-Bit, 66 MSPS, 450 MHz Input Bandwidth A/D Converter w/Internal Reference February 1, 2008 ADC11DL066 Dual 11-Bit, 66 MSPS, 450 MHz Input Bandwidth A/D Converter w/Internal Reference General Description The ADC11DL066 is a dual, low power monolithic CMOS analog-to-digital converter capable of converting analog input signals into 11-bit digital words at 66 Megasamples per second (MSPS), minimum. This converter uses a differential, pipeline architecture with digital error correction and an onchip sample-and-hold circuit to minimize die size and power consumption while providing excellent dynamic performance and a 450 MHz Full Power Bandwidth. Operating on a single 3.3V power supply, the ADC11DL066 achieves 10.3 effective bits and consumes just 686 mW at 66 MSPS, including the reference current. The Power Down feature reduces power consumption to 75 mW. The differential inputs provide a full scale differential input swing equal to 2 times VREF with the possibility of a singleended input. Full use of the differential input is recommended for optimum performance. The digital outputs from the two ADCs are available on separate 11-bit buses with an output data format choice of offset binary or two’s complement. To ease interfacing to lower voltage systems, the digital output driver power pins of the ADC11DL066 can be connected to a separate supply voltage in the range of 2.4V to the digital supply voltage. This device is available in the 64-lead TQFP package and will operate over the industrial temperature range of −40°C to +85°C. An evaluation board is available to ease the evaluation process. Features ■ ■ ■ ■ ■ Binary or 2’s complement output format Single +3.3V supply operation Outputs 2.4V to 3.3V compatible Power down mode On-chip reference Key Specifications ■ ■ ■ ■ ■ ■ ■ ■ Resolution DNL SNR (fIN = 10 MHz) SFDR (fIN = 10 MHz) Data Latency Power Consumption Operating Power Down 11 Bits ±0.25 LSB (typ) 64 dB (typ) 80 dB (typ) 6 Clock Cycles 686 mW (typ) 75 mW (typ) Applications ■ ■ ■ ■ ■ ■ ■ Ultrasound and Imaging Instrumentation Communications Receivers Sonar/Radar xDSL Cable Modems DSP Front Ends Connection Diagram 20077301 TRI-STATE® is a registered trademark of National Semiconductor Corporation. © 2008 National Semiconductor Corporation 200773 www.national.com ADC11DL066 Ordering Information Industrial (−40°C ≤ TA ≤ +85°C) ADC11DL066CIVS Use ADC12DL066EVAL Package 64 Pin TQFP Evaluation Board Block Diagram 20077302 www.national.com 2 ADC11DL066 Pin Descriptions and Equivalent Circuits Pin No. ANALOG I/O 15 2 16 1 VINA+ VINB+ VINA− VINB− Differential analog Inputs. With a 1.0V reference voltage the differential full-scale input signal level is 2.0 VP-P with each input pin voltage centered on a common mode voltage, VCM. The negative input pins may be connected to VCM for single-ended operation, but a differential input signal is required for best performance. Reference input. This pin should be bypassed to AGND with a 0.1 µF capacitor when an external reference is used. VREF is 1.0V nominal and should be between 0.8V to 1.5V. Reference source select pin. With a logic low at this pin the internal 1.0V reference is selected and the VREF pin need not be driven. With a logic high on this pin an external reference voltage should be applied to VREF input pin 7. Symbol Equivalent Circuit Description 7 VREF 11 INT/EXT REF 13 5 14 4 VRPA VRPB VRMA VRMB These pins are high impedance reference bypass pins; they are not reference output pins. Bypass per Section 1.2. DO NOT LOAD these pins. 12 6 VRNA VRNB DIGITAL I/O 60 CLK Digital clock input. The range of frequencies for this input is as specified in the electrical tables with guaranteed performance at 66 MHz. The input is sampled on the rising edge of this input. OEA and OEB are the output enable pins that, when low, holds their respective data output pins in the active state. When either of these pins is high, the corresponding outputs are in a high impedance state. PD is the Power Down input pin. When high, this input puts the converter into the power down mode. When this pin is low, the converter is in the active mode. Output Format pin. A logic low on this pin causes output data to be in offset binary format. A logic high on this pin causes the output data to be in 2’s complement format. 22 41 OEA OEB 59 PD 21 OF 3 www.national.com ADC11DL066 Pin No.   25 – 29 34 – 39     43–47 52–57   Symbol Equivalent Circuit Description DA0–DA10 Digital data output pins that make up the 11-bit conversion results of their respective converters. DA0 and DB0 are the LSBs, while DA10 and DB10 are the MSBs of the output words. Output levels are TTL/CMOS compatible. DB0–DB10 ANALOG POWER 9, 18, 19, 62, 63 3, 8, 10, 17, 20, 61, 64 DIGITAL POWER Positive digital supply pin. This pin should be connected to the same quiet +3.3V source as is VA and be bypassed to DGND with a 0.1 µF capacitor located within 1 cm of the power pin and with a 10 µF capacitor. The ground return for the digital supply. These two pins are grounded internally and may be grounded or left unconnected. Positive digital supply pin for the ADC11DL066's output drivers. This pin should be connected to a voltage source of +2.4V to VD and be bypassed to DR GND with a 0.1 µF capacitor. If the supply for this pin is different from the supply used for VA and VD, it should also be bypassed with a 10 µF capacitor. VDR should never exceed the voltage on VD. All bypass capacitors should be located within 1 cm of the supply pin. The ground return for the digital supply for the ADC11DL066's output drivers. These pins should be connected to the system digital ground, but not be connected in close proximity to the ADC11DL066's DGND or AGND pins. See Section 5 (Layout and Grounding) for more details. Positive analog supply pins. These pins should be connected to a quiet +3.3V source and bypassed to AGND with 0.1 µF capacitors located within 1 cm of these power pins, and with a 10 µF capacitor. The ground return for the analog supply. VA AGND 33, 48 VD 32, 49 24, 42 DGND DGND 30, 51 VDR 23, 31, 40, 50, 58 DR GND www.national.com 4 ADC11DL066 Absolute Maximum Ratings (Notes 1, 2) If Military/Aerospace specified devices are required, please contact the National Semiconductor Sales Office/ Distributors for availability and specifications. VA, VD, VDR |VA–VD| Voltage on Any Input or Output Pin 4.2V Operating Ratings Operating Temperature Supply Voltage (VA, VD) Output Driver Supply (VDR) VREF Input CLK, PD, OE Analog Input Pins Common Mode Input Voltage VCM |AGND–DGND| (Notes 1, 2) −40°C ≤ TA ≤ +85°C +3.0V to +3.6V +2.4V to VD 0.8V to 1.5V −0.05V to (VD + 0.05V) 0V to (VA − 0.5V) 0.5V to 1.8V Input Current at Any Pin (Note 3) Package Input Current (Note 3) Package Dissipation at TA = 25°C ESD Susceptibility Human Body Model (Note 5) 2500V Machine Model (Note 5) 250V Soldering Temperature, Infrared, 10 sec. (Note 6) 235°C Storage Temperature −65°C to +150°C ≤ 100 mV −0.3V to (VA or VD +0.3V) ±25 mA ±50 mA See (Note 4) ≤100mV Package Thermal Resistance Package 64-Lead TQFP θJ-A 50°C / W Converter Electrical Characteristics Unless otherwise specified, the following specifications apply for AGND = DGND = DR GND = 0V, VA = VD = +3.3V, VDR = +2.5V, PD = 0V, INT/EXT REF pin = +3.3V, VREF = +1.0V, fCLK = 66 MHz, fIN = 10 MHz, tr = tf = 2 ns, CL = 15 pF/pin. Boldface limits apply for TJ = TMIN to TMAX: all other limits TJ = 25°C (Notes 7, 8, 9) Symbol Parameter Conditions Typical Limits (Note 10) (Note 10) 11 ±0.5 ±0.25 0.4 −0.1 −40°C ≤ TA ≤ +85°C 0.5 −0.18 −40°C ≤ TA ≤ +85°C 0.1 0 2047 0 2047 0.5 1.8 V (min) V (max) pF pF 0.8 1.5 V (min) V (max) MΩ MHz dB 62 dB (min) dB dB 62 dB (min) dB +1.3 -1.6 ±1.6 ±0.68 ±4 ±3.6 Units (Limits) Bits (min) LSB (max) LSB (max) %FS (max) %FS (max) ppm/°C %FS (max) %FS (min) ppm/°C STATIC CONVERTER CHARACTERISTICS Resolution with No Missing Codes INL DNL PGE NGE TC GE VOFF Integral Non Linearity (Note 11) Differential Non Linearity Positive Gain Error Negative Gain Error Gain Error Tempco Offset Error (VIN+ = VIN−) TC VOFF Offset Error Tempco Under Range Output Code Over Range Output Code REFERENCE AND ANALOG INPUT CHARACTERISTICS VCM CIN VREF Common Mode Input Voltage VIN Input Capacitance (each pin to GND) Reference Voltage (Note 13) Reference Input Resistance DYNAMIC CONVERTER CHARACTERISTICS FPBW SNR Full Power Bandwidth Signal-to-Noise Ratio 0 dBFS Input, Output at −3 dB fIN = 1 MHz, VIN = −0.5 dBFS fIN = 10 MHz, VIN = −0.5 dBFS fIN = 33 MHz, VIN = −0.5 dBFS fIN = 1 MHz, VIN = −0.5 dBFS SINAD Signal-to-Noise and Distortion fIN = 10 MHz, VIN = −0.5 dBFS fIN = 33 MHz, VIN = −0.5 dBFS 450 64 64 62 63 63 62 VIN = 2.5 Vdc + 0.7 Vrms (CLK LOW) (CLK HIGH) 1.0 8 7 1.00 100 5 www.national.com ADC11DL066 Symbol Parameter Conditions fIN = 1 MHz, VIN = −0.5 dBFS Typical Limits (Note 10) (Note 10) 10.3 10.3 10.1 −78 −78 −78 −84 −84 −84 −84 −84 −83 80 80 74 ±0.03 ±0.1 73.5 −73.3 −73.5 -69.7 10.0 Units (Limits) Bits Bits (min) Bits dB dB (max) dB dB dB (max) dB dB dB (max) dB dB dB (min) dB %FS %FS dB dB ENOB Effective Number of Bits fIN = 10 MHz, VIN = −0,5 dBFS fIN = 33 MHz, VIN = −0,5 dBFS fIN = 1 MHz, VIN = −0.5 dBFS THD Total Harmonic Distortion fIN = 10 MHz, VIN = −0.5 dBFS fIN = 33 MHz, VIN = −0.5 dBFS fIN = 1 MHz, VIN = −0.5 dBFS H2 Second Harmonic fIN = 10 MHz, VIN = −0.5 dBFS fIN = 33 MHz, VIN = −0.5 dBFS fIN = 1 MHz, VIN = −0.5 dBFS H3 Third Harmonic fIN = 10 MHz, VIN = −0.5 dBFS fIN = 33 MHz, VIN = −0.5 dBFS fIN = 1 MHz, VIN = −0.5 dBFS SFDR Spurious Free Dynamic Range fIN = 10 MHz, VIN = −0.5 dBFS fIN = 33 MHz, VIN = −0.5 dBFS INTER-CHANNEL CHARACTERISTICS Channel—Channel Offset Match Channel—Channel Channel gain Match 10 MHz Tested, Channel; 20 MHz Other Channel 10 MHz Tested, Channel; 195 MHz Other Channel 80 63 Crosstalk DC and Logic Electrical Characteristics Unless otherwise specified, the following specifications apply for AGND = DGND = DR GND = 0V, VA = VD = +3.3V, VDR = +2.5V, PD = 0V, INT/EXT REF pin = 3.3V, VREF = +1.0V, fCLK = 66 MHz, fIN = 10 MHz, tr = tf = 2 ns, CL = 15 pF/pin. Boldface limits apply for TJ = TMIN to TMAX: all other limits TJ = 25°C (Notes 7, 8, 9) Symbol Parameter Conditions Typical Limits (Note 10) (Note 10) 2.0 1.0 10 −10 5 VDR = 2.5V VDR = 3V 100 −100 −20 20 5 PD Pin = DGND, VREF = 1.0V PD Pin = VDR PD Pin = DGND PD Pin = VDR, fCLK = 0 6 Units (Limits) V (min) V (max) µA µA pF CLK, PD, OE DIGITAL INPUT CHARACTERISTICS VIN(1) VIN(0) IIN(1) IIN(0) CIN Logical “1” Input Voltage Logical “0” Input Voltage Logical “1” Input Current Logical “0” Input Current Digital Input Capacitance VD = 3.6V VD = 3.0V VIN = 3.3V VIN = 0V D0–D11 DIGITAL OUTPUT CHARACTERISTICS VOUT(1) VOUT(0) IOZ +ISC −ISC COUT Logical “1” Output Voltage Logical “0” Output Voltage TRI-STATE® Output Current Output Short Circuit Source Current Output Short Circuit Sink Current Digital Output Capacitance IOUT = −0.5 mA IOUT = 1.6 mA, VDR = 3V VOUT = 2.5V or 3.3V VOUT = 0V VOUT = 0V VOUT = VDR 2.3 2.7 0.4 V (min) V (min) V (max) nA nA mA mA pF 237 35 mA (max) mA mA (max) mA POWER SUPPLY CHARACTERISTICS IA ID Analog Supply Current Digital Supply Current 197 14 11 8.7 www.national.com ADC11DL066 Symbol IDR Parameter Digital Output Supply Current Total Power Consumption Conditions PD Pin = DGND, CL = 0 pF (Note 14) PD Pin = VDR, fCLK = 0 PD Pin = DGND, CL = 0 pF (Note 15) PD Pin = VDR, fCLK = 0 Rejection of Full-Scale Error with VA = 3.0V vs. 3.6V Rejection of Power Supply Noise with 10 MHz, 500 mV riding on VA Typical Limits (Note 10) (Note 10) VA), the current at that pin should be limited to 25 mA. The 50 mA maximum package input current rating limits the number of pins that can safely exceed the power supplies with an input current of 25 mA to two. Note 4: The absolute maximum junction temperature (TJmax) for this device is 150°C. The maximum allowable power dissipation is dictated by TJmax, the junction-to-ambient thermal resistance (θJA), and the ambient temperature, (TA), and can be calculated using the formula PDMAX = (TJmax - TA ) / θJA. The values for maximum power dissipation will only be reached when the device is operated in a severe fault condition (e.g. when input or output pins are driven beyond the power supply voltages, or the power supply polarity is reversed). Obviously, such conditions should always be avoided. Note 5: Human body model is 100 pF capacitor discharged through a 1.5 kΩ resistor. Machine model is 220 pF discharged through 0Ω. Note 6: The 235°C reflow temperature refers to infrared reflow. For Vapor Phase Reflow (VPR), the following Conditions apply: Maintain the temperature at the top of the package body above 183°C for a minimum 60 seconds. The temperature measured on the package body must not exceed 220°C. Only one excursion above 183°C is allowed per reflow cycle. Note 7: The inputs are protected as shown below. Input voltage magnitudes above VA or below GND will not damage this device, provided current is limited per (Note 3). However, errors in the A/D conversion can occur if the input goes above VA or below GND by more than 100 mV. As an example, if VA is +3.3V, the full-scale input voltage must be ≤+3.4V to ensure accurate conversions. 7 www.national.com ADC11DL066 20077307 Note 8: To guarantee accuracy, it is required that |VA–VD| ≤ 100 mV and separate bypass capacitors are used at each power supply pin. Note 9: With the test condition for VREF = +1.0V (2VP-P differential input), the 11-bit LSB is 976 µV. Note 10: Typical figures are at TJ = 25°C, and represent most likely parametric norms. Test limits are guaranteed to National's AOQL (Average Outgoing Quality Level). Note 11: Integral Non Linearity is defined as the deviation of the analog value, expressed in LSBs, from the straight line that passes through positive and negative full-scale. Note 12: Timing specifications are tested at TTL logic levels, VIL = 0.4V for a falling edge and VIH = 2.4V for a rising edge. Note 13: Optimum performance will be obtained by keeping the reference input in the 0.8V to 1.5V range. The LM4051CIM3-ADJ (SOT-23 package) is recommended for external reference applications. Note 14: IDR is the current consumed by the switching of the output drivers and is primarily determined by load capacitance on the output pins, the supply voltage, VDR, and the rate at which the outputs are switching (which is signal dependent). IDR=VDR(C0 x f0 + C1 x f1 +....C10 x f10) where VDR is the output driver power supply voltage, Cn is total capacitance on the output pin, and fn is the average frequency at which that pin is toggling. Note 15: Excludes IDR. See note 14. www.national.com 8 ADC11DL066 Specification Definitions APERTURE DELAY is the time after the rising edge of the clock to when the input signal is acquired or held for conversion. APERTURE JITTER (APERTURE UNCERTAINTY) is the variation in aperture delay from sample to sample. Aperture jitter manifests itself as noise in the output. CLOCK DUTY CYCLE is the ratio of the time during one cycle that a repetitive digital waveform is high to the total time of one period. The specification here refers to the ADC clock input signal. COMMON MODE VOLTAGE (VCM) is the common d.c. voltage applied to both input terminals of the ADC. CONVERSION LATENCY is the number of clock cycles between initiation of conversion and when that data is presented to the output driver stage. Data for any given sample is available at the output pins the Pipeline Delay plus the Output Delay after the sample is taken. New data is available at every clock cycle, but the data lags the conversion by the pipeline delay. CROSSTALK is coupling of energy from one channel into the other channel. DIFFERENTIAL NON-LINEARITY (DNL) is the measure of the maximum deviation from the ideal step size of 1 LSB. EFFECTIVE NUMBER OF BITS (ENOB, or EFFECTIVE BITS) is another method of specifying Signal-to-Noise and Distortion or SINAD. ENOB is defined as (SINAD - 1.76) / 6.02 and says that the converter is equivalent to a perfect ADC of this (ENOB) number of bits. FULL POWER BANDWIDTH is a measure of the frequency at which the reconstructed output fundamental drops 3 dB below its low frequency value for a full scale input. GAIN ERROR is the deviation from the ideal slope of the transfer function. It can be calculated as: G.E. = Pos. Full-Scale Error − Neg. Full-Scale Error Gain Error can also be separated into Positive Gain Error (PGE) and Negative Gain Error (NGE), which are. PGE = Pos. Full-Scale Error − Offset Error NGE = Offset Error − Neg. Full-Scale Error GAIN ERROR MATCHING is the difference in gain errors between the two converters divided by the average gain of the converters. INTEGRAL NON LINEARITY (INL) is a measure of the deviation of each individual code from a line drawn from negative full scale (½ LSB below the first code transition) through positive full scale (½ LSB above the last code transition). The deviation of any given code from this straight line is measured from the center of that code value. INTERMODULATION DISTORTION (IMD) is the creation of additional spectral components as a result of two sinusoidal frequencies being applied to the ADC input at the same time. It is defined as the ratio of the power in the intermodulation products to the total power in the original frequencies. IMD is usually expressed in dBFS. LSB (LEAST SIGNIFICANT BIT) is the bit that has the smallest value or weight of all bits. This value is VREF/2n, where “n” is the ADC resolution in bits, which is 11 in the case of the ADC11DL066. MISSING CODES are those output codes that will never appear at the ADC outputs. The ADC11DL066 is guaranteed not to have any missing codes. MSB (MOST SIGNIFICANT BIT) is the bit that has the largest value or weight. Its value is one half of full scale. NEGATIVE FULL SCALE ERROR is the difference between the actual first code transition and its ideal value of ½ LSB above negative full scale. OFFSET ERROR is the difference between the two input voltages [(VIN+) – (VIN−)] required to cause a transition from code 1023 to 1024. OUTPUT DELAY is the time delay after the rising edge of the clock before the data update is presented at the output pins. OVER RANGE RECOVERY TIME is the time required after VIN goes from a specified voltage out of the normal input range to a specified voltage within the normal input range and the converter makes a conversion with its rated accuracy. PIPELINE DELAY (LATENCY) See CONVERSION LATENCY. POSITIVE FULL SCALE ERROR is the difference between the actual last code transition and its ideal value of 1½ LSB below positive full scale. POWER SUPPLY REJECTION RATIO (PSRR) is a measure of how well the ADC rejects a change in the power supply voltage. For the ADC11DL066, PSRR1 is the ratio of the change in Full-Scale Error that results from a change in the d.c. power supply voltage, expressed in dB. PSRR2 is a measure of how well an a.c. signal riding upon the power supply is rejected at the output. SIGNAL TO NOISE RATIO (SNR) is the ratio, expressed in dB, of the rms value of the input signal to the rms value of the sum of all other spectral components below one-half the sampling frequency, not including harmonics or d.c. SIGNAL TO NOISE PLUS DISTORTION (S/N+D or SINAD) Is the ratio, expressed in dB, of the rms value of the input signal to the rms value of all of the other spectral components below half the clock frequency, including harmonics but excluding d.c. SPURIOUS FREE DYNAMIC RANGE (SFDR) is the difference, expressed in dB, between the rms values of the input signal and the peak spurious signal, where a spurious signal is any signal present in the output spectrum that is not present at the input and may or may not be a harmonic. TOTAL HARMONIC DISTORTION (THD) is the ratio, expressed in dB, of the rms total of the first nine harmonic levels at the output to the level of the fundamental at the output. THD is calculated as where F1 is the RMS power of the fundamental (output) frequency and f2 through f10 are the RMS power of the first 9 harmonic frequencies in the output spectrum. – Second Harmonic Distortion (2nd Harm) is the difference expressed in dB, between the RMS power in the input frequency at the output and the power in its 2nd harmonic level at the output. – Third Harmonic Distortion (3rd Harm) is the difference, expressed in dB, between the RMS power in the input frequency at the output and the power in its 3rd harmonic level at the output. 9 www.national.com ADC11DL066 Timing Diagram 20077309 Output Timing Transfer Characteristic 20077310 FIGURE 1. Transfer Characteristic www.national.com 10 ADC11DL066 Typical Performance Characteristics otherwise stated DNL VA = VD = +3.3V, VDR = +2.5V, fCLK = 66 MHz, fIN = 10 MHz unless INL 20077318 20077360 DNL vs. VDR INL vs. VDR 20077321 20077326 DNL vs. fCLK INL vs. fCLK 20077319 20077324 11 www.national.com ADC11DL066 DNL vs. Clock Duty Cycle INL vs. Clock Duty Cycle 20077320 20077325 DNL vs. Temperature INL vs. Temperature 20077322 20077327 SNR, SINAD, SFDR vs. VDR SNR, SINAD, SFDR vs. fCLK 20077333 20077328 www.national.com 12 ADC11DL066 SNR, SINAD, SFDR vs. CLOCK DUTY CYCLE SNR, SINAD, SFDR vs. VCM 20077329 20077332 SNR, SINAD, SFDR vs. VREF SNR, SINAD, SFDR vs. Temperature 20077331 20077334 Distortion vs. VDR Distortion vs. FCLK 20077340 20077336 13 www.national.com ADC11DL066 Distortion vs. Clock Duty Cycle Distortion vs. VCM 20077337 20077339 Distortion vs. VREF Distortion vs. Temperature 20077338 20077341 tOD vs. VDR SPECTRAL PLOT, FIN = 1 MHz 20077343 20077361 www.national.com 14 ADC11DL066 SPECTRAL PLOT, FIN = 10 MHz SPECTRAL PLOT, FIN = 33 MHz 20077362 20077363 15 www.national.com ADC11DL066 Functional Description Operating on a single +3.3V supply, the ADC11DL066 uses a pipeline architecture and has error correction circuitry to help ensure maximum performance. The differential analog input signal is digitized to 11 bits. The user has the choice of using an internal 1.0 Volt stable reference or using an external reference. Any external reference is buffered on-chip to ease the task of driving that pin. The output word rate is the same as the clock frequency, which can be between 15 Msps (typical) and 66 Msps with fully specified performance at 66 Msps. The analog input voltage for both channels is acquired at the rising edge of the clock and the digital data for a given sample is delayed by the pipeline for 6 clock cycles. A choice of Offset Binary or Two's Complement output format is selected with the OF pin. A logic high on the power down (PD) pin reduces the converter power consumption to 75 mW. Applications Information 1.0 OPERATING CONDITIONS We recommend that the following conditions be observed for operation of the ADC11DL066: 3.0V ≤ VA ≤ 3.6V VD = VA 2.4V ≤ VDR ≤ VD 15 MHz ≤ fCLK ≤ 66 MHz 0.8V ≤ VREF ≤ 1.5V VREF/2 ≤ VCM ≤ 1.2V 1.1 Analog Inputs The ADC11DL066 has two analog signal input pairs, VIN A+ and VIN A- for one converter and VIN B+ and VIN B- for the other converter. Each pair of pins forms a differential input pair. There is one reference input pin, VREF, for use of an optional external reference. The analog input circuitry contains an input boost circuit that provides improved linearity over a wide range of analog input voltages. To prevent an on-chip over voltage condition that could impair device reliability, the input signal should never exceed the voltage described as Peak VIN ≤ VA − 1.0V. 1.2 Reference Pins The ADC11DL066 is designed to operate with a 1.0V reference, but performs well with reference voltages in the range of 0.8V to 1.5V. Lower reference voltages will decrease the signal-to-noise ratio (SNR) of the ADC11DL066. Increasing the reference voltage (and the input signal swing) beyond 1.5V may degrade THD and SFDR for a full-scale input, especially at higher input frequencies. It is important that all grounds associated with the reference voltage and the analog input signal make connection to the ground plane at a single, quiet point to minimize the effects of noise currents in the ground path. The ADC11DL066 will perform well with reference voltages up to 1.5V for full-scale input frequencies up to 10 MHz. However, more headroom is needed as the input frequency increases, so the maximum reference voltage (and input swing) will decrease for higher full-scale input frequencies. The six Reference Bypass Pins (VRPA, VRMA, VRNA, VRPB, VRMB and VRNB) are made available for bypass purposes. The VRMA and VRMB pins should each be bypassed to ground www.national.com 16 with a 0.1 µF capacitor. A series 1.5Ω resistor (5%) and 1.0 µF capacitor (±20%) should be placed between the VRPA and VRNA pins and between the VRPB and VRNB pins, as shown in Figure 4. This configuration is necessary to avoid reference oscillation, which could result in reduced SFDR and/or SNR. Smaller capacitor values than those specified will allow faster recovery from the power down mode, but may result in degraded noise performance. DO NOT LOAD these pins. Loading any of these pins may result in performance degradation. ADC11DL066 does not have a reference output pin. The nominal voltages for the reference bypass pins are as follows: VRMA = VRMB = VA / 2 VRPA = VRPB = VRM + VREF / 2 VRNA = VRNB = VRM − VREF / 2 The VRM pins may be used as common mode voltage (VCM) sources for the analog input pins as long as no d.c. current is drawn from them. However, because the voltages at the VRM pins are half that of the VA supply pin, using these pins for common mode voltage sources will result in reduced input headroom (the difference between the VA supply voltage and the peak signal voltage at either analog input) and the possibility of reduced THD and SFDR performance. For this reason, it is recommended that VA always exceed VREF by at least 2 Volts when using the VRM pins as VCM sources. For high input frequencies it may be necessary to increase this headroom to maintain THD and SFDR performance. User choice of an on-chip or external reference voltage is provided. The internal 1.0 Volt reference is in use when the the INT/EXT REF pin is at a logic low, regardless of any voltage applied to the VREF pin. When the INT/EXT REF pin is at a logic high, the voltage at the VREF pin is used for the voltage reference. Optimum ADC dynamic performance is obtained when the reference voltage is in the range of 0.8V to 1.5V. When an external reference is used, the VREF pin should be bypassed to ground with a 0.1 µF capacitor close to the reference input pin. There is no need to bypass the VREF pin when the internal reference is used. There is no direct access to the internal reference voltage. However the nominal value of the reference voltage, whether the internal or an external reference is used, is approximately equal to VRP − VRN. 1.3 Signal Inputs The signal inputs are VIN A+ and VINA− for one ADC and VINB+ and VINB− for the other ADC. The input signal, VIN, is defined as VIN A = (VINA+) – (VINA−) for the "A" converter and VIN B = (VINB+) – (VINB−) for the "B" converter. Figure 2 shows the expected input signal range. Note that the common mode input voltage, VCM, should be in the range of 0.5V to 1.5V with a nominal value of 1.0V. The ADC11DL066 performs best with a differential input signal with each input centered around a common mode voltage, VCM. The peak-to-peak voltage swing at each analog input pin should not exceed the value of the reference voltage or the output data will be clipped. The two input signals should be exactly 180° out of phase from each other and of the same amplitude. For single frequency inputs, angular errors result in a reduction of the effective full scale input. For complex waveforms, however, angular errors will result in distortion. ADC11DL066 TABLE 1. Input to Output Relationship – Differential Input VIN+ VCM − VREF / 2 VCM − VREF / 4 VCM VIN− VCM + VREF / 2 VCM + VREF / 4 VCM Binary Output 000 0000 0000 010 0000 0000 100 0000 0000 110 0000 0000 111 1111 1111 2’s Complement Output 100 0000 0000 110 0000 0000 000 0000 0000 010 0000 0000 011 1111 1111 VCM + VCM − VREF / 4 VREF / 4 20077311 FIGURE 2. Expected Input Signal Range For single frequency sine waves with angular errors of less than 45° (π/4) between the two inputs, the full scale error in LSB can be described as approximately EFS = 2(n-1) * ( 1 - cos (dev) ) = 2048 * ( 1 - cos (dev) ) Where dev is the angular difference in degrees between the two signals having a 180° relative phase relationship to each other (see Figure 3). Drive the analog inputs with a source impedance less than 100Ω. VCM + VCM − VREF / 2 VREF / 2 TABLE 2. Input to Output Relationship – Single-Ended Input VIN+ VCM − VREF VCM − VREF / 2 VCM VCM + VREF / 2 VCM + VREF VIN− VCM VCM VCM VCM VCM Binary Output 000 0000 0000 010 0000 0000 100 0000 0000 110 0000 0000 111 1111 1111 2’s Complement Output 100 0000 0000 110 0000 0000 000 0000 0000 010 0000 0000 011 1111 1111 20077312 FIGURE 3. Angular Errors Between the Two Input Signals Will Reduce the Output Level or Cause Distortion 1.3.1 Single-Ended Operation Single-ended performance is inferior to performance obtained when differential input signals are used. For this reason, single-ended operation is not recommended. However, if single ended-operation is required and the resulting performance degradation is acceptable, one of the analog inputs should be connected to the d.c. mid point voltage of the driven input. The peak-to-peak differential input signal at the driven input pin should be twice the reference voltage to maximize SNR and SINAD performance (Figure 2b). For example, set VREF to 0.5V, bias VIN− to 1.0V and drive VIN+ with a signal range of 0.5V to 1.5V. Because very large input signal swings can degrade distortion performance, better performance with a single-ended input can be obtained by reducing the reference voltage when maintaining a full-range output. Table 1 and Table 2 indicate the input to output relationship of the ADC11DL066. Note again that single-ended operation of the ADC11DL066 is not recommended because of the degraded performance that results. A single-ended to differential conversion circuit is shown in Figure 5 1.3.2 Driving the Analog Inputs The VIN+ and the VIN− inputs of the ADC11DL066 consist of an analog switch followed by a switched-capacitor amplifier. The capacitance seen at the analog input pins changes with the clock level, appearing as 8 pF when the clock is low, and 7 pF when the clock is high. As the internal sampling switch opens and closes, current pulses occur at the analog input pins, resulting in voltage spikes at these pins. As a driving amplifier attempts to counteract these voltage spikes, a damped oscillation may appear at the ADC analog inputs. Do not attempt to filter out these pulses. Rather, use amplifiers to drive the ADC11DL066 input pins that are able to react to these pluses and settle before the switch opens and another sample is taken. The LMH6550, LMH6702, LMH6628, LMH6622 and the LMH6655 are good amplifiers for driving the ADC11DL066. To help isolate the pulses at the ADC input from the amplifier output, use RCs at the inputs, as can be seen in Figure 4 and Figure 5. These components should be placed close to the ADC inputs because the input pins of the ADC is the most sensitive part of the system and this is the last opportunity to filter that input. For Nyquist applications the RC pole should be at the ADC sample rate. The ADC input capacitance in the sample mode should be considered when setting the RC pole. Setting the pole in this manner will provide best SNR performance. To obtain best SINAD and ENOB performance, reduce the RC time constant until SNR and THD are numerically equal to each other. To obtain best distortion and SFDR performance, eliminate the RC altogether 17 www.national.com ADC11DL066 20077313 FIGURE 4. Application Circuit using Transformer or Differential Op-Amp Drive Circuit 20077315 FIGURE 5. Differential Drive Circuit using a fully differential amplifier. For undersampling applications, the RC pole should be set at about 1.5 to 2 times the maximum input frequency to maintain a linear delay response. Note that the ADC11DL066 is not designed to operate with single-ended inputs. However, doing so is possible if the degraded performance is acceptable. See Section 1.3.1. Figure 4 shows a narrow band application with a transformer used to convert single-ended input signals to differential. Figure 5 shows the use of a fully differential amplifier for singleended to differential conversion. The LMH6550 is recommended for single-ended to differential conversion when d.c. or very low frequencies must be accommodated. Of course, the LMH6550 may also be used to amplify differential signals. 1.3.3 Input Common Mode Voltage The input common mode voltage, VCM, should be of a value such that the peak excursions of the analog signal does not go more negative than ground or more positive than 1.0 Volt below the VA supply voltage. The nominal VCM should gener18 www.national.com ADC11DL066 ally be about VREF/2, but VRBA and VRBB can be used as a VCM source as long as no d.c. current is drawn from either of these pins. 2.0 DIGITAL INPUTS Digital TTL/CMOS compatible inputs consist of CLK, OEA, OEB, OF, INT/EXT REF and PD. 2.1 The CLK Pin The CLK signal controls the timing of the sampling process. Drive the clock input with a stable, low jitter clock signal in the range of 15 MHz to 75 MHz with rise and fall times of 2 ns or less. The trace carrying the clock signal should be as short as possible and should not cross any other signal line, analog or digital, not even at 90°. If the CLK is interrupted, or its frequency too low, the charge on internal capacitors can dissipate to the point where the accuracy of the output data will degrade. This is what limits the lowest sample. The ADC clock line should be considered to be a transmission line and be series terminated at the source end to match the source impedance with the characteristic impedance of the clock line. It generally is not necessary to terminate the far (ADC) end of the clock line, but if a single clock source is driving more than one device (a condition that is generally not recommended), far end termination may be needed. The far end termination should be near but beyond the ADC clock pin as seen from the clock source. It is highly desirable that the the source driving the ADC CLK pin only drive that pin. However, if that source is used to drive other things, each driven pin should be a.c. terminated with a series RC to ground, as shown in Figure 4, such that the resistor value is equal to the characteristic impedance of the clock line and the capacitor value is outputs of the ADC11DL066 to drive a bus. Rather, each output pin should be located close to and drive a single digital input pin. To further reduce ADC noise, a 100 Ω resistor in series with each ADC digital output pin, located close to their respective pins, should be added to the circuit. 2.3 The PD Pin The PD pin, when high, holds the ADC11DL066 in a powerdown mode to conserve power when the converter is not being used. The power consumption in this state is 75 mW with a 66MHz clock and 40mW if the clock is stopped when PD is high. The output data pins are undefined and the data in the pipeline is corrupted while in the power down mode. The Power Down Mode Exit Cycle time is determined by the value of the components on pins 4, 5, 6, 12, 13 and 14 and is about 500 µs with the recommended components on the VRP, VRM and VRN reference bypass pins. These capacitors loose their charge in the Power Down mode and must be recharged by on-chip circuitry before conversions can be accurate. Smaller capacitor values allow slightly faster recovery from the power down mode, but can result in a reduction in SNR, SINAD and ENOB performance. 2.4 The OF Pin The output data format is offset binary when the OF pin is at a logic low or 2’s complement when the OF pin is at a logic high. While the sense of this pin may be changed "on the fly," doing this is not recommended as the output data could be erroneous for a few clock cycles after this change is made. 2.5 The INT/EXT REF Pin The INT/EXT REF pin determines whether the internal reference or an external reference voltage is used. With this pin at a logic low, the internal 1.0V reference is in use. With this pin at a logic high an external reference must be applied to the VREF pin, which should then be bypassed to ground. There is no need to bypass the VREF pin when the internal reference is used. There is no access to the internal reference voltage, but its value is approximately equal to VRP − VRN. 3.0 OUTPUTS The ADC11DL066 has 22 TTL/CMOS compatible Data Output pins. Valid data is present at these outputs while the OE and PD pins are low. While the tOD time provides information about output timing, tOD will change with a change of clock frequency. At the rated 66 MHz clock rate, the data transition can be coincident with the rise of the clock and about 7 ns before the fall of the clock (depending upon VDR), so the falling edge of the clock should be used to capture the output data. At lower clock frequencies the data transition occurs a little after the rising edge of the clock, but the fall of the clock still appears to be the best edge for data capture. However, circuit board layout will affect relative delays of the clock and data, so it is important to consider these relative delays when designing the digital interface. Be very careful when driving a high capacitance bus. The more capacitance the output drivers must charge for each conversion, the more instantaneous digital current flows through VDR and DR GND. These large charging current spikes can cause on-chip ground noise and couple into the analog circuitry, degrading dynamic performance. Adequate bypassing, limiting output capacitance and careful attention to the ground plane will reduce this problem. Additionally, bus capacitance beyond the specified 15 pF/pin will cause tOD to increase, making it difficult to properly latch the ADC output data. The result could be an apparent reduction in dynamic performance. 19 www.national.com where tPD is the signal propagation time in ns/unit length, "L" is the line length and ZO is the characteristic impedance of the clock line. This termination should be as close as possible to the ADC clock pin but beyond it as seen from the clock source. Typical tPD is about 150 ps/inch (60 ps/cm) on FR-4 board material. The units of "L" and tPD should be the same (inches or centimeters). The duty cycle of the clock signal can affect the performance of the A/D Converter. Because achieving a precise duty cycle is difficult, the ADC11DL066 is designed to maintain performance over a range of duty cycles. While it is specified and performance is guaranteed with a 50% clock duty cycle, performance is typically maintained over a clock duty cycle range of 43% to 57% at 66 MSPS. Take care to maintain a constant clock line impedance throughout the length of the line. Refer to Application Note AN-905 for information on setting characteristic impedance. 2.2 The OEA, OEB Pins The OEA and OEB pins, when high, put the output pins of their respective converters into a high impedance state. When either of these pin is low, the corresponding outputs are in the active state. The ADC11DL066 will continue to convert whether these pins are high or low, but the output can not be read while the pin is high. Since ADC noise increases with increased output capacitance at the digital output pins, do not use the TRI-STATE ADC11DL066 To minimize noise due to output switching, minimize the load currents at the digital outputs. This can be done by connecting buffers (74AC541, for example) between the ADC outputs and any other circuitry. Only one driven input should be connected to each output pin. Additionally, inserting series resistors of about 100Ω at the digital outputs, close to the ADC pins, will isolate the outputs from trace and other circuit capacitances and limit the output currents, which could otherwise result in performance degradation. See Figure 4. Note that, although the ADC11DL066 has Tri-State outputs, these outputs should not be used to drive a bus and the charging and discharging of large capacitances can degrade SNR performance. Each output pin should drive only one pin of a receiving device and the interconnecting lines should be as short as practical. 4.0 POWER SUPPLY CONSIDERATIONS The power supply pins should be bypassed with a 10 µF capacitor and with a 0.1 µF ceramic chip capacitor within a centimeter of each power pin. Leadless chip capacitors are preferred because they have low series inductance. As is the case with all high-speed converters, the ADC11DL066 is sensitive to power supply noise. Accordingly, the noise on the analog supply pin should be kept below 100 mVP-P. No pin should ever have a voltage on it that is in excess of the supply voltages, not even on a transient basis. Be especially careful of this during power turn on and turn off. The VDR pin provides power for the output drivers and may be operated from a supply in the range of 2.4V to VD (nominal 5V). This can simplify interfacing to lower voltage devices and systems. Note, however, that tOD increases with reduced VDR. DO NOT operate the VDR pin at a voltage higher than VD . 5.0 LAYOUT AND GROUNDING Proper grounding and proper routing of all signals are essential to ensure accurate conversion. Maintaining separate analog and digital areas of the board, with the ADC11DL066 between these areas, is required to achieve specified performance. The ground return for the data outputs (DR GND) carries the ground current for the output drivers. The output current can exhibit high transients that could add noise to the conversion process. To prevent this from happening, the DR GND pins should NOT be connected to system ground in close proximity to any of the ADC11DL066's other ground pins. Capacitive coupling between the typically noisy digital circuitry and the sensitive analog circuitry can lead to poor performance. The solution is to keep the analog circuitry separated from the digital circuitry, and to keep the clock line as short as possible. 20077316 FIGURE 6. Example of a Suitable Layout www.national.com 20 ADC11DL066 The effects of the noise generated from the ADC output switching can be minimized through the use of 100Ω resistors in series with each data output line. Locate these resistors as close to the ADC output pins as possible. Since digital switching transients are composed largely of high frequency components, total ground plane copper weight will have little effect upon the logic-generated noise. This is because of the skin effect. Total surface area is more important than is total ground plane volume. Generally, analog and digital lines should cross each other at 90° to avoid crosstalk. To maximize accuracy in high speed, high resolution systems, however, avoid crossing analog and digital lines altogether. It is important to keep clock lines as short as possible and isolated from ALL other lines, including other digital lines. Even the generally accepted 90° crossing should be avoided with the clock line as even a little coupling can cause problems at high frequencies. This is because other lines can introduce jitter into the clock line, which can lead to degradation of SNR. Also, the high speed clock can introduce noise into the analog chain. Best performance at high frequencies or high resolution is obtained with a straight signal path. That is, the signal path through all components should be a straight line wherever possible. Be especially careful with the layout of inductors. Mutual inductance can change the characteristics of the circuit in which they are used. Inductors should not be placed side by side, even with just a small part of their bodies beside each other. The analog input should be isolated from noisy signal traces to avoid coupling of spurious signals into the input. Any external component (e.g., a filter capacitor) connected between the converter's input pins and ground or to the reference input pin and ground should be connected to a very clean point in the ground plane. Figure 6 gives an example of a suitable layout. All analog circuitry (input amplifiers, filters, reference components, etc.) should be placed in the analog area of the board. All digital circuitry and I/O lines should be placed in the digital area of the board. The ADC11DL066 should be between these two areas. Furthermore, all components in the reference circuitry and the input signal chain that are connected to ground should be connected together with short traces and enter the ground plane at a single, quiet point. All ground connections should have a low inductance path to ground. 6.0 DYNAMIC PERFORMANCE To achieve the best dynamic performance, the clock source driving the CLK input must be free of jitter. Isolate the ADC clock from any digital circuitry with buffers, as with the clock tree shown in Figure 7. The gates used in a clock tree must be capable of operating at frequencies much higher than those used if added jitter is to be prevented. Best performance will be obtained with a differential input drive, compared with a single-ended drive, as discussed in Sections 1.3.1 and 1.3.2. As mentioned in Section 5.0, it is good practice to keep the ADC clock line as short as possible and to keep it well away from any other signals. Other signals can introduce jitter into the clock signal, which can lead to reduced SNR performance, and the clock can introduce noise into other lines. Even lines with 90° crossings have capacitive coupling, so try to avoid even these 90° crossings of the clock line. 7.0 COMMON APPLICATION PITFALLS Driving the inputs (analog or digital) beyond the power supply rails. For proper operation, all inputs should not go more than 100 mV beyond the supply rails (more than 100 mV below the ground pins or 100 mV above the supply pins). Exceeding these limits on even a transient basis may cause faulty or erratic operation. It is not uncommon for high speed digital components (e.g., 74F devices) to exhibit overshoot or undershoot that goes above the power supply or below ground. A resistor of about 47Ω to 100Ω in series with any offending digital input, close to the signal source, will eliminate the problem. Do not allow input voltages to exceed the supply voltage, even on a transient basis. Not even during power up or power down. Be careful not to overdrive the inputs of the ADC11DL066 with a device that is powered from supplies outside the range of the ADC11DL066 supply. Such practice may lead to conversion inaccuracies and even to device damage. Attempting to drive a high capacitance digital data bus. The more capacitance the output drivers must charge for each conversion, the more instantaneous digital current flows through VDR and DR GND. These large charging current spikes can couple into the analog circuitry, degrading dynamic performance. Adequate bypassing and maintaining separate analog and digital areas on the pc board will reduce this problem. Additionally, bus capacitance beyond the specified 15 pF/pin will cause t OD to increase, making it difficult to properly latch the ADC output data. The result could, again, be an apparent reduction in dynamic performance. The digital data outputs should be buffered (with 74AC541, for example). Dynamic performance can also be improved by adding series resistors at each digital output, close to the ADC11DL066, which reduces the energy coupled back into the converter output pins by limiting the output current. A reasonable value for these resistors is 100Ω. Using an inadequate amplifier to drive the analog input. As explained in Section 1.3, the capacitance seen at the input alternates between 8 pF and 7 pF, depending upon the phase of the clock. This dynamic load is more difficult to drive than is a fixed capacitance. If the amplifier exhibits overshoot, ringing, or any evidence of instability, even at a very low level, it will degrade performance. A small series resistor at each amplifier output and a capacitor at the analog inputs (as shown in Figure 4 and Figure 5) will improve performance. The LMH6702 and the LMH6628 have been successfully used to drive the analog inputs of the ADC11DL066. Also, it is important that the signals at the two inputs have exactly the same amplitude and be exactly 180º out of phase with each other. Board layout, especially equality of the length of the two traces to the input pins, will affect the effective phase between these two signals. Remember that an opera- 20077317 FIGURE 7. Clock Tree for Clock Isolation 21 www.national.com ADC11DL066 tional amplifier operated in the non-inverting configuration will exhibit more time delay than will the same device operating in the inverting configuration. Operating with the reference pins outside of the specified range. As mentioned in Section 1.2, VREF should be in the range of 0.8V ≤ VREF ≤ 1.5V Operating outside of these limits could lead to performance degradation. Inadequate network on Reference Bypass pins (VRPA, VRNA, VRMA, VRPB, VRNB and VRMB). As mentioned in Sec- tion 1.2, these pins should be bypassed with 0.1 µF capacitors to ground at VRMA and VRMB and with a series RC of 1.5 Ω and 1.0 µF between pins VRPA and VRNA and between VRPB and VRNB for best performance. Using a clock source with excessive jitter, using excessively long clock signal trace, or having other signals coupled to the clock signal trace. This will cause the sampling interval to vary, causing excessive output noise and a reduction in SNR and SINAD performance. www.national.com 22 ADC11DL066 Physical Dimensions inches (millimeters) unless otherwise noted 64-Lead TQFP Package Ordering Number ADC11DL066CIVS NS Package Number VEC64A 23 www.national.com ADC11DL066 Dual 11-Bit, 66 MSPS, 450 MHz Input Bandwidth A/D Converter w/Internal Reference Notes For more National Semiconductor product information and proven design tools, visit the following Web sites at: Products Amplifiers Audio Clock Conditioners Data Converters Displays Ethernet Interface LVDS Power Management Switching Regulators LDOs LED Lighting PowerWise Serial Digital Interface (SDI) Temperature Sensors Wireless (PLL/VCO) www.national.com/amplifiers www.national.com/audio www.national.com/timing www.national.com/adc www.national.com/displays www.national.com/ethernet www.national.com/interface www.national.com/lvds www.national.com/power www.national.com/switchers www.national.com/ldo www.national.com/led www.national.com/powerwise www.national.com/sdi www.national.com/tempsensors www.national.com/wireless WEBENCH Analog University App Notes Distributors Green Compliance Packaging Design Support www.national.com/webench www.national.com/AU www.national.com/appnotes www.national.com/contacts www.national.com/quality/green www.national.com/packaging www.national.com/quality www.national.com/refdesigns www.national.com/feedback Quality and Reliability Reference Designs Feedback THE CONTENTS OF THIS DOCUMENT ARE PROVIDED IN CONNECTION WITH NATIONAL SEMICONDUCTOR CORPORATION (“NATIONAL”) PRODUCTS. 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