EL5462IS-T13

DATASHEET EL5462 FN7492 Rev 0.00 February 14, 2005 500MHz Low Power Current Feedback Amplifier The EL5462 is a current feedback amplifier with a bandwidth of 500MHz which makes this amplifier ideal for today’s high speed video and monitor applications. With a supply current of just 1.5mA per amplifier and the ability to run from a single supply voltage from 5V to 12V, the EL5462 is also ideal for handheld, portable or batterypowered equipment. The EL5462 is available in a 14-pin SO package and operates over the industrial temperature range of -40°C to +85°C. Pinout INA- 2 D + - 11 VS- VS+ 4 10 INC+ INB+ 5 INB- 6 OUTB 7 13 IND12 IND+ INA+ 3 - + B + C • 4000V/µs slew rate • 1.5mA supply current per amplifier • Single and dual supply operation, from 5V to 12V supply span • High speed, 1.4GHz product available (EL5167 & EL5167) • High speed, 4mA, 630MHz product available (EL5164 & EL5165) Applications 14 OUTD A - + • 500MHz -3dB bandwidth • Pb-free available (RoHS compliant) EL5462 (14-PIN SO) TOP VIEW OUTA 1 Features • Battery-powered equipment • Handheld, portable devices • Video amplifiers • Cable drivers • RGB amplifiers • Test equipment 9 INC- • Instrumentation 8 OUTC • Current-to-voltage converters Ordering Information PART NUMBER PACKAGE TAPE & REEL PKG. DWG. # EL5462IS 14-Pin SO - MDP0027 EL5462IS-T7 14-Pin SO 7” MDP0027 EL5462IS-T13 14-Pin SO 13” MDP0027 EL5462ISZ (See Note) 14-Pin SO (Pb-Free) - MDP0027 EL5462ISZ-T7 (See Note) 14-Pin SO (Pb-Free) 7” MDP0027 EL5462ISZ-T13 (See Note) 14-Pin SO (Pb-Free) 13” MDP0027 NOTE: Intersil Pb-free products employ special Pb-free material sets; molding compounds/die attach materials and 100% matte tin plate termination finish, which are RoHS compliant and compatible with both SnPb and Pb-free soldering operations. Intersil Pb-free products are MSL classified at Pb-free peak reflow temperatures that meet or exceed the Pb-free requirements of IPC/JEDEC J STD-020. FN7492 Rev 0.00 February 14, 2005 Page 1 of 9 EL5462 Absolute Maximum Ratings (TA = 25°C) Supply Voltage between VS+ and VS- . . . . . . . . . . . . . . . . . . . Maximum Continuous Output Current . . . . . . . . . . . . . . . . . . . Maximum Voltage between IN+ and IN-, Disabled . . . . . . . . . Current into IN+, IN-, CE . . . . . . . . . . . . . . . . . . . . . . . . . . . . . Slew Rate from VS+ to VS- . . . . . . . . . . . . . . . . . . . . . . . . . . . 13.2V 50mA ±1.5V ±5mA 1V/µs Pin Voltages. . . . . . . . . . . . . . . . . . . . . . . . .VS- - 0.5V to VS+ +0.5V Power Dissipation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . See Curves Operating Junction Temperature . . . . . . . . . . . . . . . . . . . . . . +125°C Storage Temperature . . . . . . . . . . . . . . . . . . . . . . . .-65°C to +150°C Ambient Operating Temperature . . . . . . . . . . . . . . . .-40°C to +85°C CAUTION: Stresses above those listed in “Absolute Maximum Ratings” may cause permanent damage to the device. This is a stress only rating and operation of the device at these or any other conditions above those indicated in the operational sections of this specification is not implied. IMPORTANT NOTE: All parameters having Min/Max specifications are guaranteed. Typical values are for information purposes only. Unless otherwise noted, all tests are at the specified temperature and are pulsed tests, therefore: TJ = TC = TA Electrical Specifications PARAMETER VS+ = +5V, VS- = -5V, RF = 750 for AV = 1, RF = 400 for AV = 2, RL = 150, TA = 25°C unless otherwise specified. DESCRIPTION CONDITIONS MIN TYP MAX UNIT AC PERFORMANCE BW -3dB Bandwidth AV = +1, RL = 500RF = 598 500 MHz AV = +2, RL = 150RF = 422 233 MHz 30 MHz BW1 0.1dB Bandwidth SR Slew Rate VO = -2.5V to +2.5V, AV = +2, RL = 100 tS 0.1% Settling Time VOUT = -2.5V to +2.5V, AV = +1 eN 2500 4000 5000 V/µs 25 ns Input Voltage Noise 3 nV/Hz iN- IN- Input Current Noise 10 pA/Hz iN+ IN+ Input Current Noise 6.5 pA/Hz dG Differential Gain Error (Note 1) AV = +2 0.05 % dP Differential Phase Error (Note 1) AV = +2 0.15 ° DC PERFORMANCE VOS Offset Voltage TCVOS Input Offset Voltage Temperature Coefficient ROL Transimpedance -5 Measured from TMIN to TMAX 1.5 +5 mV 6 µV/°C 500 1000 k V INPUT CHARACTERISTICS CMIR Common Mode Input Range Guaranteed by CMRR test ±3 ±3.3 CMRR Common Mode Rejection Ratio VIN = ±3V 50 62 75 dB -ICMR - Input Current Common Mode Rejection -1 0.22 +1 µA/V +IIN + Input Current -8 0.5 +8 µA -IIN - Input Current -10 2 +10 µA RIN Input Resistance 0.8 1.6 3 M CIN Input Capacitance 1 pF OUTPUT CHARACTERISTICS VO IOUT Output Voltage Swing Output Current FN7492 Rev 0.00 February 14, 2005 RL = 150 to GND ±3.35 ±3.6 ±3.75 V RL = 1k to GND ±3.75 ±3.9 ±4.15 V RL = 10 to GND 60 100 mA Page 2 of 9 EL5462 Electrical Specifications PARAMETER VS+ = +5V, VS- = -5V, RF = 750 for AV = 1, RF = 400 for AV = 2, RL = 150, TA = 25°C unless otherwise specified. (Continued) DESCRIPTION CONDITIONS MIN TYP MAX UNIT 1.7 mA SUPPLY ISON Supply Current - Enabled, per Amplifier No load, VIN = 0V 1.3 1.5 PSRR Power Supply Rejection Ratio DC, VS = ±4.75V to ±5.25V 65 76 -IPSR - Input Current Power Supply Rejection DC, VS = ±4.75V to ±5.25V -0.5 0.1 dB +0.5 µA/V NOTE: 1. Standard NTSC test, AC signal amplitude = 286mVP-P, f = 3.58MHz Typical Performance Curves 4 AV=+1 VCC=+5V 2 VEE=-5V RL=500 RF=598 NORMALIZED GAIN (dB) NORMALIZED GAIN (dB) 4 0 -2 -4 -6 10K 100K 1M 10M 100M AV=+4.6 VCC=+5V 2 VEE=-5V RF=375 0 -2 -4 -6 100K 1G 1M FREQUENCY (Hz) 0 1 NORMALIZED GAIN (dB) NORMALIZED GAIN (dB) 3 -2 -4 100M 1G FREQUENCY (Hz) FIGURE 3. FREQUENCY RESPONSE FOR AV=+10 FN7492 Rev 0.00 February 14, 2005 1G FIGURE 2. FREQUENCY RESPONSE FOR AV=+4.6 2 10M 100M FREQUENCY (Hz) FIGURE 1. FREQUENCY RESPONSE FOR AV=+1 AV=+10 VCC=+5V -6 VEE=-5V RL=150 RF=375 -8 100K 1M 10M -1 -3 AV=+2 VCC=+5V -5 VEE=-5V RL=150 RF=422 -7 100K 1M 10M 100M 1G FREQUENCY (Hz) FIGURE 4. FREQUENCY RESPONSE FOR AV=+2 Page 3 of 9 EL5462 Typical Performance Curves (Continued) 5 1 NORMALIZED GAIN (dB) NORMALIZED GAIN (dB) 3 -1 -3 AV=+4 VCC=+5V -5 VEE=-5V RL=150 RF=422 -7 100K 1M 10M 100M 1G AV=+1 RL=150 3 RF=698 VCC,VEE=±6V 1 VCC,VEE=±4V -3 -5 100K FREQUENCY (Hz) OUTPUT IMPEDANCE () 10 VCC,VEE=±3V VCC,VEE=±2.5V 1M 10M 100M 1G FREQUENCY (Hz) FIGURE 5. FREQUENCY RESPONSE FOR AV=+4 100 VCC,VEE=±5V -1 FIGURE 6. FREQUENCY RESPONSE FOR VARIOUS VCC, VEE AV=+2 VCC=+5V VEE=-5V INPUT RISE TIME 1.028ns 1V/DIV 1 OUTPUT RISE TIME 2.218ns 0.1 0.01 10K 100K 1M 10M 100M 2V/DIV AV=+2 VCC=+5V VEE=-5V RL=150 4ns/DIV FREQUENCY (Hz) FIGURE 7. CLOSED LOOP OUTPUT IMPEDANCE INPUT FALL TIME 1.036ns AV=+2 VCC=+5V VEE=-5V RL=150 1V/DIV OUTPUT FALL TIME 2.21ns CH1=5V CH2=200mV M=100ns CH1 2V/DIV 4ns/DIV FIGURE 9. OUTPUT FALL TIME FN7492 Rev 0.00 February 14, 2005 FIGURE 8. OUTPUT RISE TIME CH2 100ns/DIV FIGURE 10. TURN ON TIME Page 4 of 9 EL5462 Typical Performance Curves (Continued) 0 AV=+2 VCC=+5V -20 VEE=-5V RL=150 CH1=5V CH2=200mV M=100ns PSRR (dB) CH1 CH2 -40 -60 -80 -100 10 100ns/DIV 1K 100 10K 100K 10M 1M 100M FREQUENCY (Hz) FIGURE 11. TURN OFF TIME FIGURE 12. PSRR (VCC) 0 1.4 POWER DISSIPATION (W) PSRR (dB) AV=+2 VCC=+5V -20 VEE=-5V RL=150 -40 -60 -80 -100 10 1K 100 10K 100K 10M 1M 100M 1.2 1.136W 1  JA 0.8 0.6 SO =8 14 8° C /W 0.4 0.2 0 0 25 50 75 85 100 125 150 AMBIENT TEMPERATURE (°C) FREQUENCY (Hz) FIGURE 13. PSRR (VEE) 1 JEDEC JESD51-7 HIGH EFFECTIVE THERMAL CONDUCTIVITY TEST BOARD FIGURE 14. PACKAGE POWER DISSIPATION vs AMBIENT TEMPERATURE JEDEC JESD51-3 LOW EFFECTIVE THERMAL CONDUCTIVITY TEST BOARD POWER DISSIPATION (W) 0.9 833mW 0.8 0.7  JA 0.6 0.5 SO =1 14 20 °C /W 0.4 0.3 0.2 0.1 0 0 25 50 75 85 100 125 150 AMBIENT TEMPERATURE (°C) FIGURE 15. PACKAGE POWER DISSIPATION vs AMBIENT TEMPERATURE FN7492 Rev 0.00 February 14, 2005 Page 5 of 9 EL5462 Pin Descriptions EL5462 PIN NAME 2, 6, 9, 13 IN- FUNCTION EQUIVALENT CIRCUIT Inverting input VS+ IN+ IN- VSCircuit 1 3, 5, 10, 12 IN+ Non-inverting input 11 VS- Negative supply 1, 7, 8, 14 OUT Output (See circuit 1) VS+ OUT VSCircuit 2 4 VS+ Positive supply Applications Information Product Description The EL5462 is a low power, current-feedback operational amplifier that offers a wide -3dB bandwidth of 500MHz and a low supply current of 1.5mA per amplifier. The EL5462 works with supply voltages ranging from a single 5V to 10V and they are also capable of swinging to within 1V of either supply on the output. Because of its current-feedback topology, the EL5462 does not have the normal gainbandwidth product associated with voltage-feedback operational amplifiers. Instead, its -3dB bandwidth to remain relatively constant as closed-loop gain is increased. This combination of high bandwidth and low power, together with aggressive pricing makes the EL5462 the ideal choice for many low-power/high-bandwidth applications such as portable, handheld, or battery-powered equipment. Power Supply Bypassing and Printed Circuit Board Layout As with any high frequency device, a good printed circuit board layout is necessary for optimum performance. Low impedance ground plane construction is essential. Surface mount components are recommended, but if leaded components are used, lead lengths should be as short as possible. The power supply pins must be well bypassed to reduce the risk of oscillation. The combination of a 4.7µF tantalum capacitor in parallel with a 0.01µF capacitor has been shown to work well when placed at each supply pin. ground plane construction is used, it should be removed from the area near the inverting input to minimize any stray capacitance at that node. Carbon or Metal-Film resistors are acceptable with the Metal-Film resistors giving slightly less peaking and bandwidth because of additional series inductance. Use of sockets, particularly for the SO package, should be avoided if possible. Sockets add parasitic inductance and capacitance which will result in additional peaking and overshoot. Capacitance at the Inverting Input Any manufacturer’s high-speed voltage or current-feedback amplifier can be affected by stray capacitance at the inverting input. For inverting gains, this parasitic capacitance has little effect because the inverting input is a virtual ground, but for non-inverting gains, this capacitance (in conjunction with the feedback and gain resistors) creates a pole in the feedback path of the amplifier. This pole, if low enough in frequency, has the same destabilizing effect as a zero in the forward open-loop response. The use of largevalue feedback and gain resistors exacerbates the problem by further lowering the pole frequency (increasing the possibility of oscillation.) The EL5462 has been optimized with a 600 feedback resistor. With the high bandwidth of these amplifiers, these resistor values might cause stability problems when combined with parasitic capacitance, thus ground plane is not recommended around the inverting input pin of the amplifier. For good AC performance, parasitic capacitance should be kept to a minimum, especially at the inverting input. (See the Capacitance at the Inverting Input section) Even when FN7492 Rev 0.00 February 14, 2005 Page 6 of 9 EL5462 Feedback Resistor Values The EL5462 has been designed and specified at a gain of +1 with RF approximately 606. This value of feedback resistor gives 500MHz of -3dB bandwidth at AV = 1 with 0.5dB of peaking. With AV = -2, an RF of approximately 600 gives 300MHz of bandwidth with 1dB of peaking. Since the EL5462 is a current-feedback amplifier, it is also possible to change the value of RF to get more bandwidth. As seen in the curve of Frequency Response for Various RF and RG, bandwidth and peaking can be easily modified by varying the value of the feedback resistor. Because the EL5462 is a current-feedback amplifier, its gainbandwidth product is not a constant for different closed-loop gains. This feature actually allows the EL5462 to maintain about the same -3dB bandwidth. As gain is increased, bandwidth decreases slightly while stability increases. Since the loop stability is improving with higher closed-loop gains, it becomes possible to reduce the value of RF below the specified TBD and still retain stability, resulting in only a slight loss of bandwidth with increased closed-loop gain. Supply Voltage Range and Single-Supply Operation The EL5462 has been designed to operate with supply voltages having a span of greater than 5V and less than 10V. In practical terms, this means that they will operate on dual supplies ranging from ±2.5V to ±5V. With single-supply, the EL5462 will operate from 5V to 10V. As supply voltages continue to decrease, it becomes necessary to provide input and output voltage ranges that can get as close as possible to the supply voltages. The EL5462 has an input range which extends to within 2V of either supply. So, for example, on +5V supplies, the EL5462 has an input range which spans ±3V. The output range of the EL5462 is also quite large, extending to within 1V of the supply rail. On a ±5V supply, the output is therefore capable of swinging from 4V to +4V. Single-supply output range is larger because of the increased negative swing due to the external pull-down resistor to ground. Video Performance For good video performance, an amplifier is required to maintain the same output impedance and the same frequency response as DC levels are changed at the output. This is especially difficult when driving a standard video load of 150, because of the change in output current with DC level. Previously, good differential gain could only be achieved by running high idle currents through the output transistors (to reduce variations in output impedance.) These currents were typically comparable to the entire 1mA supply current of the EL5462 amplifier. Special circuitry has been incorporated in the EL5462 to reduce the variation of output impedance with current output. This results in dG and dP specifications of 0.1% and 0.1°, while driving 150 at a gain of 2. Video performance has also been measured with a 500 load at a gain of +1. Under these conditions, the EL5462 has dG and dP specifications of 0.1% and 0.1°. Output Drive Capability In spite of its low 1.5mA of supply current, the EL5462 is capable of providing a minimum of ±50mA of output current. With a minimum of ±50mA of output drive, the EL5462 is capable of driving 50 loads to both rails, making it an excellent choice for driving isolation transformers in telecommunications applications. Driving Cables and Capacitive Loads When used as a cable driver, double termination is always recommended for reflection-free performance. For those applications, the back-termination series resistor will decouple the EL5462 from the cable and allow extensive capacitive drive. However, other applications may have high capacitive loads without a back-termination resistor. In these applications, a small series resistor (usually between 5 and 50) can be placed in series with the output to eliminate most peaking. The gain resistor (RG) can then be chosen to make up for any gain loss which may be created by this additional resistor at the output. In many cases it is also possible to simply increase the value of the feedback resistor (RF) to reduce the peaking. Current Limiting The EL5462 has no internal current-limiting circuitry. If the output is shorted, it is possible to exceed the Absolute Maximum Rating for output current or power dissipation, potentially resulting in the destruction of the device. Power Dissipation With the high output drive capability of the EL5462, it is possible to exceed the 125°C Absolute Maximum junction temperature under certain very high load current conditions. Generally speaking when RL falls below about 25, it is important to calculate the maximum junction temperature (TJMAX) for the application to determine if power supply voltages, load conditions, or package type need to be modified for the EL5462 to remain in the safe operating area. These parameters are calculated as follows: T JMAX = T MAX +   JA  n  PD MAX  where: • TMAX = Maximum ambient temperature • JA = Thermal resistance of the package • n = Number of amplifiers in the package • PDMAX = Maximum power dissipation of each amplifier in the package PDMAX for each amplifier can be calculated as follows: V OUTMAX PD MAX =  2  V S  I SMAX  +  V S – V OUTMAX   ---------------------------R L FN7492 Rev 0.00 February 14, 2005 Page 7 of 9 EL5462 where: • VS = Supply voltage • ISMAX = Maximum supply current of 1.5mA • VOUTMAX = Maximum output voltage (required) • RL = Load resistance Typical Application Circuits 0.1µF +5V IN+ VS+ IN- VS- OUT 0.1µF -5V 500 5 0.1µF +5V IN+ VS+ IN- VS- 500 5 0.1µF -5V VIN OUT VOUT 500 FIGURE 16. INVERTING 200mA OUTPUT CURRENT DISTRIBUTION AMPLIFIER 500 500 0.1µF +5V IN+ IN500 -5V 500 +5V VIN IN+ IN-5V VS+ VS- OUT 0.1µF 0.1µF VS+ VS- OUT VOUT 0.1µF FIGURE 17. FAST-SETTLING PRECISION AMPLIFIER FN7492 Rev 0.00 February 14, 2005 Page 8 of 9 EL5462 SO Package Outline Drawing NOTE: The package drawing shown here may not be the latest version. To check the latest revision, please refer to the Intersil website at © Copyright Intersil Americas LLC 2005. All Rights Reserved. All trademarks and registered trademarks are the property of their respective owners. For additional products, see www.intersil.com/en/products.html Intersil products are manufactured, assembled and tested utilizing ISO9001 quality systems as noted in the quality certifications found at www.intersil.com/en/support/qualandreliability.html Intersil products are sold by description only. Intersil may modify the circuit design and/or specifications of products at any time without notice, provided that such modification does not, in Intersil's sole judgment, affect the form, fit or function of the product. Accordingly, the reader is cautioned to verify that datasheets are current before placing orders. Information furnished by Intersil is believed to be accurate and reliable. However, no responsibility is assumed by Intersil or its subsidiaries for its use; nor for any infringements of patents or other rights of third parties which may result from its use. No license is granted by implication or otherwise under any patent or patent rights of Intersil or its subsidiaries. For information regarding Intersil Corporation and its products, see www.intersil.com FN7492 Rev 0.00 February 14, 2005 Page 9 of 9