TS6001
A 7ppm/°C, 0.08% Precision +2.5V Voltage Reference in SOT23
FEATURES
DESCRIPTION
The TS6001 is a 3-terminal, series-mode 2.5-V
precision voltage reference and is a pin-for-pin,
identical to the MAX6025 voltage reference with
improved electrical performance. The TS6001
consumes only 31μA of supply current at no-load,
exhibits an initial output voltage accuracy of less than
0.08%, and a low output voltage temperature
coefficient of 7ppm/°C. In addition, the TS6001’s
output stage is stable for all capacitive loads to
2200pF and is capable of sinking and sourcing load
currents up to 500µA.
Improved Electrical Performance
over MAX6025
Initial Accuracy:
0.08% (max) – TS6001A
0.16% (max) – TS6001B
Temperature Coefficient:
7ppm/°C (max) – TS6001A
10ppm/°C (max) – TS6001B
Quiescent Supply Current: 35μA (max)
Low Supply Current Change with VIN: 0.1μA/V
Output Source/Sink Current: ±500µA
Low Dropout at 500μA Load Current: 75mV
Load Regulation: 30ppm/mA
Line Regulation: 10ppm/V
Stable with CLOAD up to 2200pF
APPLICATIONS
Battery-Operated Equipment
Data Acquisition Systems
Hand-Held Equipment
Smart Industrial Transmitters
Industrial and Process-Control Systems
Precision 3V/5V Systems
Hard-Disk Drives
Since the TS6001 is a series-mode voltage reference,
its supply current is not affected by changes in the
applied supply voltage unlike two-terminal shuntmode references that require an external resistor.
The TS6001’s small form factor and low supply
current operation all combine to make it an ideal
choice in low-power, precision applications.
The TS6001 is fully specified over the -40°C to +85°C
temperature range and is available in a 3-pin SOT23
package.
TYPICAL APPLICATION CIRCUIT
Output Voltage Temperature Drift
OUTPUT VOLTAGE - Volt
2.5010
THREE TYPICAL DEVICES
DEVICE #1
2.5005
DEVICE #2
2.5000
DEVICE #3
2.4995
2.4990
-40
-15
10
35
60
85
TEMPERATURE DRIFT- °C
Page 1
© 2014 Silicon Laboratories, Inc. All rights reserved.
TS6001
ABSOLUTE MAXIMUM RATINGS
IN to GND................................................................. -0.3V to +13.5V
OUT to GND.................................................................... -0.3V to 7V
Short Circuit to GND or IN (VIN < 6V) .............................. Continuous
Output Short Circuit to GND or IN (VIN ≥ 6V) .............................. 60s
Continuous Power Dissipation (TA = +70°C)
3-Pin SOT23 (Derate at 4.0mW/°C above +70°C) .......... 320mW
Operating Temperature Range ................................. -40°C to +85°C
Storage Temperature Range .................................. -65°C to +150°C
Lead Temperature (Soldering, 10s)...................................... +300°C
Electrical and thermal stresses beyond those listed under “Absolute Maximum Ratings” may cause permanent damage to the device. These
are stress ratings only and functional operation of the device at these or any other condition beyond those indicated in the operational sections
of the specifications is not implied. Exposure to any absolute maximum rating conditions for extended periods may affect device reliability and
lifetime.
PACKAGE/ORDERING INFORMATION
ORDER NUMBER
PART
CARRIERQUANTITY
MARKING
TS6001AIG325
Tape
& Reel
-----
TS6001AIG325T
Tape
& Reel
3000
TS6001BIG325
Tape
& Reel
-----
Tape
& Reel
3000
AAG
AAH
TS6001BIG325T
Lead-free Program: Silicon Labs supplies only lead-free packaging.
Consult Silicon Labs for products specified with wider operating temperature ranges.
Page 2
TS6001 Rev. 1.0
TS6001
ELECTRICAL CHARACTERISTICS
VIN = +5V, IOUT = 0, TA = TMIN to TMAX, unless otherwise noted. Typical values are at TA = +25°C. See Note 1.
PARAMETER
OUTPUT
SYMBOL
CONDITIONS
TS6001A
Output Voltage
VOUT
TA = +25°C
TS6001B
Output Voltage Temperature
Coefficient (See Note 2)
Line Regulation
Load Regulation
Dropout Voltage (See Note 3)
OUT Short-Circuit Current
Temperature Hysteresis
(See Note 4)
Long-Term Stability
(See Note 5)
DYNAMIC
Noise Voltage
Ripple Rejection
Turn-On Settling Time
Capacitive-Load Stability
Range
INPUT
Supply Voltage Range
Quiescent Supply Current
Change in Supply Current
TCVOUT
(∆VOUT/VOUT)
/∆VIN
(∆VOUT/VOUT)
/∆IOUT
VIN -VOUT
ISC
∆VOUT/ time
eOUT
∆VOUT/ ∆VIN
tR
0°C ≤ TA ≤ +85°C
-40°C ≤ TA ≤ +85°C
0°C ≤ TA ≤ +85°C
-40°C ≤ TA ≤ +85°C
MIN
TYP
MAX
UNITS
2.498
-0.08
2.496
-0.16
2.500
V
%
V
%
2
2.5
3
4
2.502
0.08
2.504
0.16
7
10
10
15
10
30
30
70
75
4
4
240
320
150
TS6001A
TS6001B
(VOUT + 0.2V) ≤ VIN ≤ 12.6V
Sourcing
Sinking
IOUT = 500μA
VOUT Short to GND
VOUT Short to IN
0 ≤ IOUT ≤ 500μA
-500μA ≤ IOUT ≤ 0
2.500
ppm/°C
ppm/V
ppm/mA
mV
mA
100
ppm
168hr at TA = +25°C
75
ppm/
168hr
f = 0.1Hz to 10Hz
f = 10Hz to 10kHz
VIN = 5V ±100mV, f = 120Hz
To VOUT = 0.1% of final value, COUT = 50 pF
50
75
82
340
μVP-P
μVRMS
dB
μs
COUT
See Note 6
VIN
IIN
IIN/VIN
Guaranteed by line-regulation test
(VOUT + 0.2V) ≤ VIN ≤ 12.6V
0
VOUT + 0.2
31
0.1
2200
pF
12.6
35
2
V
μA
μA/V
Note 1: All devices are 100% production tested at TA = +25°C and are guaranteed by characterization for TA = TMIN to TMAX, as specified.
Note 2: Temperature Coefficient is measured by the “box” method; i.e., the maximum ∆VOUT is divided by the maximum ∆T.
Note 3: Dropout voltage is the minimum input voltage at which VOUT changes ≤0.2% from VOUT at VIN = 5.0V.
Note 4: Temperature hysteresis is defined as the change in the +25°C output voltage before and after cycling the device from +25°C to TMIN to
+25°C and from +25°C to TMAX to +25°C.
Note 5: Reference long-term drift or stability listed in the table is an intermediate result of a 1000-hour evaluation. Soldered onto a printed
circuit board (pcb), voltage references exhibit more drift early in the evaluation because of assembly-induced differential stresses
between the package and the pcb.
Note 6: Not production tested; guaranteed by design.
TS6001 Rev. 1.0
Page 3
TS6001
TYPICAL PERFORMANCE CHARACTERISTICS
VIN = +5V; IOUT = 0mA; TA = +25°C, unless otherwise noted.
Output Voltage Histogram
Output Voltage Temperature Drift
9
2.5010
THREE TYPICAL DEVICES
OUTPUT VOLTAGE - Volt
8
NUMBER OF UNITS
7
6
5
4
3
2
DEVICE #1
2.5005
DEVICE #2
2.5000
DEVICE #3
2.4995
1
0
2.4990
-0.02
0.02
0
0.04
-40
Long-Term Output Voltage Drift
Line Regulation
85
120
OUTPUT VOLTAGE CHANGE - ppm
OUTPUT VOLTAGE - Volt
60
TEMPERATURE DRIFT- °C
THREE TYPICAL DEVICES
DEVICE #1
2.5025
2.5000
DEVICE #2
2.4975
DEVICE #3
TA = -40°C
80
TA = +25°C
40
TA = +85°C
0
-40
2.4950
0
42
84
126
2
168
6
4
8
10
12
TIME - Hours
SUPPLY VOLTAGE - Volt
Dropout Voltage vs Source Current
Load Regulation
0.4
14
160
OUTPUT VOLTAGE CHANGE - ppm
DROPOUT VOLTAGE - V
35
10
OUTPUT VOLTAGE ERROR - %
2.5050
0.3
TA = +85°C
0.2
TA = +25°C
TA = -40°C
0.1
0
0
200
400
600
800
SOURCE CURRENT- µA
Page 4
-15
1000
80
TA = -40°C
TA = +85°C
0
TA = +25°C
-80
-160
-0.5
-0.25
0
0.25
0.5
LOAD CURRENT- mA
TS6001 Rev. 1.0
TS6001
TYPICAL PERFORMANCE CHARACTERISTICS
VIN = +5V; IOUT = 0mA; TA = +25°C, unless otherwise noted.
Power Supply Rejection vs Frequency
Supply Current vs Input Voltage
100
SUPPLY CURENT - µA
POWER SUPPLY REJECTION – mV/V
40
VCC =+5.5V±0.25V
10
1
36
32
28
24
0.1
20
0.01
2
100
1k
10k
100k
6
4
8
10
12
14
1M
INPUT VOLTAGE - Volt
FREQUENCY - Hz
Output Impedance vs Frequency
Supply Current vs Temperature
10k
VCC =+12.5V
OUTPUT IMPEDANCE - Ω
SUPPLY CURENT - µA
40
VCC =+7.5V
35
30
VCC = +2.5V, +5.5V
25
1k
100
10
1
0.1
20
-15
10
35
60
85
0.1
1
100
10k
TEMPERATURE - °C
FREQUENCY - Hz
0.1Hz to 10Hz Output Noise
Power-On Transient Response
OUTPUT
1V/DIV
VOUT(N)
10µV/DIV
46µVPP
1s/DIV
TS6001 Rev. 1.0
1M
INPUT
2V/DIV
-40
200µs/DIV
Page 5
TS6001
TYPICAL PERFORMANCE CHARACTERISTICS
IOUT
1mA/DIV
Large-signal Load Transient Response
IOUT = 0mA → 1mA → 0mA, AC-Coupled
OUTPUT
200mV/DIV
IOUT = 0µA → 50µA → 0µA, AC-Coupled
OUTPUT
20mV/DIV
IOUT
50µA/DIV
VIN = +5V; IOUT = 0mA; TA = +25°C, unless otherwise noted.
Small-signal Load Transient Response
10µs/DIV
10µs/DIV
VIN
200mV/DIV
Line Transient Response
OUTPUT
100mV/DIV
VIN =5V±0.25V, AC-Coupled
2µs/DIV
Page 6
TS6001 Rev. 1.0
TS6001
PIN FUNCTIONS
PIN
1
2
3
NAME
IN
OUT
GND
FUNCTION
Supply Voltage Input
+2.5V Output
Ground
DESCRIPTION/THEORY OF OPERATION
The TS6001 incorporates a precision 1.25-V
bandgap reference that is followed by an output
amplifier configured to amplify the base bandgap
output voltage to a 2.5-V output. The design of the
bandgap reference incorporates proprietary circuit
design techniques to achieve its low temperature
coefficient of 7ppm/°C and initial output voltage
accuracy less than 0.08%. The design of the output
amplifier’s frequency compensation does not require
a separate compensation capacitor and is stable
with capacitive loads up to 2200pF. The design of
the output amplifier also incorporates low headroom
design as it can source and sink load currents to
500μA with a dropout voltage less than 100mV.
APPLICATIONS INFORMATION
Power Supply Input Bypass Capacitance
If there are other analog ICs within 1 to 2 inches of
the TS6001 with their own bypass capacitors to
GND, the TS6001 would not then require its own
bypass capacitor. If this is not the case, then it is
considered good analog circuit engineering practice
to place a 0.1µF ceramic capacitor in as close
proximity to the TS6001 as practical with very short
pcb track lengths.
Output/Load Capacitance Considerations
As mentioned previously, the TS6001 does not
require a separate, external capacitor at VOUT for
transient response stability as it is stable for
capacitive loads up to 2200pF. For improved load
regulation transient response, the use of a capacitor
at VOUT helps to reduce output voltage
overshoot/undershoot to transient load current
conditions. Figure 1 illustrates the TS6001’s
transient load regulation performance with CLOAD =
0pF to a 50-µA transient upon a 175-µA steady-state
load current. Peak transients are approximately
20mV and the TS6001 settles in less than 8µs. As
shown in Figure 2, adding a capacitive load reduces
peak transients at the expense of settling time. In
this case, the TS6001’s output was loaded with
CLOAD = 1000pF and subjected to the same transient
load current profile. Peak transients were reduced to
less than 10mV and the TS6001 settled in less than
10µs.
IOUT = 175µA → 225µA → 175µA
OUTPUT
20mV/DIV
OUTPUT
20mV/DIV
IOUT
50µA/DIV
IOUT
50µA/DIV
IOUT = 175µA → 225µA → 175µA
Figure 1: TS6001 Transient Load Regulation
Response, CLOAD = 0pF
TS6001 Rev. 1.0
Figure 2: TS6001 Transient Load Regulation
Response, CLOAD = 1000pF
Page 7
TS6001
Supply Current
outputs of precision voltage references is illustrated
in Figure 3.
The TS6001 exhibits excellent dc line regulation as
its supply current changes slightly as a function of
the applied supply voltage. Because of a unique bias
loop design, the change in its supply current as a
function of supply voltage (its ∆IIN/∆VIN) is less than
0.1μA/V. Since the TS6001 is a series-mode
reference, load current is drawn from the supply
voltage only when required. In this case, circuit
efficiency is maintained at all applied supply
voltages. Reducing power dissipation and extending
battery life are the net benefits of improved circuit
efficiency.
When the applied supply voltage is less than the
minimum specified input voltage of the TS6001 (for
example, during the power-up or “cold-start”
transition), the TS6001 performs an internal
calibration routine and can draw up to 200μA above
its nominal, steady-state supply current. This internal
calibration sequence also dominates the TS6001’s
turn-on time. To ensure reliable power-up behavior,
the input power source must have sufficient reserve
power to provide the extra supply current drawn
during the power-up transition.
Voltage Reference Turn-On Time
With a (VIN – VOUT) voltage differential larger than
200mV and ILOAD = 0mA, the TS6001’s typical
combined turn-on and settling time to within 0.1% of
its 2.5V final value is approximately 340μs.
Output Voltage Hysteresis
Reference output voltage thermal hysteresis is the
change in the reference’s +25°C output voltage after
temperature cycling from +25°C to +85°C to +25°C
and from +25°C to -40°C to +25°C. Thermal
hysteresis is caused by differential package stress
impressed upon the TS6001’s internal bandgap core
transistors and depends on whether the reference IC
was previously at a higher or lower temperature. At
100ppm, the TS6001’s typical temperature
hysteresis is equal to 0.25mV with respect to a 2.5V
output voltage.
Connecting Two or More TS6001s in Stacked
VOUT Arrangements
In many applications, it is desired to combine the
outputs of two or more precision voltage references,
especially if the combined output voltage is not
available or is an uncommon output voltage. One
such technique for combining (or “stacking”) the
Page 8
Figure 3: Connecting Two TS6001-2.5s in a
Stacked VREFOUT Arrangement
In this example and powered by an unregulated
supply voltage (VIN ≥ +5.2V), two TS6001-2.5
precision voltage references are used. The GND
terminal of REFA is connected to the OUT terminal
of REFB. This connection produces two output
voltages, VREFOUT1 and VREFOUT2, where VREFOUT1 is
the terminal voltage of REFB and VREFOUT2 is
VREFOUT1 plus the OUT terminal voltage of REFB. By
implementing this stacked arrangement with a pair
of TS6001-2.5s, VREFOUT2 is 5V and VREFOUT1 is 2.5V.
Although the TS6001-2.5s do not specifically require
input bypass capacitors, it is good engineering
practice to bypass both references from VIN to the
global GND terminal (at REFB). If either or both
reference ICs are required to drive a load
capacitance, it is also good engineering practice to
route the load capacitor’s return lead to each
reference’s corresponding REF’s GND terminal. The
circuit’s minimum input supply voltage, VIN, is
determined by VREFOUT2 and REFB’s dropout voltage
(75mV, typically).
How to Configure the TS6001 into a GeneralPurpose Current Source
In many low-voltage applications, a general-purpose
current source is needed with very good line
regulation. The TS6001-2.5 can be configured as a
grounded-load, floating current source as shown
Figure 4. In this example, the TS6001-2.5’s output
voltage is bootstrapped across an external resistor
(R1 + P1) which, in turn, sets the output current. The
circuit’s total output current is IOUT = ISET+IQSC where
IQSC is the TS6001 supply current (up to 35µA). For
TS6001 Rev. 1.0
TS6001
improved output current accuracy, ISET should be at
least 10 times IQSC.
The circuit illustrated in Figure 5 avoids the need for
multiple op amps and well-matched resistors by
using an active integrator circuit. In this circuit, the
voltage reference’s output is used as the input signal
to the integrator. Because of op amp loop action, the
integrator adjusts its output voltage to establish the
correct relationship between the reference’s OUT
and GND terminals (=VREF). In other words, the
output voltage polarity of the integrator stage is
opposite that of the reference’s output voltage.
Figure 4: A Low-power, General-Purpose Current
Source.
A Negative, Precision Voltage Reference without
Precision Resistors
When using current-output DACs, it is oftentimes
desired that the polarity of the output signal voltage
is the same as the external reference voltage. There
are two conventional techniques used to accomplish
this objective: a) inverting the full-scale DAC output
voltage or b) converting a current-output DAC into a
voltage-switching DAC. In the first technique, an op
amp and pair of precision resistors would be
required because the DAC’s output signal voltage
requires re-inversion to match the polarity of the
external reference voltage. The second technique is
a bit more involved and requires converting the
current-output DAC into a voltage-switching DAC by
driving the DAC’s VREF and IOUT terminals in
reverse. Additional components required are two
precision resistors, an op amp, and an external
voltage reference, typically a 1.25-V reference. If the
1.25-V full-scale output voltage requires scaling to a
2.5-V or a 5-V full scale, then a second op amp and
pair of precision resistors would be necessary to
perform the amplification.
To avoid the need for either re-inversion of the
current-switching DAC’s output voltage or amplifying
the voltage-switching DAC’s output voltage, it would
then be desired to apply a negative voltage
reference to the original current-switching DAC. In
general, any positive voltage reference can be
converted into a negative voltage reference using
pair of matched resistors and an op amp configured
for inverting mode operation. The disadvantage to
this approach is that the largest single source of
error in the circuit is the relative matching of the
resistors used.
TS6001 Rev. 1.0
Figure 5: How to Convert a VREF to a –VREF without
Precision Resistors.
The 2200pF capacitor at the output of the TS6001 is
optional and the resistor in series with the output of
the op amp should be empirically determined based
on the amplifier choice and whether the amplifier is
required to drive a large capacitive load.
Rail-to-rail output op amps used for the integrator
stage work best in this application; however, these
types of op amps require a finite amount of
headroom (in the millivolt range) when sinking load
current. Therefore, good engineering judgment is
always recommended when selecting the most
appropriate negative supply for the circuit.
How to Use the TS6001 in a High-Input Voltage
Floating Current Source
By adopting the technique previously shown in
Figure 2, the basic floating current source circuit can
be adapted to operate at much higher supply
voltages beyond the supply voltage rating of the
TS6001-2.5 by adding a discrete n-channel JFET.
As shown in Figure 6, the JFET acts as a supply
voltage regulator since its source voltage will always
be 2.5V higher than VSY. The circuit minimizes
reference IC self-heating because the JFET and the
2N3904 NPN transistor carry the load current. This
circuit can operate up to +35V and is determined by
the BVDS breakdown voltage of the external JFET.
Page 9
TS6001
For example, if VSY is 0V, then the upper input
supply voltage level for the circuit is 35V. With a
2.1kΩ load and the TS6001’s supply current of 35µA
(max), this circuit supplies approximately a 1.23-mA
current to the load.
excellent load regulation while sourcing load
currents up to 150mA. If the application circuit is
designed to operate across a wide temperature
range, it is recommended that circuit performance is
thoroughly evaluated across the PNP transistor’s
beta (β, or current gain) distribution. When the PNP
transistor’s current gain is a minimum, the increase
in base current must be absorbed by the TS6001 for
a given load current. For higher output load currents,
higher output power PNP transistors can be used so
long as good thermal management techniques are
applied and transistor current-gain vs ambient
temperature behavior is evaluated.
Figure 6: Using the TS6001-2.5 in a High-Input
Voltage Floating Current Source.
In many current source applications, the possibility
of an output short-circuit condition - whether
transient or sustained - exists. It is recommended to
test thoroughly for either scenario to prevent the
possibility that the TS6001 would be exposed to a
total voltage from its IN terminal to GND terminal
higher than its absolute maximum rating of 13.5V.
Boosting the TS6001’s Output Current Drive
While the TS6001 is capable of sourcing up to
500µA with excellent load regulation, there are
applications where tight load regulation is required at
much higher output load currents. By adding a
general-purpose, industry-standard PNP transistor
and one resistor to the TS6001’s basic configuration
as shown in Figure 7, increasing a precision
Figure 7: Boosting the TS6001’s Output Current
with an External PNP Transistor.
reference’s output source current drive is
straightforward. Using a 2N2905 PNP transistor and
a 1.5kΩ resistor, the TS6001 is able to maintain
Page 10
TS6001 Rev. 1.0
TS6001
Generating Positive and Negative Low-Power
Voltage References
The circuit in Figure 8 uses a CD4049 hex inverter
and a few external capacitors as the power supply to
a dual-supply precision op amp to form a ±2.5V
precision, bipolar output voltage reference around
the TS6001. The CD4049-based circuit is a discrete
charge pump voltage doubler/inverter that generates
±6V supplies for any precision, micropower op amp
with VOS and TCVOS specifications consistent with
the TS6001’s initial accuracy and output voltage drift
performance.
Figure 8: Generating Positive and Negative 2.5V References from a Single +3V or +5V
Supply.
TS6001 Rev. 1.0
Page 11
TS6001
PACKAGE OUTLINE DRAWING
3-Pin SOT23 Package Outline Drawing
(N.B., Drawings are not to scale)
Patent Notice
Silicon Labs invests in research and development to help our customers differentiate in the market with innovative low-power, small size,
analog-intensive mixed-signal solutions. Silicon Labs' extensive patent portfolio is a testament to our unique approach and world-class
engineering team.
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