Dual IF Receiver
AD6642
FEATURES
APPLICATIONS
Communications
Diversity radio and smart antenna (MIMO) systems
Multimode digital receivers (3G)
WCDMA, LTE, CDMA2000
WiMAX, TD-SCDMA
I/Q demodulation systems
General-purpose software radios
FUNCTIONAL BLOCK DIAGRAM
AVDD
AGND
DRVDD
DRGND
AD6642
VIN+A
PIPELINE
ADC
VIN–A
DC0±AB
14
NOISE SHAPING
REQUANTIZER
11
VCMA
VIN+B
PIPELINE
ADC
VIN–B
14
NOISE SHAPING
REQUANTIZER
VCMB
11
DATA MULTIPLEXER
AND LVDS DRIVERS
D0±AB
D10±AB
MODE
REFERENCE
CLOCK
DIVIDER
PDWN
SERIAL PORT
SCLK
SDIO
SYNC
CSB
CLK+ CLK–
08563-001
11-bit, 200 MSPS output data rate per channel
Integrated noise shaping requantizer (NSR)
Performance with NSR enabled
SNR: 75.5 dBFS in 40 MHz band to 70 MHz @ 185 MSPS
SNR: 73.7 dBFS in 60 MHz band to 70 MHz @ 185 MSPS
Performance with NSR disabled
SNR: 66.5 dBFS to 70 MHz @ 185 MSPS
SFDR: 83 dBc to 70 MHz @ 185 MSPS
Low power: 0.62 W @ 185 MSPS
1.8 V analog supply operation
1.8 V LVDS (ANSI-644 levels) output
1-to-8 integer clock divider
Internal ADC voltage reference
1.75 V p-p analog input range (programmable to 2.0 V p-p)
Differential analog inputs with 800 MHz bandwidth
95 dB channel isolation/crosstalk
Serial port control
User-configurable built-in self-test (BIST) capability
Energy-saving power-down modes
Figure 1.
PRODUCT HIGHLIGHTS
1.
2.
3.
4.
5.
6.
7.
Two ADCs are contained in a small, space-saving,
10 mm × 10 mm × 1.4 mm, 144-ball CSP_BGA package.
Pin selectable noise shaping requantizer (NSR) function
that allows for improved SNR within a reduced bandwidth
of up to 60 MHz at 185 MSPS.
LVDS digital output interface configured for low cost
FPGA families.
120 mW per ADC core power consumption.
Operation from a single 1.8 V supply.
Standard serial port interface (SPI) that supports various
product features and functions, such as data formatting
(offset binary or twos complement), NSR, power-down,
test modes, and voltage reference mode.
On-chip integer 1-to-8 input clock divider and multichip
sync function to support a wide range of clocking schemes
and multichannel subsystems.
Rev. A
Information furnished by Analog Devices is believed to be accurate and reliable. However, no
responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other
rights of third parties that may result from its use. Specifications subject to change without notice. No
license is granted by implication or otherwise under any patent or patent rights of Analog Devices.
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Tel: 781.329.4700
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Fax: 781.461.3113 ©2009–2010 Analog Devices, Inc. All rights reserved.
AD6642
TABLE OF CONTENTS
Features .............................................................................................. 1
Power Dissipation and Standby Mode .................................... 20
Applications....................................................................................... 1
Channel/Chip Synchronization................................................ 20
Functional Block Diagram .............................................................. 1
Digital Outputs ........................................................................... 21
Product Highlights ........................................................................... 1
Timing ......................................................................................... 21
Revision History ............................................................................... 2
Noise Shaping Requantizer (NSR) ............................................... 22
General Description ......................................................................... 3
22% BW Mode (>40 MHz @ 184.32 MSPS)........................... 22
Specifications..................................................................................... 4
33% BW Mode (>60 MHz @ 184.32 MSPS)........................... 22
DC Specifications ......................................................................... 4
MODE Pin................................................................................... 23
AC Specifications.......................................................................... 5
Built-In Self-Test (BIST) and Output Test .................................. 24
Digital Specifications ................................................................... 6
Built-In Self-Test (BIST)............................................................ 24
Switching Specifications .............................................................. 7
Output Test Modes..................................................................... 24
Timing Specifications .................................................................. 8
Serial Port Interface (SPI).............................................................. 25
Absolute Maximum Ratings............................................................ 9
Configuration Using the SPI..................................................... 25
Thermal Characteristics .............................................................. 9
Hardware Interface..................................................................... 25
ESD Caution.................................................................................. 9
Memory Map .................................................................................. 26
Pin Configuration and Function Descriptions........................... 10
Reading the Memory Map Register Table............................... 26
Typical Performance Characteristics ........................................... 12
Memory Map Register Table..................................................... 27
Equivalent Circuits ......................................................................... 15
Memory Map Register Descriptions........................................ 29
Theory of Operation ...................................................................... 16
Applications Information .............................................................. 30
ADC Architecture ...................................................................... 16
Design Guidelines ...................................................................... 30
Analog Input Considerations.................................................... 16
Outline Dimensions ....................................................................... 31
Clock Input Considerations ...................................................... 18
Ordering Guide .......................................................................... 31
REVISION HISTORY
7/10—Rev. 0 to Rev. A
Changes to ADC Architecture Section........................................ 16
Changes to Figure 34 and Figure 35............................................. 18
Changes to Timing Section and Data Clock Output (DCO)
Section.............................................................................................. 21
Changes to 22% BW Mode (>40 MHz @ 184.32 MSPS) Section
and 33% BW Mode (>60 MHz @ 184.32 MSPS) Section ......... 22
Changes to Design Guidelines Section........................................ 30
10/09—Revision 0: Initial Version
Rev. A | Page 2 of 32
AD6642
GENERAL DESCRIPTION
The AD6642 is an 11-bit, 200 MSPS, dual-channel intermediate
frequency (IF) receiver specifically designed to support multiantenna systems in telecommunication applications where high
dynamic range performance, low power, and small size are desired.
The device consists of two high performance analog-to-digital
converters (ADCs) and noise shaping requantizer (NSR) digital
blocks. Each ADC consists of a multistage, differential pipelined
architecture with integrated output error correction logic. The
ADC features a wide bandwidth switched-capacitor sampling
network within the first stage of the differential pipeline. An
integrated voltage reference eases design considerations. A duty
cycle stabilizer (DCS) compensates for variations in the ADC
clock duty cycle, allowing the converters to maintain excellent
performance.
Each ADC output is connected internally to an NSR block. The
integrated NSR circuitry allows for improved SNR performance
in a smaller frequency band within the Nyquist bandwidth. The
device supports two different output modes selectable via the
external MODE pin or the SPI.
With the NSR feature enabled, the outputs of the ADCs are
processed such that the AD6642 supports enhanced SNR
performance within a limited portion of the Nyquist bandwidth
while maintaining an 11-bit output resolution. The NSR block
can be programmed to provide a bandwidth of either 22% or
33% of the sample clock. For example, with a sample clock rate
of 185 MSPS, the AD6642 can achieve up to 75.5 dBFS SNR for
a 40 MHz bandwidth in the 22% mode and up to 73.7 dBFS
SNR for a 60 MHz bandwidth in the 33% mode.
With the NSR block disabled, the ADC data is provided directly to
the output with a resolution of 11 bits. The AD6642 can achieve
up to 66.5 dBFS SNR for the entire Nyquist bandwidth when
operated in this mode. This allows the AD6642 to be used in
telecommunication applications such as a digital predistortion
observation path where wider bandwidths are desired.
After digital signal processing, multiplexed output data is
routed into two 11-bit output ports such that the maximum
data rate is 400 Mbps (DDR). These outputs are set at 1.8 V
LVDS and support ANSI-644 levels.
The AD6642 receiver digitizes a wide spectrum of IF frequencies.
Each receiver is designed for simultaneous reception of a separate
antenna. This IF sampling architecture greatly reduces component cost and complexity compared with traditional analog
techniques or less integrated digital methods.
Flexible power-down options allow significant power savings.
Programming for device setup and control is accomplished
using a 3-wire SPI-compatible serial interface with numerous
modes to support board-level system testing.
The AD6642 is available in a Pb-free/RoHS compliant, 144-ball,
10 mm × 10 mm chip scale package ball grid array (CSP_BGA)
and is specified over the industrial temperature range of −40°C
to +85°C.
Rev. A | Page 3 of 32
AD6642
SPECIFICATIONS
DC SPECIFICATIONS
AVDD = 1.8 V, DRVDD = 1.8 V, fS = 185 MSPS, 1.75 V p-p differential input, VIN = −1.0 dBFS differential input, and default SPI, unless
otherwise noted.
Table 1.
Parameter
RESOLUTION
ACCURACY
No Missing Codes
Offset Error
Gain Error
Differential Nonlinearity (DNL) 1
Integral Nonlinearity (INL)1
MATCHING CHARACTERISTIC
Offset Error
Gain Error
TEMPERATURE DRIFT
Offset Error
Gain Error
ANALOG INPUT
Input Range
Input Common-Mode Voltage
Input Resistance (Differential)
Input Capacitance 2
POWER SUPPLIES
Supply Voltage
AVDD
DRVDD
Supply Current
IAVDD1
IDRVDD1 (1.8 V LVDS)
POWER CONSUMPTION
Sine Wave Input1
Standby Power 3
Power-Down Power
1
2
3
Temperature
Full
Full
Full
Full
Full
Full
Full
Full
Min
11
−4.5
−2.4
Full
Full
Typ
Max
Unit
Bits
Guaranteed
2
±3
±0.1
±0.2
7.4
±7
±0.5
±0.5
mV
% FSR
LSB
LSB
2.5
±1
8.3
±3
mV
% FSR
2
40
ppm/°C
ppm/°C
Full
Full
Full
Full
1.4
1.75
0.9
20
5
2.0
V p-p
V
kΩ
pF
Full
Full
1.7
1.7
1.8
1.8
1.9
1.9
V
V
Full
Full
265
79
291
89
mA
mA
Full
Full
Full
619
83
4.5
684
mW
mW
mW
Measured with a 10 MHz, 0 dBFS sine wave, with 100 Ω termination on each LVDS output pair.
Input capacitance refers to the effective capacitance between one differential input pin and AGND.
Standby power is measured with a dc input and the CLKx pins inactive (set to AVDD or AGND).
Rev. A | Page 4 of 32
18
AD6642
AC SPECIFICATIONS
AVDD = 1.8 V, DRVDD = 1.8 V, fS = 185 MSPS, 1.75 V p-p differential input, VIN = −1.0 dBFS differential input, and default SPI, unless
otherwise noted.
Table 2.
Parameter 1
SIGNAL-TO-NOISE-RATIO (SNR)—NSR DISABLED
fIN = 30 MHz
fIN = 70 MHz
fIN = 170 MHz
fIN = 250 MHz
SIGNAL-TO-NOISE-RATIO (SNR)—NSR ENABLED
22% BW Mode
fIN = 70 MHz
fIN = 170 MHz
fIN = 230 MHz
33% BW Mode
fIN = 70 MHz
fIN = 170 MHz
fIN = 230 MHz
SIGNAL-TO-NOISE-AND DISTORTION (SINAD)
fIN = 30 MHz
fIN = 70 MHz
fIN = 170 MHz
fIN = 250 MHz
EFFECTIVE NUMBER OF BITS (ENOB)
fIN = 30 MHz
fIN = 70 MHz
fIN = 170 MHz
fIN = 250 MHz
WORST SECOND OR THIRD HARMONIC
fIN = 30 MHz
fIN = 70 MHz
fIN = 170 MHz
fIN = 250 MHz
SPURIOUS-FREE DYNAMIC RANGE (SFDR)
fIN = 30 MHz
fIN = 70 MHz
fIN = 170 MHz
fIN = 250 MHz
WORST OTHER HARMONIC (FOURTH THROUGH EIGHTH)
fIN = 30 MHz
fIN = 70 MHz
fIN = 170 MHz
fIN = 250 MHz
TWO-TONE SFDR (−7 dBFS)
fIN1 = 169 MHz, fIN2 = 172 MHz
CROSSTALK 2
ANALOG INPUT BANDWIDTH
1
2
Temperature
25°C
25°C
Full
25°C
Min
65.7
Typ
Max
Unit
66.5
66.5
66.1
65.5
dBFS
dBFS
dBFS
dBFS
dBFS
dBFS
dBFS
25°C
Full
25°C
72.8
75.5
74.4
72.8
25°C
Full
25°C
71.0
73.7
72.6
71.0
dBFS
dBFS
dBFS
65.5
66.3
65.6
64.3
dBFS
dBFS
dBFS
dBFS
10.6
10.7
10.6
10.3
Bits
Bits
Bits
Bits
−90
−83
−78
−80
dBc
dBc
dBc
dBc
90
83
78
80
dBc
dBc
dBc
dBc
−100
−96
−90
−95
dBc
dBc
dBc
dBc
82
95
800
dBc
dB
MHz
25°C
25°C
Full
25°C
25°C
25°C
Full
25°C
25°C
25°C
Full
25°C
25°C
25°C
Full
25°C
25°C
25°C
Full
25°C
25°C
Full
25°C
64.1
10.3
−72
72
−82
See the AN-835 Application Note, Understanding High Speed ADC Testing and Evaluation, for a complete set of definitions.
Crosstalk is measured at 155 MHz with −1 dBFS on one channel and no input on the alternate channel.
Rev. A | Page 5 of 32
AD6642
DIGITAL SPECIFICATIONS
AVDD = 1.8 V, DRVDD = 1.8 V, fS = 185 MSPS, 1.75 V p-p differential input, VIN = −1.0 dBFS differential input, and default SPI, unless
otherwise noted.
Table 3.
Parameter
DIFFERENTIAL CLOCK INPUTS (CLK+, CLK−)
Logic Compliance
Internal Common-Mode Bias
Differential Input Voltage
Input Voltage Range
High Level Input Voltage
Low Level Input Voltage
High Level Input Current
Low Level Input Current
Input Resistance
Input Capacitance
SYNC INPUT
Logic Compliance
Internal Bias
Input Voltage Range
High Level Input Voltage
Low Level Input Voltage
High Level Input Current
Low Level Input Current
Input Resistance
Input Capacitance
LOGIC INPUT (CSB) 1
High Level Input Voltage
Low Level Input Voltage
High Level Input Current
Low Level Input Current
Input Resistance
Input Capacitance
LOGIC INPUT (SCLK) 2
High Level Input Voltage
Low Level Input Voltage
High Level Input Current
Low Level Input Current
Input Resistance
Input Capacitance
LOGIC INPUT/OUTPUT (SDIO)2
High Level Input Voltage
Low Level Input Voltage
High Level Input Current
Low Level Input Current
Input Resistance
Input Capacitance
LOGIC INPUT (MODE)1
High Level Input Voltage
Low Level Input Voltage
High Level Input Current
Low Level Input Current
Temperature
Full
Full
Full
Full
Full
Full
Full
Full
Full
Full
Full
Full
Full
Full
Full
Full
Full
Min
Typ
Max
Unit
3.6
AVDD + 0.2
2.0
0.8
+10
+10
12
V
V p-p
V
V
V
μA
μA
kΩ
pF
AVDD
AVDD
0.6
+100
+100
20
V
V
V
V
μA
μA
kΩ
pF
CMOS/LVDS/LVPECL
0.9
0.2
AGND − 0.3
1.2
0
−10
−10
8
10
4
CMOS
0.9
AGND
1.2
AGND
−100
−100
12
Full
Full
Full
Full
Full
Full
1.22
0
−10
40
Full
Full
Full
Full
Full
Full
1.22
0
−92
−10
Full
Full
Full
Full
Full
Full
1.22
0
−10
38
Full
Full
Full
Full
1.22
0
−10
40
16
1
2.1
0.6
+10
132
V
V
μA
μA
kΩ
pF
2.1
0.6
−135
+10
V
V
μA
μA
kΩ
pF
2.1
0.6
+10
128
V
V
μA
μA
kΩ
pF
2.1
0.6
+10
132
V
V
μA
μA
26
2
26
2
26
5
Rev. A | Page 6 of 32
AD6642
Parameter
Input Resistance
Input Capacitance
LOGIC INPUT (PDWN)2
High Level Input Voltage
Low Level Input Voltage
High Level Input Current
Low Level Input Current
Input Resistance
Input Capacitance
DIGITAL OUTPUTS (LVDS)
Differential Output Voltage (VOD)
Output Offset Voltage (VOS)
1
2
Temperature
Full
Full
Min
Full
Full
Full
Full
Full
Full
1.22
0
−90
−10
Full
Full
247
1.125
Typ
26
2
Max
Unit
kΩ
pF
2.1
0.6
−134
+10
V
V
μA
μA
kΩ
pF
454
1.375
mV
V
26
5
Pull up.
Pull down.
SWITCHING SPECIFICATIONS
AVDD = 1.8 V, DRVDD = 1.8 V, fS = 185 MSPS, 1.75 V p-p differential input, VIN = −1.0 dBFS differential input, and default SPI, unless
otherwise noted.
Table 4.
Parameter
CLOCK INPUT PARAMETERS
Input Clock Rate
Conversion Rate 1
CLK Pulse Width High (tCH)
Aperture Delay (tA)
Aperture Uncertainty (Jitter, tJ)
DATA OUTPUT PARAMETERS
Data Propagation Delay (tPD)
DCO Propagation Delay (tDCO)
DCO to Data Skew (tSKEW)
Pipeline Delay (Latency)
With NSR Enabled
Wake-Up Time 2
OUT-OF-RANGE RECOVERY TIME
1
2
Temperature
Full
Full
Full
Full
Full
Full
Full
Full
Full
Full
Full
Full
Min
Typ
40
185
2.7
1.3
0.13
3.0
3.2
−0.4
4.35
4.55
Conversion rate is the clock rate after the divider.
Wake-up time is dependent on the value of the decoupling capacitors.
Rev. A | Page 7 of 32
−0.2
9
12
1.2
2
Max
Unit
625
200
MHz
MSPS
ns
ns
ps rms
5.7
5.9
0
ns
ns
ns
Cycles
Cycles
μs
Cycles
AD6642
TIMING SPECIFICATIONS
AVDD = 1.8 V, DRVDD = 1.8 V, fS = 185 MSPS, 1.75 V p-p differential input, VIN = −1.0 dBFS differential input, and default SPI, unless
otherwise noted.
Table 5.
Parameter
SYNC TIMING REQUIREMENTS
tSSYNC
tHSYNC
SPI TIMING REQUIREMENTS
tDS
tDH
tCLK
tS
tH
tHIGH
tLOW
tEN_SDIO
tDIS_SDIO
Description
Min
Typ
SYNC to rising edge of CLK setup time
SYNC to rising edge of CLK hold time
Max
0.24
0.40
Setup time between the data and the rising edge of SCLK
Hold time between the data and the rising edge of SCLK
Period of the SCLK
Setup time between CSB and SCLK
Hold time between CSB and SCLK
SCLK pulse width high
SCLK pulse width low
Time required for the SDIO pin to switch from an input to
an output relative to the SCLK falling edge
Time required for the SDIO pin to switch from an output to
an input relative to the SCLK rising edge
Unit
ns
ns
2
2
40
2
2
10
10
10
ns
ns
ns
ns
ns
ns
ns
ns
10
ns
Timing Diagrams
tA
N–1
N+4
N+5
N
N+3
VIN
N+1
tCH
tCL
N+2
1/fS
CLK+
CLK–
tDCO
DCO+
DCO–
tSKEW
tPD
D10+AB (MSB)
D10A
D10B
D10A
D10B
D10A
D10B
D10A
D10B
D10A
D10B
D10A
D10B
D10A
D10B
D0A
D0B
D0A
D0B
D0A
D0B
D0A
D0B
D0A
D0B
D0A
D0B
D0A
D0B
D0+AB (LSB)
D0–AB (LSB)
Figure 2. Data Output Timing
CLK+
tHSYNC
08563-003
tSSYNC
SYNC
Figure 3. SYNC Input Timing Requirements
Rev. A | Page 8 of 32
08563-002
D10–AB (MSB)
AD6642
ABSOLUTE MAXIMUM RATINGS
THERMAL CHARACTERISTICS
Table 6.
Parameter
AVDD to AGND
DRVDD to AGND
VIN+x, VIN−x to AGND
CLK+, CLK− to AGND
SYNC to AGND
VCMx to AGND
CSB to AGND
SCLK to AGND
SDIO to AGND
PDWN to AGND
MODE to AGND
Digital Outputs to AGND
DCO+AB, DCO−AB to AGND
Operating Temperature Range
(Ambient)
Maximum Junction Temperature
Under Bias
Storage Temperature Range
(Ambient)
Rating
−0.3 V to +2.0 V
−0.3 V to +2.0 V
−0.3 V to AVDD + 0.2 V
−0.3 V to AVDD + 0.2 V
−0.3 V to AVDD + 0.2 V
−0.3 V to AVDD + 0.2 V
−0.3 V to DRVDD + 0.2 V
−0.3 V to DRVDD + 0.2 V
−0.3 V to DRVDD + 0.2 V
−0.3 V to DRVDD + 0.2 V
−0.3 V to DRVDD + 0.2 V
−0.3 V to DRVDD + 0.2 V
−0.3 V to DRVDD + 0.2 V
−40°C to +85°C
The values in Table 7 are per JEDEC JESD51-7 plus JEDEC
JESD25-5 for a 2S2P test board. Typical θJA is specified for a
4-layer PCB with a solid ground plane. As shown in Table 7,
airflow improves heat dissipation, which reduces θJA. In addition, metal in direct contact with the package leads from metal
traces, through holes, ground, and power planes reduces θJA.
150°C
The values in Table 8 are from simulations. The PCB is a JEDEC
multilayer board. Thermal performance for actual applications
requires careful inspection of the conditions in the application
to determine whether they are similar to those assumed in these
calculations.
−65°C to +150°C
Stresses above those listed under Absolute Maximum Ratings
may cause permanent damage to the device. This is a stress
rating only; functional operation of the device at these or any
other conditions above those indicated in the operational
section of this specification is not implied. Exposure to absolute
maximum rating conditions for extended periods may affect
device reliability.
Table 7.
Package Type
144-Ball CSP_BGA,
10 mm × 10 mm
(BC-144-1)
1
2
3
Airflow
Velocity
0 m/s
1 m/s
2.5 m/s
θJA1
26.9
24.2
23.0
θJC2
8.9
θJB3
6.6
Unit
°C/W
Per JEDEC JESD51-2 (still air) or JEDEC JESD51-6 (moving air).
Per MIL-STD 883, Method 1012.1.
Per JEDEC JESD51-8 (still air).
Table 8.
Package Type
144-Ball CSP_BGA,
10 mm × 10 mm
(BC-144-1)
ESD CAUTION
Rev. A | Page 9 of 32
Airflow
Velocity
0 m/s
1 m/s
2.5 m/s
ΨJB
14.4
14.0
13.9
ΨJT
0.23
0.50
0.53
Unit
°C/W
AD6642
1
2
3
4
5
6
7
8
9
10
11
12
A
AGND
DNC
DNC
AGND
AVDD
CLK–
CLK+
AVDD
AGND
VIN–B
VIN+B
AGND
B
AGND
AGND
DNC
AGND
AVDD
AVDD
AVDD
AVDD
AGND
VCMB
AGND
AGND
C
DNC
AGND
AGND
CSB
SDIO
SCLK
PDWN
SYNC
MODE
AGND
AGND
VIN+A
D
DNC
DNC
AGND
AVDD
AVDD
AVDD
AVDD
AVDD
AVDD
AGND
VCMA
VIN–A
E
AGND
AVDD
AVDD
AVDD
AVDD
AVDD
AVDD
AVDD
AVDD
AVDD
AVDD
AGND
F
AGND
AGND
AGND
AGND
AGND
AGND
AGND
AGND
AGND
AGND
AGND
AGND
G
DRGND
DRGND
DRGND
DRGND
DRGND
DRGND
DRGND
DRGND
DRGND
DRGND
DRGND
DRGND
H
DRVDD
DRVDD
DRVDD
DRVDD
DRVDD
DRVDD
DRVDD
DRVDD
DRVDD
DRVDD
DRVDD
DRVDD
J
DNC
DNC
DNC
DNC
DNC
DNC
D0–AB
D2–AB
D4–AB
D6–AB
D8–AB
D10–AB
K
DNC
DNC
DNC
DNC
DNC
DNC
D0+AB
D2+AB
D4+AB
D6+AB
D8+AB
D10+AB
L
DNC
DNC
DNC
DNC
DNC
DNC
D1–AB
D3–AB
D5–AB
D7–AB
D9–AB
DCO–AB
M
DNC
DNC
DNC
DNC
DNC
DNC
D1+AB
D3+AB
D5+AB
D7+AB
D9+AB
DCO+AB
08563-004
PIN CONFIGURATION AND FUNCTION DESCRIPTIONS
Figure 4. Pin Configuration (Top View)
Table 9. Pin Function Descriptions
Pin No.
A5, A8, B5, B6, B7, B8,
D4, D5, D6, D7, D8,
D9, E2, E3, E4, E5, E6,
E7, E8, E9, E10, E11
A1, A4, A9, A12, B1,
B2, B4, B9, B11, B12,
C2, C3, C10, C11, D3,
D10, E1, E12, F1, F2,
F3, F4, F5, F6, F7, F8,
F9, F10, F11, F12
H1, H2, H3, H4, H5,
H6, H7, H8, H9, H10,
H11, H12
G1, G2, G3, G4, G5,
G6, G7, G8, G9, G10,
G11, G12
A7
A6
C12
D12
D11
A11
A10
B10
A2, A3, B3, C1, D1,
D2, J1 to J6, K1 to K6,
L1 to L6, M1 to M6
K7
J7
M7
L7
Mnemonic
AVDD
Type
Supply
Description
Analog Power Supply (1.8 V Nominal)
AGND
Ground
Analog Ground
DRVDD
Supply
Digital Output Driver Supply (1.8 V Nominal)
DRGND
Ground
Digital Output Driver Ground
CLK+
CLK−
VIN+A
VIN−A
VCMA
VIN+B
VIN−B
VCMB
DNC
Input
Input
Input
Input
Output
Input
Input
Output
ADC Clock Input—True
ADC Clock Input—Complement
Differential Analog Input Pin (+) for Channel A
Differential Analog Input Pin (−) for Channel A
Common-Mode Level Bias Output for Analog Input Channel A
Differential Analog Input Pin (+) for Channel B
Differential Analog Input Pin (−) for Channel B
Common-Mode Level Bias Output for Analog Input Channel B
Do Not Connect
D0+AB
D0−AB
D1+AB
D1−AB
Output
Output
Output
Output
Channel A and Channel B LVDS Output Data 0—True
Channel A and Channel B LVDS Output Data 0—Complement
Channel A and Channel B LVDS Output Data 1—True
Channel A and Channel B LVDS Output Data 1—Complement
Rev. A | Page 10 of 32
AD6642
Pin No.
K8
J8
M8
L8
K9
J9
M9
L9
K10
J10
M10
L10
K11
J11
M11
L11
K12
J12
M12
L12
C9
C8
C7
C6
C5
C4
Mnemonic
D2+AB
D2−AB
D3+AB
D3−AB
D4+AB
D4−AB
D5+AB
D5−AB
D6+AB
D6−AB
D7+AB
D7−AB
D8+AB
D8−AB
D9+AB
D9−AB
D10+AB
D10−AB
DCO+AB
DCO−AB
MODE
SYNC
PDWN
SCLK
SDIO
CSB
Type
Output
Output
Output
Output
Output
Output
Output
Output
Output
Output
Output
Output
Output
Output
Output
Output
Output
Output
Output
Output
Input
Input
Input
Input
Input/Output
Input
Description
Channel A and Channel B LVDS Output Data 2—True
Channel A and Channel B LVDS Output Data 2—Complement
Channel A and Channel B LVDS Output Data 3—True
Channel A and Channel B LVDS Output Data 3—Complement
Channel A and Channel B LVDS Output Data 4—True
Channel A and Channel B LVDS Output Data 4—Complement
Channel A and Channel B LVDS Output Data 5—True
Channel A and Channel B LVDS Output Data 5—Complement
Channel A and Channel B LVDS Output Data 6—True
Channel A and Channel B LVDS Output Data 6—Complement
Channel A and Channel B LVDS Output Data 7—True
Channel A and Channel B LVDS Output Data 7—Complement
Channel A and Channel B LVDS Output Data 8—True
Channel A and Channel B LVDS Output Data 8—Complement
Channel A and Channel B LVDS Output Data 9—True
Channel A and Channel B LVDS Output Data 9—Complement
Channel A and Channel B LVDS Output Data 10—True
Channel A and Channel B LVDS Output Data 10—Complement
Data Clock LVDS Output for Channel A and Channel B—True
Data Clock LVDS Output for Channel A and Channel B—Complement
Mode Select Pin (Logic Low Enables NSR; Logic High Disables NSR)
Digital Synchronization Pin
Power-Down Input (Active High)
SPI Clock
SPI Data
SPI Chip Select (Active Low)
Rev. A | Page 11 of 32
AD6642
TYPICAL PERFORMANCE CHARACTERISTICS
AVDD = 1.8 V, DRVDD = 1.8 V, sample rate = 185 MSPS, 1.75 V p-p differential input, VIN = −1.0 dBFS, 32k sample, TA = 25°C, unless
otherwise noted.
0
0
fS = 185MSPS
fIN = 30.3MHz @ –1dBFS
SNR = 65.7dB (66.7dBFS)
SFDR = 89.7dBc
–40
–60
SECOND
HARMONIC
–80
THIRD
HARMONIC
SNR = 64.8dB (65.8dBFS)
SFDR = 80dBc
–40
–60
SECOND
HARMONIC
–80
–100
10
20
30
40
50
60
FREQUENCY (MHz)
70
80
90
–120
08563-005
0
0
Figure 5. Single-Tone FFT with fIN = 30.3 MHz
SNR = 65.4dB (66.4dBFS)
SFDR = 86dBc
AMPLITUDE (dBFS)
40
50
60
FREQUENCY (MHz)
70
80
90
–40
–60
THIRD
HARMONIC
–80
fS = 185MSPS
fIN = 230.3MHz @ –1dBFS
SNR = 64.6dB (65.6dBFS)
SFDR = 86.1dBc
SECOND
HARMONIC
–40
–60
THIRD
HARMONIC
–80
SECOND
HARMONIC
10
20
30
40
50
60
FREQUENCY (MHz)
70
80
90
–120
08563-006
0
0
Figure 6. Single-Tone FFT with fIN = 70.3 MHz
10
20
30
40
50
60
FREQUENCY (MHz)
70
80
90
08563-109
–100
Figure 9. Single-Tone FFT with fIN = 230.3 MHz
0
0
fS = 185MSPS
fIN = 140.1MHz @ –1dBFS
AMPLITUDE (dBFS)
SNR = 65.3dB (66.3dBFS)
SFDR = 88dBc
–20
–40
–60
SECOND
HARMONIC
THIRD
HARMONIC
–80
fS = 185MSPS
fIN = 140.1MHz @ –1.6dBFS
NSR 22% BW MODE, TW = 28
SNR = 73dB (74.6dBFS) (IN-BAND)
SFDR = 89.7dBc (IN-BAND)
–20
–100
–40
SECOND
HARMONIC
–60
THIRD
HARMONIC
–80
–100
0
10
20
30
40
50
60
FREQUENCY (MHz)
70
80
90
08563-007
–120
Figure 7. Single-Tone FFT with fIN = 140.1 MHz
–140
0
10
20
30
40
50
60
FREQUENCY (MHz)
70
80
90
Figure 10. Single-Tone FFT with fIN = 140.1 MHz, NSR Enabled
in 22% BW Mode with Tuning Word = 28
Rev. A | Page 12 of 32
08563-110
AMPLITUDE (dBFS)
30
–20
–100
AMPLITUDE (dBFS)
20
0
fS = 185MSPS
fIN = 70.3MHz @ –1dBFS
–20
–120
10
Figure 8. Single-Tone FFT with fIN = 200.3 MHz
0
–120
THIRD
HARMONIC
08563-108
–100
–120
fS = 185MSPS
fIN = 200.3MHz @ –1dBFS
–20
AMPLITUDE (dBFS)
AMPLITUDE (dBFS)
–20
AD6642
95
0
fS = 185MSPS
fIN = 230.3MHz @ –1.6dBFS
90
NSR 33% BW MODE, TW = 17
SNR = 69.3dB (71dBFS) (IN-BAND)
SFDR = 85.4dBc (IN-BAND)
–40
SNR/SFDR (dBFS/dBc)
AMPLITUDE (dBFS)
–20
SECOND
HARMONIC
–60
THIRD
HARMONIC
–80
–100
85
SFDR (dBc)
80
75
70
SNR (dBFS)
0
10
20
30
40
50
60
FREQUENCY (MHz)
70
80
90
60
08563-111
–140
95
90
90
80
160
210
INPUT FREQUENCY (MHz)
260
300
SFDR (dBc)
60
SNR (dBc)
SFDR (dBc)
SNR (dBFS)
SFDR (dBFS)
50
40
30
80
75
70
0
08563-112
–5
–10
–15
–20
–25
–30
–35
–40
–45
–50
–55
50
–60
0
–65
55
–70
10
–75
60
–80
20
–85
SNR (dBFS)
65
30
Figure 12. Single-Tone SNR/SFDR vs. Input Amplitude (AIN)
with fIN = 70.3 MHz
50
70
90
110 130 150 170 190
SAMPLE RATE (MSPS)
210
230
250
08563-015
SNR/SFDR (dBFS/dBc)
85
70
INPUT AMPLITUDE (dBFS)
Figure 15. Single-Tone SNR/SFDR vs. Sample Rate (fS)
with fIN = 70.1 MHz
0
95
90
fS = 185MSPS
fIN1 = 169.1MHz @ –7dBFS
fIN2 = 172.1MHz @ –7dBFS
–20
SFDR = 81.8dBc
AMPLITUDE (dBFS)
85
SFDR (dBc)
80
75
70
–40
–60
–80
SNR (dBFS)
60
60
110
160
210
INPUT FREQUENCY (MHz)
260
300
–120
0
10
20
30
40
50
60
FREQUENCY (MHz)
70
80
90
08563-016
–100
65
08563-013
SNR/SFDR (dBFS/dBc)
110
Figure 14. Single-Tone SNR/SFDR vs. Input Frequency (fIN)
with 2.0 V p-p Full Scale
100
–90
SNR/SFDR (dBc AND dBFS)
Figure 11. Single-Tone FFT with fIN = 230.3 MHz, NSR Enabled
in 33% BW Mode with Tuning Word = 17
60
08563-114
65
–120
Figure 16. Two-Tone FFT with fIN1 = 169.1 MHz and fIN2 = 172.1 MHz
Figure 13. Single-Tone SNR/SFDR vs. Input Frequency (fIN)
with 1.75 V p-p Full Scale
Rev. A | Page 13 of 32
AD6642
0
0.20
0.15
0.10
SFDR (dBc)
–40
DNL ERROR (LSB)
SFDR/IMD3 (dBc AND dBFS)
–20
IMD3 (dBc)
–60
–80
SFDR (dBFS)
0.05
0
–0.05
–0.10
–100
–0.15
–78
–66
–54
–42
–30
INPUT AMPLITUDE (dBFS)
–18
–6
–0.20
08563-017
–120
–90
0
500
Figure 17. Two-Tone SFDR/IMD3 vs. Input Amplitude (AIN)
with fIN1 = 169.1 MHz and fIN2 = 172.1 MHz
1000
OUTPUT CODE
1500
2000
Figure 20. DNL with fIN = 30.3 MHz
1,200,000
69
68
1,000,000
800,000
66
SNR (dBFS)
NUMBER OF HITS
67
600,000
65
64
63
400,000
62
200,000
N–3
N–2
N–1
N
N+1
OUTPUT CODE
N+2
N+3
1.0
0.8
0.4
0.2
0
–0.2
–0.4
–0.6
–0.8
–1.0
1000
OUTPUT CODE
1500
2000
08563-019
INL ERROR (LSB)
0.6
500
30
35
40
45
50
55
60
65
DUTY CYCLE (%)
Figure 21. SNR vs. Duty Cycle with fIN = 10.3 MHz
Figure 18. Grounded Input Histogram
0
60
Figure 19. INL with fIN = 30.3 MHz
Rev. A | Page 14 of 32
70
08563-021
0
08563-018
61
08563-020
IMD3 (dBFS)
AD6642
EQUIVALENT CIRCUITS
AVDD
350Ω
SCLK
OR
PDWN
30kΩ
08563-008
08563-012
VIN
Figure 26. Equivalent SCLK and PDWN Input Circuit
Figure 22. Equivalent Analog Input Circuit
AVDD
AVDD
AVDD
30kΩ
AVDD
0.9V
CLK–
350Ω
08563-009
CLK+
15kΩ
08563-014
15kΩ
CSB
OR
MODE
Figure 27. Equivalent CSB and MODE Input Circuit
Figure 23. Equivalent Clock Input Circuit
DRVDD
DRVDD
V+
V–
DATAOUT+
V–
SDIO
V+
350Ω
08563-010
30kΩ
Figure 28. Equivalent SDIO Circuit
Figure 24. Equivalent LVDS Output Circuit
AVDD
AVDD
SYNC
0.9V
08563-025
16kΩ
0.9V
Figure 25. Equivalent SYNC Input Circuit
Rev. A | Page 15 of 32
08563-011
DATAOUT–
AD6642
THEORY OF OPERATION
The AD6642 architecture consists of dual front-end sampleand-hold circuits, followed by pipelined, switched-capacitor
ADCs. The quantized outputs from each stage are combined
into a final 14-bit result in the digital correction logic.
Alternately, the 14-bit result can be processed through the noise
shaping requantizer (NSR) block before it is sent to the digital
correc-tion logic.
The pipelined architecture permits the first stage to operate on
a new input sample and the remaining stages to operate on the
preceding samples. Sampling occurs on the rising edge of the clock.
Each stage of the pipeline, excluding the last, consists of a low
resolution flash ADC connected to a switched-capacitor digitalto-analog converter (DAC) and an interstage residue amplifier
(MDAC). The residue amplifier magnifies the difference between
the reconstructed DAC output and the flash input for the next
stage in the pipeline. One bit of redundancy is used in each stage
to facilitate digital correction of flash errors. The last stage
simply consists of a flash ADC.
The input stage of each channel contains a differential sampling
circuit that can be ac- or dc-coupled in differential or singleended modes. The output staging block aligns the data, corrects
errors, and passes the data to the output buffers. The output
buffers are powered from a separate supply, allowing adjustment of the output drive current. During power-down, the
output buffers go into a high impedance state.
The AD6642 dual IF receiver can simultaneously digitize two
channels, making it ideal for diversity reception and digital predistortion (DPD) observation paths in telecommunication
systems.
Synchronization capability is provided to allow synchronized
timing between multiple channels or multiple devices.
Programming and control of the AD6642 are accomplished
using a 3-wire SPI-compatible serial interface.
ANALOG INPUT CONSIDERATIONS
The analog input to the AD6642 is a differential switchedcapacitor circuit that has been designed for optimum
performance while processing a differential input signal.
The clock signal alternatively switches the input between sample
mode and hold mode (see Figure 29). When the input is switched
to sample mode, the signal source must be capable of charging
the sample capacitors and settling within 1/2 of a clock cycle.
A small resistor in series with each input can help reduce the
peak transient current required from the output stage of the
driving source. A shunt capacitor can be placed across the
inputs to provide dynamic charging currents. This passive
network creates a low-pass filter at the ADC input; therefore,
the precise values are dependent on the application.
In intermediate frequency (IF) undersampling applications,
any shunt capacitors should be reduced. In combination with
the driving source impedance, the shunt capacitors limit the
input bandwidth. For more information on this subject, see
Application Note AN-742, Frequency Domain Response of
Switched-Capacitor ADCs; Application Note AN-827, A Resonant
Approach to Interfacing Amplifiers to Switched-Capacitor ADCs;
and the Analog Dialogue article, “Transformer-Coupled Front-End
for Wideband A/D Converters” (see www.analog.com).
BIAS
S
S
CFB
CS
VIN+
CPAR1
CPAR2
H
S
S
CS
VIN–
CPAR1
CPAR2
S
S
CFB
BIAS
08563-037
ADC ARCHITECTURE
Figure 29. Switched-Capacitor Input
For best dynamic performance, the source impedances driving
the VIN+ and VIN− pins should be matched.
An internal differential reference buffer creates positive and
negative reference voltages that define the input span of the ADC
core. The span of the ADC core is set by this buffer to 2 × VREF.
Input Common Mode
The analog inputs of the AD6642 are not internally dc biased.
In ac-coupled applications, the user must provide this bias
externally. An on-board common-mode voltage reference is
included in the design and is available from the VCMx pins.
Optimum performance is achieved when the common-mode
voltage of the analog input is set by the VCMx pin voltage
(typically 0.5 × AVDD). The VCMx pins must be decoupled
to ground by a 0.1 μF capacitor.
Rev. A | Page 16 of 32
AD6642
Differential Input Configurations
The signal characteristics must be considered when selecting
a transformer. Most RF transformers saturate at frequencies
below a few megahertz (MHz). Excessive signal power can also
cause core saturation, which leads to distortion.
Optimum performance is achieved when driving the AD6642
in a differential input configuration. For baseband applications,
the AD8138, ADA4937-2, and ADA4938-2 differential drivers
provide excellent performance and a flexible interface to the ADC.
At input frequencies in the second Nyquist zone and above, the
noise performance of most amplifiers is not adequate to achieve
the true SNR performance of the AD6642. For applications in
which SNR is a key parameter, differential double balun coupling
is the recommended input configuration (see Figure 32). In this
configuration, the input is ac-coupled and the CML is provided to
each input through a 33 Ω resistor. These resistors compensate
for losses in the input baluns to provide a 50 Ω impedance to
the driver.
The output common-mode voltage of the ADA4938-2 is easily
set with the VCMx pin of the AD6642 (see Figure 30), and the
driver can be configured in a Sallen-Key filter topology to
provide band limiting of the input signal.
15pF
200Ω
33Ω
90Ω
15Ω
VIN–
AVDD
5pF
ADA4938-2
0.1µF
33Ω
15Ω
VCM
VIN+
120Ω
08563-039
15pF
200Ω
In the double balun and transformer configurations, the value
of the input capacitors and resistors is dependent on the input
frequency and source impedance and may need to be reduced
or removed. Table 10 lists recommended values to set the RC
network. At higher input frequencies, good performance can be
achieved by using a ferrite bead in series with a resistor and
removing the capacitors. However, these values are dependent
on the input signal and should be used only as a starting guide.
ADC
Figure 30. Differential Input Configuration Using the ADA4938-2
For baseband applications where SNR is a key parameter,
differential transformer coupling is the recommended input
configuration. An example is shown in Figure 31. To bias the
analog input, the VCM voltage can be connected to the center
tap of the secondary winding of the transformer.
Table 10. Example RC Network
Frequency
Range
(MHz)
0 to 100
100 to 200
100 to 300
C2
R2
VIN+
R1
C1
ADC
R2
R1
0.1µF
1
VCM
VIN–
C2
C1 Differential
5 pF
5 pF
Remove
Figure 31. Differential Transformer-Coupled Configuration
C2
2V p-p
R1
R2
VIN+
33Ω
PA
S
S
P
0.1µF
33Ω
C1
0.1µF
R1
ADC
R2
VIN–
VCM
C2
Figure 32. Differential Double Balun Input Configuration
VCC
ANALOG INPUT
0.1µF 0Ω
16
1
8, 13
11
0.1µF
0.1µF
RD
RG
3
ANALOG INPUT
0.1µF 0Ω
VIN+
C
AD8352
10
4
5
R
200Ω
2
CD
C2 Shunt
(Each)
15 pF
10 pF
Remove
In this configuration, R1 is a ferrite bead with a value of 10 Ω @ 100 MHz.
0.1µF
0.1µF
R2 Series
(Each)
15 Ω
10 Ω
66 Ω
An alternative to using a transformer-coupled input at frequencies
in the second Nyquist zone is to use the AD8352 differential driver
(see Figure 33). For more information, see the AD8352 data sheet.
08563-041
49.9Ω
08563-040
2V p-p
R1 Series
(Each)
33 Ω
10 Ω
10 Ω1
0.1µF
200Ω
R
14
0.1µF
0.1µF
Figure 33. Differential Input Configuration Using the AD8352
Rev. A | Page 17 of 32
ADC
VIN–
VCM
08563-042
76.8Ω
VIN
AD6642
ANALOG
INPUT
XFMR 1:4 Z
ETC4-1T-7
0.1µF
33Ω
0.1µF
121Ω
0.1µF
0.1µF
121Ω
3.0kΩ
AIN–
33Ω
0.1µF
3.0pF
ADC
INTERNAL
INPUT Z
VCM
08563-116
431nH
INPUT
Z = 50Ω
Figure 34. 1:4 Transformer Passive Configuration
1000pF
180nH 220nH
1µH
165Ω
VPOS
AD8376
301Ω
5.1pF
1nF
1µH
1000pF
3.9pF
165Ω
15pF
VCM
3.0kΩ║3.0pF
1nF
AD6642
68nH
180nH 220nH
08563-115
NOTES
1. ALL INDUCTORS ARE COILCRAFT 0603CS COMPONENTS
WITH THE EXCEPTION OF THE 1µH CHOKE INDUCTORS (0603LS).
Figure 35. Active Front-End Configuration Using the AD8376
For the popular IF band of 140 MHz, Figure 34 shows an
example of a 1:4 transformer passive configuration where a
differential inductor is used to resonate with the internal input
capacitance of the AD6642. This configuration realizes excellent
noise and distortion performance. Figure 35 shows an example
of an active front-end configuration using the AD8376 dual
VGA. This configuration is recommended when signal gain
is required.
CLOCK INPUT CONSIDERATIONS
For optimum performance, the AD6642 sample clock inputs,
CLK+ and CLK−, should be clocked with a differential signal.
The signal is typically ac-coupled into the CLK+ and CLK− pins
via a transformer or capacitors. These pins are biased internally
(see Figure 36) and require no external bias.
Figure 37 and Figure 38 show two preferred methods for clocking the AD6642 (at clock rates up to 625 MHz). A low jitter clock
source is converted from a single-ended signal to a differential
signal using either an RF balun or an RF transformer.
The RF balun configuration is recommended for clock frequencies
between 125 MHz and 625 MHz, and the RF transformer configuration is recommended for clock frequencies from 10 MHz to
200 MHz. The back-to-back Schottky diodes across the transformer/balun secondary limit clock excursions into the AD6642
to approximately 0.8 V p-p differential.
This limit helps to prevent the large voltage swings of the clock
from feeding through to other portions of the AD6642 while
preserving the fast rise and fall times of the signal that are
critical to a low jitter performance.
AVDD
ADT1-1WT, 1:1Z
0.1µF
XFMR
0.1µF
1.2V
CLOCK
INPUT
CLK+
CLK+
100Ω
50Ω
CLK–
ADC
0.1µF
CLK–
SCHOTTKY
DIODES:
HSMS2822
0.1µF
08563-056
2pF
08563-055
2pF
Figure 37. Transformer-Coupled Differential Clock (Up to 200 MHz)
Figure 36. Equivalent Clock Input Circuit
1nF
The AD6642 has a very flexible clock input structure. The clock
input can be a CMOS, LVDS, LVPECL, or sine wave signal.
Regardless of the type of signal being used, clock source jitter is
of the most concern (see the Jitter Considerations section).
CLOCK
INPUT
0.1µF
CLK+
50Ω
ADC
0.1µF
1nF
CLK–
SCHOTTKY
DIODES:
HSMS2822
Figure 38. Balun-Coupled Differential Clock (Up to 625 MHz)
Rev. A | Page 18 of 32
08563-057
Clock Input Options
AD6642
If a low jitter clock source is not available, another option is to
ac-couple a differential PECL signal to the sample clock input
pins, as shown in Figure 39. The AD9510/AD9511/AD9512/
AD9513/AD9514/AD9515/AD9516 clock drivers offer excellent
jitter performance.
VCC
CLOCK
INPUT
0.1µF
50Ω 1
1kΩ
AD951x
CMOS DRIVER
OPTIONAL 0.1µF
100Ω
1kΩ
CLK+
ADC
CLK–
0.1µF
CLOCK
INPUT
Figure 42. Single-Ended 3.3 V CMOS Input Clock (Up to 200 MHz)
CLK+
0.1µF
50kΩ
50kΩ
AD951x
PECL DRIVER
100Ω
0.1µF
240Ω
Input Clock Divider
ADC
CLK–
08563-058
CLOCK
INPUT
150Ω RESISTOR IS OPTIONAL.
0.1µF
08563-061
0.1µF
240Ω
Figure 39. Differential PECL Sample Clock (Up to 625 MHz)
A third option is to ac-couple a differential LVDS signal to the
sample clock input pins, as shown in Figure 40. The AD9510/
AD9511/AD9512/AD9513/AD9514/AD9515/AD9516 clock
drivers offer excellent jitter performance.
The AD6642 contains an input clock divider with the ability to
divide the input clock by integer values from 1 to 8.
The AD6642 clock divider can be synchronized using the
external SYNC input. Bit 1 of Register 0x3A enables the clock
divider to be resynchronized on every SYNC signal. A valid
SYNC causes the clock divider to reset to its initial state. This
synchronization feature allows multiple parts to have their clock
dividers aligned to guarantee simultaneous input sampling.
Clock Duty Cycle
0.1µF
CLOCK
INPUT
CLK+
0.1µF
50kΩ
AD951x
LVDS DRIVER
100Ω
0.1µF
ADC
CLK–
08563-059
CLOCK
INPUT
0.1µF
50kΩ
Figure 40. Differential LVDS Sample Clock (Up to 625 MHz)
In some applications, it may be acceptable to drive the sample
clock inputs with a single-ended CMOS signal. In such applications, the CLK+ pin should be driven directly from a CMOS
gate, and the CLK− pin should be bypassed to ground with a
0.1 μF capacitor in parallel with a 39 kΩ resistor (see Figure 41).
VCC
0.1µF
CLOCK
INPUT
50Ω1
1kΩ
AD951x
CMOS DRIVER
OPTIONAL
0.1µF
100Ω
1kΩ
CLK+
ADC
CLK–
150Ω
39kΩ
08563-060
0.1µF
RESISTOR IS OPTIONAL.
Figure 41. Single-Ended 1.8 V CMOS Input Clock (Up to 200 MHz)
CLK+ can be driven directly from a CMOS gate. Although
the CLK+ input circuit supply is AVDD (1.8 V), this input is
designed to withstand input voltages of up to 3.6 V, making the
selection of the drive logic voltage very flexible (see Figure 42).
Typical high speed ADCs use both clock edges to generate
a variety of internal timing signals and, as a result, may be
sensitive to clock duty cycle. Commonly, a ±5% tolerance is
required on the clock duty cycle to maintain dynamic
performance characteristics.
The AD6642 contains a duty cycle stabilizer (DCS) that retimes
the nonsampling (falling) edge, providing an internal clock signal
with a nominal 50% duty cycle. This allows the user to provide a
wide range of clock input duty cycles without affecting the performance of the AD6642. Noise and distortion performance are
nearly flat for a wide range of duty cycles with the DCS enabled.
Jitter in the rising edge of the input is still of paramount concern
and is not easily reduced by the internal stabilization circuit. The
duty cycle control loop does not function for clock rates less
than 40 MHz nominally. The loop has a time constant associated with it that must be considered in applications in which
the clock rate can change dynamically. A wait time of 1.5 μs to
5 μs is required after a dynamic clock frequency increase or
decrease before the DCS loop is relocked to the input signal.
During the time period that the loop is not locked, the DCS
loop is bypassed, and internal device timing is dependent on the
duty cycle of the input clock signal.
Rev. A | Page 19 of 32
AD6642
Jitter Considerations
1.5
High speed, high resolution ADCs are sensitive to the quality of
the clock input. The degradation in SNR from the low frequency
SNR (SNRLF) at a given input frequency (fIN) due to jitter (tJRMS)
can be calculated by
1.3
0.30
1.4
0.20
1.0
0.9
0.8
0.15
0.7
TOTAL POWER
0.6
0.10
0.5
0.4
IDRVDD
0.3
0.05
0.2
80
CURRENT (A)
In the equation, the rms aperture jitter represents the clock
input jitter specification. IF undersampling applications are
particularly sensitive to jitter, as illustrated in Figure 43.
0.25
1.1
TOTAL POWER (W)
SNRHF = −10log[(2π × fIN × tJRMS)2 + 10(−SNRLF/10) ]
IAVDD
1.2
0.1
0
SAMPLING FREQUENCY (MSPS)
Figure 44. Power and Current vs. Sampling Frequency
0.20ps
By asserting PDWN (either through the SPI port or by asserting
the PDWN pin high), the AD6642 is placed in power-down
mode. In this state, the ADC typically dissipates 4.5 mW.
During power-down, the output drivers are placed in a high
impedance state. Asserting the PDWN pin low returns the
AD6642 to its normal operating mode. Note that PDWN is
referenced to the digital output driver supply (DRVDD) and
should not exceed that supply voltage.
65
60
0.50ps
55
1.00ps
50
1.50ps
1
10
100
INPUT FREQUENCY (MHz)
1k
08563-053
SNR (dBc)
70
08563-142
200
190
180
170
160
150
140
130
120
110
90
100
80
70
60
50
30
0
40
0.05ps
75
Figure 43. SNR vs. Input Frequency and Jitter
The clock input should be treated as an analog signal in cases
in which aperture jitter may affect the dynamic range of the
AD6642. Power supplies for clock drivers should be separated
from the ADC output driver supplies to avoid modulating the
clock signal with digital noise. Low jitter, crystal-controlled
oscillators make the best clock sources. If the clock is generated
from another type of source (by gating, dividing, or another
method), it should be retimed by the original clock at the last
step. Refer to Application Note AN-501 and Application Note
AN-756 for more information about jitter performance as it
relates to ADCs (see www.analog.com).
Low power dissipation in power-down mode is achieved by
shutting down the reference, reference buffer, biasing networks,
and clock. Internal capacitors are discharged when entering
power-down mode and must be recharged when returning to
normal operation. As a result, wake-up time is related to the
time spent in power-down mode; shorter power-down cycles
result in proportionally shorter wake-up times.
When using the SPI port interface, the user can place the ADC
in power-down mode or standby mode. Standby mode allows
the user to keep the internal reference circuitry powered when
faster wake-up times are required. See the Memory Map
Register Descriptions section for more details.
POWER DISSIPATION AND STANDBY MODE
CHANNEL/CHIP SYNCHRONIZATION
The power dissipated by the AD6642 is proportional to its clock
rate (see Figure 44). The digital power dissipation does not vary
significantly because it is determined primarily by the DRVDD
supply and the bias current of the LVDS drivers.
The AD6642 has a SYNC input that offers the user flexible synchronization options for synchronizing the clock divider. The
clock divider sync feature is useful for guaranteeing synchronized
sample clocks across multiple ADCs.
Reducing the capacitive load presented to the output drivers can
minimize digital power consumption. The data in Figure 44 was
taken using the same operating conditions as those used in the
Typical Performance Characteristics section, with a 5 pF load
on each output driver.
The SYNC input is internally synchronized to the sample clock;
however, to ensure that there is no timing uncertainty between
multiple parts, the SYNC input signal should be externally synchronized to the input clock signal, meeting the setup and hold
times shown in Table 5. The SYNC input should be driven using
a single-ended CMOS-type signal.
Rev. A | Page 20 of 32
AD6642
DIGITAL OUTPUTS
The AD6642 output drivers are configured to interface with
LVDS outputs using a DRVDD supply voltage of 1.8 V. The
output bits are DDR LVDS as shown in Figure 2. Applications
that require the ADC to drive large capacitive loads or large
fanouts may require external buffers or latches.
As described in Application Note AN-877, Interfacing to High
Speed ADCs via SPI, the data format can be selected for offset
binary or twos complement when using the SPI control.
TIMING
The AD6642 provides latched data with a latency of nine clock
cycles. Data outputs are available one propagation delay (tPD)
after the rising edge of the clock signal.
The length of the output data lines and the loads placed on
them should be minimized to reduce transients within the
AD6642. These transients can degrade converter dynamic
performance.
The lowest typical conversion rate of the AD6642 is 40 MSPS.
At clock rates below 40 MSPS, dynamic performance can degrade.
Data Clock Output (DCO)
The AD6642 provides a data clock output (DCO) signal
intended for capturing the data in an external register. The
output data for Channel A is valid when DCO is high; the
output data for Channel B is valid when DCO is low. See
Figure 2 for a graphical timing description.
Table 11. Output Data Format
Input (V)
VIN+ − VIN−
VIN+ − VIN−
VIN+ − VIN−
VIN+ − VIN−
VIN+ − VIN−
Condition (V)
< −VREF − 0.5 LSB
= −VREF
=0
= +VREF − 1.0 LSB
> +VREF − 0.5 LSB
Offset Binary Output Mode
0000 0000 0000 0000
0000 0000 0000 0000
1000 0000 0000 0000
1111 1111 1111 1111
1111 1111 1111 1111
Rev. A | Page 21 of 32
Twos Complement Mode
1000 0000 0000 0000
1000 0000 0000 0000
0000 0000 0000 0000
0111 1111 1111 1111
0111 1111 1111 1111
AD6642
NOISE SHAPING REQUANTIZER (NSR)
fS = 184.32MSPS
fIN = 140MHz @ –1.6dBFS
NSR 22% BW MODE, TW = 28
SNR = 73.4dB (75dBFS) (IN-BAND)
SFDR = 93dBc (IN-BAND)
–20
Two different bandwidth modes are provided; the mode can be
selected from the SPI port. In each of the two modes, the center
frequency of the band can be tuned such that IFs can be placed
anywhere in the Nyquist band.
–40
–60
–80
–100
–120
0
10
20
30
40
50
60
70
80
90
FREQUENCY (MHz)
22% BW MODE (>40 MHZ @ 184.32 MSPS)
Figure 46. 22% BW Mode, Tuning Word = 28 (fS/4 Tuning)
0
fS = 184.32MSPS
fIN = 140MHz @ –1.6dBFS
NSR 22% BW MODE, TW = 41
SNR = 73.4dB (75dBFS) (IN-BAND)
SFDR = 94dBc (IN-BAND)
–20
AMPLITUDE (dBFS)
The first bandwidth mode offers excellent noise performance
over 22% of the ADC sample rate (44% of the Nyquist band)
and can be centered by setting the NSR mode bits in the NSR
control register (Address 0x3C) to 000. In this mode, the useful
frequency range can be set using the 6-bit tuning word in the
NSR tuning register (Address 0x3E). There are 57 possible
tuning words (TW); each step is 0.5% of the ADC sample rate.
The following three equations describe the left band edge (f0),
the channel center (fCENTER), and the right band edge (f1),
respectively.
08563-045
The NSR feature can be independently controlled per channel
via the SPI or the MODE pin.
0
AMPLITUDE (dBFS)
The AD6642 features a noise shaping requantizer (NSR) to
allow higher than 11-bit SNR to be maintained in a subset of
the Nyquist band. The harmonic performance of the receiver
is unaffected by the NSR feature. When enabled, the NSR
contributes an additional 0.6 dB of loss to the input signal, such
that a 0 dBFS input is reduced to −0.6 dBFS at the output pins.
f0 = fADC × .005 × TW
–40
–60
–80
–100
–120
f1 = f0 + 0.22 × fADC
20
30
40
fS = 184.32MSPS
fIN = 140MHz @ –1.6dBFS
NSR 22% BW MODE, TW = 13
SNR = 73.4dB (75dBFS) (IN-BAND)
SFDR = 92.6dBc (IN-BAND)
–20
–40
–60
–80
30
40
50
60
70
FREQUENCY (MHz)
80
90
08563-044
20
70
80
90
33% BW MODE (>60 MHZ @ 184.32 MSPS)
f0 = fADC × .005 × TW
10
60
Figure 47. 22% BW Mode, Tuning Word = 41
–100
0
50
The second bandwidth mode offers excellent noise performance
over 33% of the ADC sample rate (66% of the Nyquist band)
and can be centered by setting the NSR mode bits in the NSR
control register (Address 0x3C) to 001. In this mode, the useful
frequency range can be set using the 6-bit tuning word in the
NSR tuning register (Address 0x3E). There are 34 possible
tuning words (TW); each step is 0.5% of the ADC sample rate.
The following three equations describe the left band edge (f0),
the channel center (fCENTER), and the right band edge (f1),
respectively.
0
AMPLITUDE (dBFS)
10
FREQUENCY (MHz)
Figure 45 to Figure 47 show the typical spectrum that can be
expected from the AD6642 in the 22% BW mode for three
different tuning words.
–120
0
08563-046
fCENTER = f0 + 0.11 × fADC
Figure 45. 22% BW Mode, Tuning Word = 13
Rev. A | Page 22 of 32
fCENTER = f0 + 0.165 × fADC
f1 = f0 + 0.33 × fADC
AD6642
0
Figure 48 to Figure 50 show the typical spectrum that can be
expected from the AD6642 in the 33% BW mode for three
different tuning words.
fS = 184.32MSPS
fIN = 140MHz @ –1.6dBFS
NSR 33% BW MODE, TW = 27
SNR = 71dB (72.5dBFS) (IN-BAND)
SFDR = 93dBc (IN-BAND)
–20
AMPLITUDE (dBFS)
0
fS = 184.32MSPS
fIN = 140MHz @ –1.6dBFS
NSR 33% BW MODE, TW = 5
SNR = 71dB (72.5dBFS) (IN-BAND)
SFDR = 92.5dBc (IN-BAND)
–40
–60
–80
–60
–100
–80
–120
0
10
20
30
40
50
60
70
FREQUENCY (MHz)
–100
80
90
08563-049
AMPLITUDE (dBFS)
–20
–40
–120
0
10
20
30
40
50
60
70
80
90
FREQUENCY (MHz)
08563-047
Figure 50. 33% BW Mode, Tuning Word = 27
Figure 48. 33% BW Mode, Tuning Word = 5
0
fS = 184.32MSPS
fIN = 140MHz @ –1.6dBFS
NSR 33% BW MODE, TW = 17
SNR = 71.2dB (72.8dBFS) (IN-BAND)
SFDR = 93.7dBc (IN-BAND)
–40
–60
The MODE pin input allows convenient control of the NSR
feature. A logic low enables NSR mode and a logic high sets the
receiver to straight 11-bit mode with NSR disabled. By default,
the MODE pin is pulled high internally to disable the NSR.
Each channel can be individually configured to ignore the
MODE pin state by writing to Bit 4 of the NSR control register
at Address 0x3C. Use of the NSR control register in conjunction
with the MODE pin allows for very flexible control of the NSR
feature on a per-channel basis.
–80
–100
–120
0
10
20
30
40
50
60
70
80
FREQUENCY (MHz)
90
08563-048
AMPLITUDE (dBFS)
–20
MODE PIN
Figure 49. 33% BW Mode, Tuning Word = 17 (fS/4 Tuning)
Rev. A | Page 23 of 32
AD6642
BUILT-IN SELF-TEST (BIST) AND OUTPUT TEST
The AD6642 includes built-in test features designed to verify
the integrity of each channel and to facilitate board-level debugging. A BIST (built-in self-test) feature is included that verifies
the integrity of the digital datapath of the AD6642. Various
output test options are also provided to place predictable values
on the outputs of the AD6642.
The outputs are not disconnected during this test, so the PN
sequence can be observed as it runs. The PN sequence can be
continued from its last value or reset from the beginning, based
on the value programmed in Register 0x0E, Bit 2. The BIST
signature result varies based on the channel configuration.
BUILT-IN SELF-TEST (BIST)
The output test options are shown in Table 13. When an output
test mode is enabled, the analog section of the receiver is disconnected from the digital back-end blocks, and the test pattern
is run through the output formatting block. Some of the test
patterns are subject to output formatting. The seed value for the
PN sequence tests can be forced if the PN reset bits are used to
hold the generator in reset mode by setting Bit 4 or Bit 5 of
Register 0x0D. These tests can be performed with or without an
analog signal (if present, the analog signal is ignored), but they
require an encode clock. For more information, see Application
Note AN-877, Interfacing to High Speed ADCs via SPI.
The BIST is a thorough test of the digital portion of the selected
AD6642 signal path. When enabled, the test runs from an internal
pseudorandom noise (PN) source through the digital datapath
starting at the ADC block output. The BIST sequence runs for
512 cycles and stops. The BIST signature value for the selected
channel is written to Register 0x24 and Register 0x25. If one channel is selected, its BIST signature is written to the two registers.
If Channel A and Channel B are both selected, the results from
Channel A are written to the BIST signature registers.
OUTPUT TEST MODES
Rev. A | Page 24 of 32
AD6642
SERIAL PORT INTERFACE (SPI)
During an instruction phase, a 16-bit instruction is transmitted.
The first bit of the first byte in a serial data transfer frame indicates
whether a read command or a write command is issued. Data
follows the instruction phase, and its length is determined by
the W0 and W1 bits. All data is composed of 8-bit words.
The AD6642 serial port interface (SPI) allows the user to configure the receiver for specific functions or operations through a
structured internal register space. The SPI provides added flexibility
and customization, depending on the application. Addresses are
accessed via the serial port and can be written to or read from
via the port. Memory is organized into bytes that can be further
divided into fields, which are documented in the Memory Map
section. For detailed operational information, see Application
Note AN-877, Interfacing to High Speed ADCs via SPI.
The instruction phase determines whether the serial frame is a
read or write operation, allowing the serial port to be used both
to program the chip and to read the contents of the on-chip
memory. If the instruction is a read operation, the serial data
input/output (SDIO) pin changes direction from an input to an
output at the appropriate point in the serial frame.
CONFIGURATION USING THE SPI
Three pins define the SPI of the AD6642: SCLK, SDIO, and CSB
(see Table 12). SCLK (a serial clock) is used to synchronize the
read and write data presented from and to the AD6642. SDIO
(serial data input/output) is a bidirectional pin that allows data
to be sent to and read from the internal memory map registers.
CSB (chip select bar) is an active low control that enables or
disables the read and write cycles.
Data can be sent in MSB first mode or in LSB first mode.
MSB first is the default mode on power-up and can be changed
via the SPI port configuration register. For more information
about this and other features, see Application Note AN-877,
Interfacing to High Speed ADCs via SPI.
HARDWARE INTERFACE
The pins described in Table 12 constitute the physical interface
between the user programming device and the serial port of the
AD6642. The SCLK pin and the CSB pin function as inputs
when using the SPI interface. The SDIO pin is bidirectional,
functioning as an input during the write phase and as an output
during readback.
Table 12. Serial Port Interface Pins
Pin
SCLK
Function
Serial clock. Serial shift clock input. SCLK is used to
synchronize serial interface reads and writes.
Serial data input/output. Bidirectional pin that serves
as an input or an output, depending on the instruction
being sent and the relative position in the timing frame.
Chip select bar (active low). This control gates the read
and write cycles.
SDIO
CSB
The SPI interface is flexible enough to be controlled by either
FPGAs or microcontrollers. One method for SPI configuration
is described in detail in Application Note AN-812, Microcontroller-Based Serial Port Interface (SPI) Boot Circuit.
The falling edge of the CSB pin, in conjunction with the rising
edge of the SCLK pin, determines the start of the framing. An
example of the serial timing can be found in Figure 51 (for
symbol definitions, see Table 5).
The SPI port should not be active during periods when the full
dynamic performance of the AD6642 is required. Because the
SCLK signal, the CSB signal, and the SDIO signal are typically
asynchronous to the ADC clock, noise from these signals can
degrade AD6642 performance. If the on-board SPI bus is used
for other devices, it may be necessary to provide buffers between
this bus and the AD6642 to prevent these signals from transitioning at the receiver inputs during critical sampling periods.
CSB can be held low indefinitely, which permanently enables
the device; this is called streaming. CSB can stall high between
bytes to allow for additional external timing. When CSB is tied
high, SPI functions are placed in high impedance mode.
tDS
tS
tHIGH
tH
tCLK
tDH
tLOW
CSB
SCLK DON’T
CARE
DON’T
CARE
R/W
W1
W0
A12
A11
A10
A9
A8
A7
D5
D4
D3
D2
D1
D0
DON’T CARE
08563-073
SDIO
DON’T CARE
Figure 51. Serial Port Interface Timing Diagram
Rev. A | Page 25 of 32
AD6642
MEMORY MAP
READING THE MEMORY MAP REGISTER TABLE
Logic Levels
Each row in the memory map register table has eight bit locations (see Table 13). The memory map is roughly divided into
four sections: the chip configuration registers (Address 0x00
and Address 0x01); the channel index and transfer registers
(Address 0x05 and Address 0xFF); the ADC function registers,
including setup, control, and test (Address 0x08 to Address 0x25);
and the digital feature control registers (Address 0x3A to
Address 0x3E).
An explanation of logic level terminology follows:
The memory map register table (see Table 13) provides the
default hexadecimal value for each hexadecimal address shown.
The column with the heading (MSB) Bit 7 is the start of the
default hexadecimal value given. Application Note AN-877,
Interfacing to High Speed ADCs via SPI, documents the functions
controlled by Register 0x00 to Register 0xFF. The remaining
registers, Register 0x3A to Register 0x3E, are documented in
the Memory Map Register Descriptions section.
Open Locations
All address and bit locations that are not included in Table 13 are
not currently supported for this device. Unused bits of a valid
address location should be written with 0s. Writing to these
locations is required only when part of an address location is
open (for example, Address 0x18). If the entire address location
is open (for example, Address 0x13), this address location
should not be written.
Default Values
After the AD6642 is reset, critical registers are loaded with
default values. The default values for the registers are given in
the memory map register table (see Table 13).
•
•
“Bit is set” is synonymous with “bit is set to Logic 1” or
“writing Logic 1 for the bit.”
“Clear a bit” is synonymous with “bit is set to Logic 0” or
“writing Logic 0 for the bit.”
Transfer Register Map
Address 0x08 to Address 0x3E are shadowed. Writes to these
addresses do not affect part operation until a transfer command
is issued by writing 0x01 to Address 0xFF, setting the transfer
bit. This allows these registers to be updated internally and
simultaneously when the transfer bit is set. The transfer bit is
autoclearing.
Channel-Specific Registers
Some channel setup functions, such as the NSR control function, can be programmed differently for each channel. In these
cases, channel address locations are internally duplicated for
each channel. These registers and bits are designated in Table 13
as local. Local registers and bits can be accessed by setting the
appropriate channel bits in Register 0x05.
If multiple channel bits are set, the subsequent write affects the
registers of all selected channels. In a read cycle, only a single
channel should be selected to read one of the registers. If multiple
channels are selected during a SPI read cycle, the part returns
the value for Channel A only. Registers and bits designated as
global in Table 13 affect the entire part or the channel features
for which there are no independent per-channel settings. The
settings in Register 0x05 do not affect the global registers and bits.
Rev. A | Page 26 of 32
AD6642
MEMORY MAP REGISTER TABLE
All address and bit locations that are not included in Table 13 are not currently supported for this device.
Table 13. Memory Map Registers
Addr. Register
(MSB)
(Hex) Name
Bit 7
Chip Configuration Registers
0x00
SPI port
Open
configuration
(global)
Chip ID
(global)
Channel Index and Transfer Registers
0x05
Channel
Open
index
Bit 6
Bit 5
Bit 4
Bit 3
Bit 2
Bit 1
(LSB)
Bit 0
LSB first
Soft reset
1
1
Soft reset
LSB first
Open
0x01
8-bit chip ID, Bits[7:0]
AD6642 = 0x7A (default)
Default
Value
(Hex)
0x18
0x7A
Enable
output
port for
Channel
A and
Channel
B
Open
Open
Open
Open
Channel
B enable
Channel
A enable
0xCF
Open
Open
Open
Open
Open
Open
Open
SW
transfer
1 = on
0 = off
(default)
0x00
ADC Function Registers
0x08
Power modes
Open
Open
Open
Internal power-down
mode (local)
00 = normal operation
(default)
01 = full power-down
10 = standby
0x0B
Clock divide
(global)
Open
Open
Open
Open
External
powerdown pin
function
(global)
0 = full
powerdown
1=
standby
Clock divide phase
000 = 0 input clock cycles delayed
001 = 1 input clock cycle delayed
010 = 2 input clock cycles delayed
0x0C
Shuffle mode
(local)
Open
Open
0xFF
Transfer
Open
Open
Open
Rev. A | Page 27 of 32
Clock divide ratio
000 = divide by 1
001 = divide by 2
010 = divide by 3
011 = divide by 4
100 = divide by 5
101 = divide by 6
110 = divide by 7
111 = divide by 8
Open
Shuffle mode enable
00 = shuffle disabled
01 = shuffle enabled
0x00
Comments
Nibbles are
mirrored so
that LSB first
or MSB first
mode is set
correctly,
regardless of
shift mode.
To control
this register,
all channel
index bits in
Register 0x05
must be set.
Read only.
Bits are set to
determine
which
channel
on the chip
receives the
next write
command;
applies to
local registers.
Synchronously
transfers
data from
the master
shift register
to the slave.
Determines
generic
modes
of chip
operation.
0x00
0x01
Enables or
disables
shuffle mode
AD6642
Addr.
(Hex)
0x0D
Register
Name
Test mode
(local)
(MSB)
Bit 7
Open
Bit 6
Open
0x0E
BIST enable
(local)
Open
Open
0x10
Offset adjust
(local)
Open
Open
0x14
Output mode
(local)
Open
Open
0x15
Output adjust
(local)
Open
Open
0x16
Clock phase
control
(local)
0x17
DCO output
delay
(global)
Invert DCO
clock
0 = off
1 = on
DCO delay
enable
0 = off
1 = on
0x18
VREF select
(global)
Open
Bit 5
Reset
long PN
generator
0 = on
1 = off
(default)
Bit 4
Reset
short PN
generator
0 = on
1 = off
(default)
Bit 3
Open
(LSB)
Bit 0
Default
Value
(Hex)
0x00
Open
Bit 2
Bit 1
Output test mode
000 = off (normal operation)
001 = midscale short
010 = positive FS
011 = negative FS
100 = alternating checkerboard
101 = PN sequence long
110 = PN sequence short
111 = 1/0 word toggle
Open
Open
Open
BIST reset
Open
BIST
0 = on
enable
1 = off
1 = on
(default)
0 = off
(default)
Offset adjustment in LSBs from +127 to −128
(twos complement format)
011111 = +31 LSB
011110 = +30 LSB
011101 = +29 LSB
…
000010 = +2 LSB
000001 = +1 LSB
000000 = 0 LSB
…
111111 = −1 LSB
111110 = −2 LSB
111101 = −3 LSB
…
100001 = −31 LSB
100000 = −32 LSB
Output format (local)
Open
Output
Open
Output
00 = offset binary
invert
enable bar
01 = twos
(local)
(local)
complement
1 = on
1 = off
0 = off
0 = on
Open
Open
Output port LVDS drive current
0000 = 3.72 mA
0001 = 3.5 mA (default)
0010 = 3.3 mA
0011 = 2.96 mA
0100 = 2.82 mA
0101 = 2.57 mA
0110 = 2.27 mA
0111 = 2.0 mA
1000 = 2.0 mA
Open
Open
Open
Open
Open
Open
0x00
Open
Open
0x00
Open
Open
Output port DCO clock delay
00000 = 100 ps additional delay on the DCO pin
00001 = 200 ps additional delay on the DCO pin
00010 = 300 ps additional delay on the DCO pin
…
11101 = 3.0 ns additional delay on the DCO pin
11110 = 3.1 ns additional delay on the DCO pin
11111 = 3.2 ns additional delay on the DCO pin
Internal VREF full-scale adjustment
Main reference full-scale VREF adjustment
01111: internal 2.087 V p-p
…
00001: internal 1.772 V p-p
00000: internal 1.75 V p-p
…
11111: internal 1.727 V p-p
…
10000: internal 1.383 V p-p
Rev. A | Page 28 of 32
0x00
0x00
0x00
0x01
0x00
Comments
When set,
the test data
is placed on
the output
pins in place
of normal
data.
When Bit 0
is set, the
built-in selftest function
is initiated.
Device
offset trim.
Configures
the outputs
and the
format of
the data.
Output
current
adjustments.
When Bit 7
is set, clock
polarity is
reversed.
Enable DCO
delay and
set the delay
time.
Select
adjustments
for VREF.
AD6642
Addr.
(Hex)
0x24
Register
(MSB)
Name
Bit 7
BIST signature
LSB (local)
0x25
BIST signature
MSB (local)
Digital Feature Control Registers
0x3A
Sync control
Open
(global)
Bit 6
Bit 5
Bit 4
Bit 3
BIST Signature[7:0]
Bit 2
Bit 1
Default
Value
(Hex)
0x00
Comments
Read only.
0x00
Read only.
Master
sync
enable
0 = off
1 = on
0x00
Control
register to
synchronize
the clock
divider.
NSR
enable
0 = off
1 = on
(used
only if
Bit 4 = 1;
otherwise
ignored)
0x00
Noise
shaping
requantizer
(NSR)
controls.
0x1C
NSR
frequency
tuning word.
(LSB)
Bit 0
BIST Signature[15:8]
Open
Open
Open
Open
Open
MODE
pin disable
0 = MODE
pin used
1 = MODE
pin disabled
NSR mode
000 = 22% BW mode
001 = 33% BW mode
Clock
divider
sync
enable
0 = off
1 = on
0x3C
NSR control
(local)
Open
Open
Open
0x3E
NSR tuning
word (local)
Open
Open
NSR tuning word
See the Noise Shaping Requantizer (NSR) section.
Equations for the tuning word are dependent on the NSR mode.
MEMORY MAP REGISTER DESCRIPTIONS
Bits[3:1]— NSR Mode
For additional information about functions controlled
in Register 0x00 to Register 0xFF, see Application Note
AN-877, Interfacing to High Speed ADCs via SPI.
Bits[3:1] determine the bandwidth mode of the NSR. When
Bits[3:1] are set to 000, the NSR is configured for a 22% BW
mode that provides enhanced SNR performance over 22% of
the sample rate. When Bits[3:1] are set to 001, the NSR is configured for a 33% BW mode that provides enhanced SNR
performance over 33% of the sample rate.
Sync Control (Register 0x3A)
Bits[7:2]—Reserved
Bit 1—Clock Divider Sync Enable
Bit 0—NSR Enable
Bit 1 gates the sync pulse to the clock divider. The sync signal is
enabled when Bit 1 is high and Bit 0 is high. This is continuous
sync mode.
Bit 0—Master Sync Enable
The NSR is enabled when Bit 0 is high and disabled when Bit 0
is low. Bit 0 is ignored unless the MODE pin disable bit (Bit 4)
is set.
NSR Tuning Word (Register 0x3E)
Bits[7:6]—Reserved
Bit 0 must be high to enable any of the sync functions. If
the sync capability is not used, this bit should remain low
to conserve power.
Bits[5:0]— NSR Tuning Word
NSR Control (Register 0x3C)
Bits[7:5]—Reserved
Bit 4—MODE Pin Disable
Bit 4 specifies whether the selected channels will be controlled
by the MODE pin. Local registers act on the channels that are
selected by the channel index register (Address 0x05).
The NSR tuning word sets the band edges of the NSR band. In
22% BW mode, there are 57 possible tuning words; in 33% BW
mode, there are 34 possible tuning words. For either mode, each
step represents 0.5% of the ADC sample rate. For the equations
used to calculate the tuning word based on the BW mode of
operation, see the Noise Shaping Requantizer (NSR) section.
Rev. A | Page 29 of 32
AD6642
APPLICATIONS INFORMATION
DESIGN GUIDELINES
VCMx Pins
Before starting the design and layout of the AD6642 in a system,
it is recommended that the designer become familiar with these
guidelines, which discuss the special circuit connections and
layout requirements needed for certain pins.
The VCMx pins are provided to set the common-mode level
of the analog inputs. The VCMx pins should be decoupled to
ground with a 0.1 μF capacitor, as shown in Figure 31.
Power and Ground Recommendations
The SPI port should not be active during periods when the full
dynamic performance of the AD6642 is required. Because the
SCLK signal, the CSB signal, and the SDIO signal are typically
asynchronous to the ADC clock, noise from these signals can
degrade AD6642 performance. If the on-board SPI bus is used
for other devices, it may be necessary to provide buffers between
this bus and the AD6642 to prevent these signals from transitioning at the receiver inputs during critical sampling periods.
When connecting power to the AD6642, it is recommended
that two separate 1.8 V supplies be used. Use one supply for
analog (AVDD); use a separate supply for the digital outputs
(DRVDD). The AVDD and DRVDD supplies should be isolated
with separate decoupling capacitors. Several different decoupling
capacitors can be used to cover both high and low frequencies.
These capacitors should be located close to the point of entry
at the PCB level and close to the pins of the part, with minimal
trace length.
SPI Port
A single PCB ground plane should be sufficient when using the
AD6642. With proper decoupling and smart partitioning of the
PCB analog, digital, and clock sections, optimum performance
is easily achieved.
Rev. A | Page 30 of 32
AD6642
OUTLINE DIMENSIONS
A1 CORNER
INDEX AREA
10.10
10.00
9.90
9
7
3
1
5
12 11 10
8
6
4
2
A
B
C
D
E
F
G
H
J
K
L
M
BALL A1
INDICATOR
TOP VIEW
8.80
BSC SQ
0.80 BSC
BOTTOM VIEW
DETAIL A
1.40 MAX
DETAIL A
1.00
0.85
0.43 MAX
0.25 MIN
SEATING
PLANE
COPLANARITY
0.12 MAX
COMPLIANT WITH JEDEC STANDARDS MO-205-AC.
012006-0
0.55
0.50
0.45
BALL DIAMETER
Figure 52. 144-Ball Chip Scale Package Ball Grid Array [CSP_BGA]
(BC-144-1)
Dimensions shown in millimeters
ORDERING GUIDE
Model1
AD6642BBCZ
AD6642BBCZRL
AD6642EBZ
1
Temperature Range
−40°C to +85°C
−40°C to +85°C
Package Description
144-Ball Chip Scale Package Ball Grid Array [CSP_BGA]
144-Ball Chip Scale Package Ball Grid Array [CSP_BGA]
Evaluation Board
Z = RoHS Compliant Part.
Rev. A | Page 31 of 32
Package Option
BC-144-1
BC-144-1
AD6642
NOTES
©2009–2010 Analog Devices, Inc. All rights reserved. Trademarks and
registered trademarks are the property of their respective owners.
D08563-0-7/10(A)
Rev. A | Page 32 of 32
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