AD7868AQ

a LC2MOS Complete, 12-Bit Analog I/O System AD7868 FEATURES Complete 12-Bit I/O System, Comprising: 12-Bit ADC with Track/Hold Amplifier 83 kHz Throughout Rate 72 dB SNR 12-Bit DAC with Output Amplifier 3 ms Settling Time 72 dB SNR On-Chip Voltage Reference Operates from 65 V Supplies Low Power – 130 mW typ Small 0.3" Wide DIP APPLICATIONS Digital Signal Processing Speech Recognition and Synthesis Spectrum Analysis High Speed Modems DSP Servo Control FUNCTIONAL BLOCK DIAGRAM VDD RI DAC R LDAC 12-BIT DAC TFS TCLK DT DAC SERIAL INTERFACE The AD7868 is a complete 12-bit I/O system containing a DAC and an ADC . The ADC is a successive approximation type with a track-and-hold amplifier having a combined throughput rate of 83 kHz. The DAC has an output buffer amplifier with a settling time of 3 µs to 12 bits. Temperature compensated 3 V buried Zener references provide precision references for the DAC and ADC. Interfacing to both the DAC and ADC is serial, minimizing pin count and giving a small 24-pin package size. Standard control signals allow serial interfacing to most DSP machines. Asynchronous ADC conversion control and DAC updating is made possible with the CONVST and LDAC logic inputs. The AD7868 operates from ± 5 V power supplies, the analog input/output range of the ADC/DAC is ± 3 V. The part is fully specified for dynamic parameters such as signal-to-noise ratio and harmonic distortion as well as traditional dc specifications. VOUT DAC 3V REFERENCE RO DAC ADC 3V REFERENCE CONTROL RFS RCLK DR ADC SERIAL INTERFACE RO ADC R CLK CLOCK R 12-BIT ADC CONVST AD7868 GENERAL DESCRIPTION R DGND VIN TRACK/HOLD VSS AGND PRODUCT HIGHLIGHTS 1. Complete 12-Bit I/O System. The AD7868 contains a 12-bit ADC with a track-and-hold amplifier and a 12-bit DAC with output amplifier. Also included are separate on-chip voltage references for the DAC and the ADC. 2. Dynamic Specifications for DSP Users. In addition to traditional dc specifications, the AD7868 is specified for ac parameters including signal-to-noise ratio and harmonic distortion. These parameters along with important timing parameters are tested on every device. 3. Small Package. The AD7868 is available in a 24-pin DIP and a 28-pin SOIC package. The part is available in a 24-pin, 0.3" wide, plastic or hermetic dual-in-line package (DIP) and in a 28-pin, plastic SOIC package. REV. B Information furnished by Analog Devices is believed to be accurate and reliable. However, no responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other rights of third parties which may result from its use. No license is granted by implication or otherwise under any patent or patent rights of Analog Devices. © Analog Devices, Inc., 1996 One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A. Tel: 617/329-4700 Fax: 617/326-8703 AD7868–SPECIFICATIONS (V = +5 V 6 5%, V = –5 V 6 5%, AGND = DGND = 0 V, f ADC SECTION DD SS CLK = 2.0 MHz external. All specifications TMIN to TMAX- unless otherwise noted.) A Version1 B Version1 T Version1 Units Test Conditions/Comments 70 70 –78 72 71 –78 70 70 –76 dB min dB min dB max Peak Harmonic or Spurious Noise –78 –78 –76 dB max VIN = 10 kHz Sine Wave, fSAMPLE = 83 kHz Typically 71.5 dB for 0 < VIN < 41.5 kHz VIN = 10 kHz Sine Wave, fSAMPLE = 83 kHz Typically 71.5 dB for 0 < VIN < 41.5 kHz VIN = 10 kHz Sine Wave, fSAMPLE = 83 kHz Typically 71.5 dB for 0 < VIN < 41.5 kHz Intermodulation Distortion (IMD) Second Order Terms Third Order Terms Track/Hold Acquisition Time –78 –80 2 –78 –80 2 –76 –78 2 dB max dB max µs max 12 12 ± 12 ± 0.9 ±5 ±5 ±5 12 12 ± 12 ±1 ± 0.9 ±5 ±5 ±5 12 12 ± 12 ±1 ± 0.9 ±5 ±5 ±5 Bits Bits LSB typ LSB max LSB max LSB max LSB max LSB max ANALOG INPUT Input Voltage Range Input Current ±3 ±1 ±3 ±1 ±3 ±1 Volts mA max REFERENCE OUTPUT6 RO ADC @ +25°C RO ADC TC RO ADC TC Reference Load Sensitivity (∆RO ADC vs. ∆I) 2.99/3.01 2.99/3.01 2.99/3.01 ± 25 ± 25 ± 25 ± 40 ± 50 –1.5 –1.5 –1.5 V min/V max ppm/°C typ ppm/°C max mV max LOGIC INPUTS (CONVST, CLK, CONTROL) Input High Voltage, VINH Input Low Voltage, VINL Input Current, IIN Input Current7 (CONTROL Input Only) Input Capacitance, CIN8 2.4 0.8 ± 10 ± 10 10 2.4 0.8 ± 10 ± 10 10 2.4 0.8 ± 10 ± 10 10 V min V max µA max µA max pF max VDD = 5 V ± 5% VDD = 5 V ± 5% VIN = 0 V to VDD VIN = VSS to DGND 0.4 0.4 0.4 V max ISINK = 1.6 mA, Pull-Up Resistor = 4.7 kΩ ISINK = 2.6 mA, Pull-Up Resistor = 2 kΩ Parameter 2 DYNAMIC PERFORMANCE Signal-to-Noise Ratio3, 4 (SNR) @ +25°C TMIN to TMAX Total Harmonic Distortion (THD) DC ACCURACY Resolution Minimum Resolution Integral Nonlinearity Integral Nonlinearity Differential Nonlinearity Bipolar Zero Error Positive Gain Error5 Negative Gain Error5 fa = 9 kHz, fb = 9.5 kHz, fSAMPLE = 50 kHz fa = 9 kHz, fb = 9.5 kHz, fSAMPLE = 50 kHz No Missing Codes Are Guaranteed Reference Load Current Change (0 µA–500 µA), Reference Load Should Not Be Changed During Conversion LOGIC OUTPUTS DR, RFS Outputs Output Low Voltage, VOL RCLK Output Output Low Voltage, VOL DR, RFS, RCLK Outputs Floating-State Leakage Current Floating-State Output Capacitance8 0.4 0.4 0.4 V max ± 10 15 ± 10 15 ± 10 15 µA max pF max CONVERSION TIME External Clock Internal Clock 10 10 10 10 10 10 µs max µs max The Internal Clock Has a Nominal Value of 2.0 MHz POWER REQUIREMENTS VDD VSS IDD ISS Total Power Dissipation +5 –5 22 12 170 +5 –5 22 12 170 +5 –5 25 13 190 V nom V nom mA max mA max mW max For Both DAC and ADC ± 5% for Specified Performance ± 5% for Specified Performance Cumulative Current from the Two VDD Pins Cumulative Current from the Two VSS Pins Typically 130 mW NOTES 1 Temperature ranges are as follows: A/B Versions, –40°C to +85°C; T Version, –55°C to +125°C. 2 VIN = ± 3 V 3 SNR calculation includes distortion and noise components. 4 SNR degradation due to asynchronous DAC updating during conversion is 0.1 dB typ. 5 Measured with respect to internal reference. 6 For capacitive loads greater than 50 pF a series resistor is required (see INTERNAL REFERENCE section). 7 Tying the CONTROL input to V DD places the device in a factory test mode where normal operation is not exhibited. 8 Sample tested @ +25°C to ensure compliance. Specifications subject to change without notice. –2– REV. B AD7868 DAC SECTION (VDD = +5 V 6 5%, VSS = –5 V 6 5%, AGND = DGND = 0 V, RI DAC = +3 V and decoupled as shown in Figure 2, VOUT Load to AGND; RL = 2 kΩ, CL = 100 pF. All specifications TMIN to TMAX unless otherwise noted.) Parameter A Version1 B Version1 T Version1 Units Test Conditions/Comments 70 70 –78 72 71 –78 70 70 –76 dB min dB min dB max –78 –78 –76 dB max VOUT = 1 kHz Sine Wave, fSAMPLE = 83 kHz Typically 71.5 dB at +25°C for 0 < VOUT < 20 kHz4 VOUT = 1 kHz Sine Wave, fSAMPLE = 83 kHz Typically –84 dB at +25°C for 0 < VOUT < 20 kHz4 VOUT = 1 kHz Sine Wave, fSAMPLE = 83 kHz Typically –84 dB at +25°C for 0 < VOUT < 20 kHz4 12 ± 1/2 12 ± 1/2 ±1 ± 0.9 ±5 ±5 ±5 12 ± 1/2 ±1 ± 0.9 ±5 ±5 ±5 Bits LSB typ LSB max LSB max LSB max LSB max LSB max 2 DYNAMIC PERFORMANCE Signal-to-Noise Ratio3 (SNR) @ +25°C TMIN to TMAX Total Harmonic Distortion (THD) Peak Harmonic or Spurious Noise DC ACCURACY Resolution Integral Nonlinearity Integral Nonlinearity Differential Nonlinearity Bipolar Zero Error Positive Full-Scale Error5 Negative Full-Scale Error5 ± 0.9 ±5 ±5 ±5 Guaranteed Monotonic REFERENCE OUTPUT6 RO ADC @ +25°C RO ADC TC RO ADC TC Reference Load Change (∆RO DAC vs. ∆I) 2.99/3.01 2.99/3.01 2.99/3.01 ± 25 ± 25 ± 25 ± 40 ± 50 –1.5 –1.5 –1.5 V min/V max ppm/°C typ ppm/°C max mV max Reference Load Current Change (0–500 µA) REFERENCE INPUT RI DAC Input Range Input Current 2.85/3.15 2.85/3.15 2.85/3.15 1 1 1 V min/V max 3 V ± 5% µA max LOGIC INPUTS (LDAC, TFS, TCLK, DT) Input High Voltage, VINH Input Low Voltage, VINL Input Current, IIN Input Capacitance, CIN7 2.4 0.8 ± 10 10 2.4 0.8 ± 10 10 2.4 0.8 ± 10 10 V min V max µA max pF max ANALOG INPUT Output Voltage Range dc Output Impedance Short-Circuit Current ±3 0.3 20 ±3 0.3 20 ±3 0.3 20 V nom Ω typ mA typ AC CHARACTERISTICS7 Voltage Output Settling-Time Positive Full-Scale Change Negative Full-Scale Change Digital-to-Analog Glitch Impulse Digital Feedthrough VIN to VOUT Isolation 3 3 10 2 100 3 3 10 2 100 3 3 10 2 100 µs max µs max nV secs typ nV secs typ dB typ POWER REQUIREMENTS As per ADC Section NOTES 1 Temperature ranges are as follows: A/B Versions, –40°C to +85°C; T Version, –55°C to +125°C. 2 VOUT (pk–pk) = ± 3 V. 3 SNR calculation includes distortion and noise components. 4 Using external sample and hold. 5 Measured with respect to RI DAC and includes bipolar offset error. 6 For capacitive loads greater than 50 pF a series resistor is required (see INTERNAL REFERENCE section). 7 Sample tested @ +25°C to ensure compliance. Model Specifications subject to change without notice. AD7868AN AD7868AQ AD7868BN AD7868BQ AD7868AR AD7868BR VDD = 5 V ± 5% VDD = 5 V ± 5% VIN = 0 V to VDD Settling Time to Within ± 1/2 LSB of Final Value Typically 2 µs Typically 2.5 µs DAC Code Change All 1s to All 0s VIN = ± 3 V, 41.5 kHz Sine Wave ORDERING GUIDE Temperature Range –40°C to +85°C –40°C to +85°C –40°C to +85°C –40°C to +85°C –40°C to +85°C –40°C to +85°C SNR Relative Accuracy (LSB) Package Option* 70 dB 70 dB 72 dB 72 dB 70 dB 72 dB ± 1/2 typ ± 1/2 typ ± 1 max ± 1 max ± 1/2 typ ± 1 max N-24 Q-24 N-24 Q-24 R-28 R-28 *N = Plastic DIP; Q = Cerdip; R = SOIC (Small Outline IC). REV. B –3– AD7868 TIMING CHARACTERISTICS1, 2 (V Parameter ADC TIMING t1 t2 3 t3 t4 t5 4 t6 t135 DAC TIMING t7 t8 t9 6 t10 t11 t12 DD = +5 V 6 5%, VSS = –5 V 6 5%, AGND = DGND = 0 V) Limit at TMIN, TMAX (A, B Versions) Limit at TMIN, TMAX (T Version) 50 440 100 20 100 155 4 100 2 RCLK +200 to 3 RCLK + 200 50 75 150 30 75 40 Units Conditions/Comments 50 440 100 20 100 155 4 100 2 RCLK +200 to 3 RCLK + 200 ns min ns min ns min ns min ns max ns max ns min ns max ns typ CONVST Pulse Width RCLK Cycle Time, Internal Clock RFS to RCLK Falling Edge Setup Time RCLK Rising Edge to RFS 50 100 200 40 100 40 ns min ns min ns min ns min ns min ns min RCLK to Valid Data Delay, CL = 35 pF Bus Relinquish Time after RCLK CONVST to RFS Delay TFS to TCLK Falling Edge TCLK Falling Edge to TFS TCLK Cycle Time Data Valid to TCLK Setup Time Data Valid to TCLK Hold Time LDAC Pulse Width NOTES 1 Timing specifications are sample tested at +25°C to ensure compliance. All input signals are specified with tr = tf = 5 ns (10% to 90% of 5 V) and timed from a voltage level of 1.6 V. 2 Serial timing is measured with a 4.7 kΩ pull-up resistor on DR and RFS and a 2 kΩ pull-up resistor on RCLK . The capacitance on all three output is 35 pF. 3 When using internal clock, RCLK mark/space ratio (measured from a voltage level of 1.6 V) range is 40/60 to 60/40. For external clock, RCLK mark/space ratio = external clock mark/space ratio. 4 DR will drive higher capacitance loads but this will add to t 5 since it increases the external RC time constant (4.7 kΩ/CL) and hence the time to reach 2.4 V. 5 Time 2 RCLK to 3 RCLK depends on conversion start to ADC clock synchronization. 6 TCLK mark/space ratio is 40/60 to 60/40. ABSOLUTE MAXIMUM RATINGS* PIN CONFIGURATIONS (TA = +25°C unless otherwise noted) VDD to AGND . . . . . . . . . . . . . . . . . . . . . . . . . –0.3 V to +7 V VSS to AGND . . . . . . . . . . . . . . . . . . . . . . . . . +0.3 V to –7 V AGND to DGND . . . . . . . . . . . . . . . . . –0.3 V to VDD +0.3 V VOUT to AGND . . . . . . . . . . . . . . . . . . . . . . . . . . . VSS to VDD VIN to AGND . . . . . . . . . . . . . . . . VSS –0.3 V to VDD + 0.3 V RO ADC to AGND . . . . . . . . . . . . . . . –0.3 V to VDD + 0.3 V RO DAC to AGND . . . . . . . . . . . . . . . –0.3 V to VDD + 0.3 V RI DAC to AGND . . . . . . . . . . . . . . . –0.3 V to VDD + 0.3 V Digital Inputs to AGND . . . . . . . . . . . –0.3 V to VDD + 0.3 V Digital Outputs to AGND . . . . . . . . . . –0.3 V to VDD + 0.3 V Operating Temperature Range A, B Versions . . . . . . . . . . . . . . . . . . . . . . . –40°C to +85°C T Version . . . . . . . . . . . . . . . . . . . . . . . . . –55°C to +125°C Storage Temperature Range . . . . . . . . . . . . –65°C to +150°C Lead Temperature (Soldering, 10 secs) . . . . . . . . . . . +300°C Power Dissipation (Any Package) to +75°C . . . . . . . . 450 mW Derates above +75°C by . . . . . . . . . . . . . . . . . . . . 10 mW/°C DIP SOIC 1 24 CONTROL CONVST 1 28 CONTROL CLK 2 23 VDD CLK 2 27 VDD RFS 3 22 VSS RFS 3 26 VSS RCLK 4 21 VIN NC 4 25 NC RCLK 5 20 RO ADC 5 24 DR VIN DR 6 23 RO ADC DGND 7 22 AGND VDD 8 21 DGND AGND 9 20 TCLK VOUT 10 19 NC NC 11 18 NC VSS 12 17 DT 13 16 TFS RI DAC 14 15 LDAC CONVST DGND VDD AGND VOUT 6 AD7868 7 TOP VIEW (Not to Scale) 19 AGND 18 NC AD7868 TOP VIEW (Not to Scale) 17 DGND 8 16 TCLK 9 VSS 10 15 DT 14 TFS RO DAC 11 13 LDAC RI DAC 12 NC = NO CONNECT *Stresses above those listed under “Absolute Maximum Ratings” may cause permanent damage to the device. This is a stress rating only and functional operation of the device at these or any other conditions above those listed in the operational sections of this specification is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability. RO DAC NC = NO CONNECT CAUTION ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily accumulate on the human body and test equipment and can discharge without detection. Although the AD7868 features proprietary ESD protection circuitry, permanent damage may occur on devices subjected to high energy electrostatic discharges. Therefore, proper ESD precautions are recommended to avoid performance degradation or loss of functionality. –4– WARNING! ESD SENSITIVE DEVICE REV. B AD7868 PIN FUNCTION DESCRIPTION DIP Pin Number Mnemonic POWER SUPPLY 7 & 23 VDD 10 & 22 VSS 8 & 19 AGND 6 &17 DGND Function Positive Power Supply, 5 V ± 5%. Both VDD pins must be tied together. Negative Power Supply, –5 V ± 5%. Both VSS pins must be tied together. Analog Ground. Both AGND pins must be tied together. Digital Ground. Both DGND pins must be tied together. ANALOG SIGNAL AND REFERENCE 21 VIN ADC Analog Input. The ADC input range is ± 3 V. 9 VOUT Analog Output Voltage from DAC. This output comes from a buffer amplifier. The range is bipolar, ± 3 V with RI DAC = +3 V. 20 RO ADC Voltage Reference Output. The internal ADC 3 V reference is provided at this pin. This output may be used as a reference for the DAC by connecting it to the RI DAC input. The external load capability of this reference is 500 µA. 11 RO DAC DAC Voltage Reference Output. This is one of two internal voltage references. To operate the DAC with this internal reference, RO DAC should be connected to RI DAC. The external load capability of the reference is 500 µA. 12 RI DAC DAC Voltage Reference Input. The voltage reference for the DAC must be applied to this pin. It is internally buffered before being applied to the DAC. The nominal reference voltage for correct operation of the AD7868 is 3 V. ADC INTERFACE AND CONTROL 2 CLK Clock Input. An external TTL-compatible clock may be applied to this input. Alternatively, tying pin to VSS enables the internal laser-trimmed oscillator. RFS Receive Frame Synchronization, Logic Output. This is an active low open-drain output which provides 3 a framing pulse for serial data. An external 4.7 kΩ pull-up resistor is required on RFS. 4 RCLK Receive Clock, Logic Output. RCLK is the gated serial clock output which is derived from the internal or external ADC clock. If the CONTROL input is at VSS the clock runs continuously. With the CONTROL input at DGND the RCLK output is gated off (three-stated) after serial transmission is complete. RCLK is an open-drain output and requires an external 2 kΩ pull-up resistor. 5 DR Receive Data, Logic Output. This is an open-drain data output used in conjunction with RFS and RCLK to transmit data from the ADC. Serial data is valid on the falling edge of RCLK when RFS is low. An external 4.7 kΩ resistor is required on the DR output. 1 CONVST Convert Start, Logic Input. A low to high transition on this input puts the track-and-hold amplifier into the hold mode and starts an ADC conversion. This input in asynchronous to the CLK input. 24 CONTROL Control, Logic Input. With this pin at 0 V, the RCLK is noncontinuous. With this pin at –5 V, the RCLK is continuous. Note, tying this pin to VDD places the part in a factory test mode where normal operation is not exhibited. DAC INTERFACE AND CONTROL 14 TFS Transmit Frame Synchronization, Logic Input. This is a frame or synchronization signal for the DAC with serial data expected after the falling edge of this signal. 15 DT Transmit Data, Logic Input. This is the data input which is used in conjunction with TFS and TCLK to transfer serial data to the input latch. 16 TCLK Transmit Clock, Logic Input. Serial data bits are latched on the falling edge of TCLK when TFS is low. LDAC Load DAC, Logic Input. A new word is transferred into the DAC latch from the input latch on the 13 falling edge of this signal. 18 NC No Connect. REV. B –5– AD7868 CONVERTER DETAILS The AD7868 is a complete 12-bit I/O port, the only external components required for normal operation are pull-up resistors for the ADC data outputs and power supply decoupling capacitors. It is comprised of a 12-bit successive approximation ADC with a track/hold amplifier, a 12-bit DAC with a buffered output and two 3 V buried Zener references, a clock oscillator and control logic. ADC CLOCK The AD7868 has an internal clock oscillator which can be used for the ADC conversion procedure. The oscillator is enabled by tying the CLK input to VSS. The oscillator in laser trimmed at the factory to give a conversion time of between 8.5 and 10 µs. The mark/space ratio can vary from 40/60 to 60/40. Alternatively, an external TTL compatible clock may be applied to this input. The allowable mark/space ratio of an external clock is 40/60 to 60/40. RCLK is a clock output, used for the serial interface. This output is derived directly from the ADC clock source and can be switched off at the end of conversion with the CONTROL input. The conversion time for both external clock and continuous internal clock can vary from 19 to 20 rising clock edges depending on the conversion start to ADC clock synchronization. If a conversion is initiated within 30 ns prior to a rising edge of the ADC clock, the conversion time will consist of 20 rising clock edges, i.e., 9.5 µs conversion time. For noncontinuous internal clock, the conversion time is always 19 rising clock edges. ADC TRACK-AND-HOLD AMPLIFIER The track-and-hold amplifier on the analog input of the AD7868 allows the ADC to accurately convert an input sine wave of 6 V peak–peak amplitude to 12-bit accuracy. The input impedance is typically 9 kΩ, an equivalent circuit is shown in Figure 1. The input bandwidth of the track/hold amplifier is much greater than the Nyquist rate of the ADC, even when the ADC is operated at its maximum throughput rate. The 0.1 dB cutoff frequency occurs typically at 500 kHz. The track/hold amplifier acquires an input signal to 12-bit accuracy in less than 2 µs. 4.5kΩ The AD7868 has two on-chip temperature compensated buried Zener references which are factory trimmed to 3 V ± 10 mV. One reference provides the appropriate biasing for the ADC, while the other is available as a reference of the DAC. Both reference outputs are available (labeled RO DAC and RO ADC) and are capable of providing up to 500 µA to an external load. The maximum recommended capacitance on either of the reference output pins for normal operation is 50 pF. If either of the reference outputs is required to drive a capacitive load greater than 50 pF, then a 200 Ω resistor must be placed in series with the capacitive load. The addition of decoupling capacitors, 10 µF in parallel with 0.1 µF, as shown in Figure 2, improves noise performance. The improvement in noise performance can be seen from the graph in Figure 3. Note, this applies for the DAC output only; reference decoupling components do not affect ADC performance. So, a typical application will have just the DAC reference source decoupled with the other one open circuited. RO DAC or RO ADC* 200Ω EXT LOAD GREATER THAN 50pF 10µF 0.1µF RI DAC *RO DAC/RO ADC CAN BE LEFT OPEN CIRCUIT IF NOT USED Figure 2. Reference Decoupling Circuitry DAC OUTPUT AMPLIFIER TRACK/HOLD AMPLIFIER VIN INTERNAL REFERENCES The DAC input reference (RI DAC) can be stored externally or connected to any of the two on-chip references. Applications requiring good full-scale error matching between the DAC and the ADC should use the ADC reference as shown in Figure 4. ADC CONVERSION TIMING 4.5kΩ The operation of the track/hold amplifier is essentially transparent to the user. The track/hold amplifier goes from its track mode to its hold mode at the start of conversion on the rising edge of CONVST. The output from the voltage-mode DAC is buffered by a noninverting amplifier. The buffer amplifier is capable of developing ± 3 V across 2 kΩ and 100 pF load to ground and can produce 6 V peak-to-peak sine wave signals to a frequency of 20 kHz. The output is updated on the falling edge of the LDAC input. The output voltage settling time, to within 1/2 LSB of its final value, is typically less than 2 µs. TO INTERNAL COMPARATOR AD7868* TO INTERNAL 3V REFERENCE The small signal (200 mV p-p) bandwidth of the output buffer amplifier is typically 1 MHz. The output noise from the amplifier is low with a figure of 30 nV/√Hz at a frequency of 1 kHz. The broadband noise from the amplifier exhibits a typical peakto-peak figure of 150 µV for a 1 MHz output bandwidth. Figure 3 shows a typical plot of noise spectral density versus frequency for the output buffer amplifier and for either of the on-chip references. *ADDITIONAL PINS OMITTED FOR CLARITY Figure 1. ADC Analog Input The overall throughput rate is equal to the conversion time plus the track/hold amplifier acquisition time. For a 2.0 MHz input clock the throughput time is 12 µs max. –6– REV. B AD7868 the input signal is within the full dynamic range of the ADC. For applications which require that the input signal range match the full analog input dynamic range of the ADC, offset and full-scale errors have to be adjusted to zero. 500 TA = +25°C VDD = +5V 200 VSS = –5V ADC ADJUSTMENT REF OUT nV – √Hz 100 50 DAC OUTPUT WITH ALL 0s LOADED REF OUT DECOUPLED AS SHOWN IN FIGURE 2 20 10 50 100 200 1k 10k 2k 100k 20k FREQUENCY – Hz Figure 3. Noise Spectral Density vs. Frequency INPUT/OUTPUT TRANSFER FUNCTIONS A bipolar circuit for the AD7868 is shown in Figure 4. The analog input/output voltage range of the AD7868 is ± 3 V. The designed code transitions for the ADC occur midway between successive integer LSB values (i.e., 1/2 LSB, 3/2 LSB, 5/2 LSB . . . FS – 3/2 LSBs). The input/output code is 2s complement binary with 1 LSB = FS/4096 = 1.46 mV. The ideal transfer function is shown in Figure 5. AD7868* VIN VOUT ANALOG INPUT RANGE = ±3V ANALOG OUTPUT RANGE = ±3V RO ADC C2 0.1µF AGND *ADDITIONAL PINS OMITTED FOR CLARITY Figure 4. AD7868 Basic Bipolar Operation Using RO ADC as a Reference Input for the DAC 011...111 011...110 Apply a voltage of 2.9978 V (FS/2 – 3/2 LSBs) at V1. Adjust R2 until the ADC output code flickers between 0111 1111 1110 (7FE HEX) and 0111 1111 1111 (7FF HEX). ADC Negative Full-Scale Adjustment Apply a voltage of –2.9993 V (–FS/2 + 1/2 LSB) at V1 and adjust R2 until the ADC output code flickers between 1000 0000 0000 (800 HEX) and 1000 0000 0001 (801 HEX). Op amp A2 is included in Figure 6 for the DAC transfer function adjustment. Again offset must be adjusted before full scale. To adjust offset: load the DAC with 0000 0000 0000 (000 HEX) and trim the offset of A2 to 0 V. As with the ADC adjustment, gain error can be adjusted at either the first code transition (DAC negative full scale) or the last code transition (DAC positive full scale). The trim procedures for both cases are as follows: DAC Positive Full-Scale Adjustment DAC Negative Full-Scale Adjustment Load the DAC with 1000 0000 0000 (800 HEX) and adjust R7 until the op amp output voltage is equal to 3.0 V (–FS/2). 000...010 000...000 ADC Positive Full-Scale Adjustment Load the DAC with 0111 1111 1111 (7FF HEX) and adjust R7 until the op amp output voltage is equal to 2.9985 V, (FS/2 – 1 LSB). OUTPUT CODE 000...001 ADC gain error can be adjusted at either the first code transition (ADC negative full scale) or the last code transition (ADC positive full scale). The trim procedures for both cases are as follows (see Figure 6). DAC ADJUSTMENT RI DAC R1 200 C1 10µF Figure 6 has signal conditioning at the input and output of the AD7868 for trimming the end points of the transfer functions of both the ADC and the DAC. Offset error must be adjusted before full-scale error. For the ADC, this is achieved by trimming the offset of A1 while the input voltage, V1, is 1/2 LSB below ground. The trim procedure is as follows: apply a voltage of –0.73 mV (–1/2 LSB) at V1 in Figure 6 and adjust the offset voltage of A1 until the ADC output code flickers between 1111 1111 1111 (FFF HEX) and 0000 0000 0000 (000 HEX). -FS 2 + FS 111...111 2 111...110 V1 INPUT VOLTAGE RANGE = ±3V -1LSB FS = 6V 1LSB = 100...001 FS R1 10k 4096 R2 500 100...000 A1 R3 10k 0V INPUT VOLTAGE R5 10k Figure 5. AD7868 Input/Output Transfer Function R4 10k VIN AD7868* AGND OFFSET AND FULL-SCALE ADJUSTMENT R6 10k R7 500 A2 V0 OUTPUT VOLTAGE RANGE = ± 3V R8 10k In most digital signal processing (DSP) applications, offset and full-scale errors have little or no effect on system performance. Offset error can always be eliminated in the analog domain by ac coupling. Full-scale errors do not cause problems as long as REV. B VOUT *ADDITIONAL PINS OMITTED FOR CLARITY R10 10k R9 10k Figure 6. AD7868 with Input/Output Adjustment –7– AD7868 TIMING AND CONTROL serial clock which runs continuously. Both options are available on the AD7868 ADC. With the CONTROL input at 0 V, RCLK is noncontinuous and when it is at –5 V, RCLK is continuous. Communication with the AD7868 is managed by 6 dedicated pins. These consist of separate serial clocks, word framing or strobe pulses and data signals for both receiving and transmitting data. Conversion starts and DAC updating are controlled by two digital inputs; CONVST and LDAC. These inputs can be asserted independently of the microprocessor by an external timer when precise sampling intervals are required. Alternatively, the LDAC and CONVST can be driven from a decoded address bus allowing the microprocessor control over conversion start and DAC updating as well as data communication to the AD7868. DAC Timing The AD7868 DAC contains two latches, an input latch and a DAC latch. Data must be loaded to the input latch under the control of the TCLK, TFS and DT serial logic inputs. Data is then transferred from the input latch to the DAC latch under the control of the LDAC signal. Only the data in the DAC latch determines the analog output of the AD7868. Data is loaded to the input latch under control of TCLK, TFS and DT. The AD7868 DAC expects a 16-bit stream of serial data on its DT input. Data must be valid on the falling edge of TCLK. The TFS input provides the frame synchronization signal which tells the AD7868 DAC that valid serial data will be available for the next 16 falling edges of TCLK. Figure 8 shows the timing diagram for the serial data format. ADC Timing Conversion control is provided by the CONVST input. A low to high transition on CONVST input starts conversion and drives the track/hold amplifier into its hold mode. Serial data then becomes available while conversion is in progress. The corresponding timing diagram is shown in Figure 7. The word length is 16 bits; 4 leading zeros, followed by the 12-bit conversion result starting with the MSB. The data is synchronized to the serial clock output (RCLK) and is framed by the serial strobe (RFS). Data is clocked out on a low to high transition of the serial clock and is valid on the falling edge of this clock while the RFS output is low. RFS goes low at the start of conversion and the first serial data bit (which is the first leading zero) is valid on the first falling edge of RCLK. All the ADC serial lines are open-drain outputs and require external pull-up resistors. Although 16 bits of data are clocked into the input latch, only 12 bits are transferred into the DAC latch. Therefore, 4 bits in the stream are don’t cares since their value does not affect the DAC latch data. The bit positions are 4 don’t cares followed by the 12-bit DAC data starting with the MSB. The LDAC signal controls the transfer of data to the DAC latch. Normally, data is loaded to the DAC latch on the falling edge of LDAC. However, if LDAC is held low, then serial data is loaded to the DAC latch on the sixteenth falling edge of TCLK. If LDAC goes low during the loading of serial data to the input latch, no DAC latch update takes place on the falling edge of LDAC. If LDAC stays low until the serial transfer is completed, then the update takes place on the sixteenth falling edge of TCLK. If LDAC returns high before the serial data transfer is completed, no DAC latch update takes place. The serial clock out is derived from the ADC master clock source which may be internal or external. Normally, RCLK is required during the serial transmission only. In these cases it can be shut down (i.e., placed into high impedance) at the end of conversion to allow multiple ADCs to share a common serial bus. However, some serial systems (e.g., TMS32020) require a CONVERSION TIME t1 CONVST t13 RFS 1 t3 RCLK t2 t4 2, 3 t5 DR 1 DB11 t6 DB10 DB9 DB1 DB0 NOTES 1EXTERNAL 4.7k Ω PULL-UP RESISTOR 2EXTERNAL 2k Ω PULL-UP RESISTOR 3CONTINUOUS RCLK (DASHED LINE) WHEN THE CONTROL INPUT = –5V AND NONCONTINUOUS WHEN THE CONTROL INPUT = 0V Figure 7. ADC Control Timing Diagram t7 t8 TFS t9 TCLK t11 t10 DT DON'T DON'T DON'T DON'T CARE CARE CARE CARE DB11 DB10 DB1 DB0 Figure 8. DAC Control Timing Diagram –8– REV. B AD7868 AD7868 DYNAMIC SPECIFICATIONS The AD7868 is specified and 100% tested for dynamic performance specifications as well as traditional dc specifications such as integral and differential nonlinearity. These ac specifications are required for signal processing applications such as speech recognition, spectrum analysis, and high-speed modems. These applications require information on the converter’s effect on the spectral content of the input signal. Hence, the parameters for which the AD7868 is specified include SNR, harmonic distortion and peak harmonics. These terms are discussed in more detail in the following sections. Figure 10 shows a typical plot of effective number of bits versus frequency for an AD7868BQ with a sampling frequency of 83 kHz. The effective number of bits typically falls between 11.7 and 11.85 corresponding to SNR figures of 72.2 and 73.1 dB. Signal-to-Noise Ratio (SNR) SNR is the measured signal-to-noise ratio at the output of the ADC or DAC. The signal is the rms magnitude of the fundamental. Noise is the rms sum of all the nonfundamental signals up to half the sampling frequency (fs/2) excluding dc. SNR is dependent upon the number of levels used in the quantization process; the more levels, the smaller the quantization noise. The theoretical signal-to-noise ratio for a sine wave input is given by SNR = (6.02N + 1.76) dB (1) where N is the number of bits. Thus for an ideal 12-bit converter, SNR = 74 dB. Figure 9. AD7868, ADC FFT Plot 12 Effective Number of Bits N= SNR – 1.76 6.02 EFFECTIVE NUMBER OF BITS The formula given in Equation 1 relates the SNR to the number of bits. Rewriting the formula, as in Equation 2, it is possible to get a measure of performance expressed in effective number of bits (N). (2) The effective number of bits for a device can be calculated directly from its measured SNR. 11.5 11 SAMPLE FREQUENCY = 83 kHz TA = 25°C 10.5 Harmonic Distortion Harmonic distortion is the ratio of the rms sum of harmonics to the fundamental. For the AD7868, total harmonic distortion (THD) is defined as 2 THD = 20 log 2 2 2 2 V 2 +V 3 +V 4 +V 5 +V 6 V1 where V1 is the rms amplitude of the fundamental and V2, V3, V4, V5 and V6 are the rms amplitudes of the second through to the sixth harmonic. The THD is also derived from the FFT plot of the ADC or DAC output spectrum. ADC Testing The output spectrum from the ADC is evaluated by applying a sine-wave signal of very low distortion to the VIN input which is sampled at an 83 kHz sampling rate. A Fast Fourier Transform (FFT) plot is generated from which the SNR data can be obtained. Figure 9 shows a typical 2048 point FFT plot of the AD7868BQ ADC with an input signal of 10 kHz and a sampling frequency of 83 kHz. The SNR obtained from this graph is 73 dB. It should be noted that the harmonics are taken into account when calculating the SNR. REV. B 10 0 INPUT FREQUENCY – kHz 41.5 Figure 10. Effective Number of Bits vs. Frequency for the ADC DAC Testing A simplified diagram of the method used to test the dynamic performance specifications of the DAC is outlined in Figure 11. Data is loaded to the DAC under control of the microcontroller and associated logic. The output of the DAC is applied to a 9th order low-pass filter whose cutoff frequency corresponds to the Nyquist limit. The output of the filter is in turn applied to a 16-bit accurate digitizer. This digitizes the signal and the microcontroller generates an FFT plot from which the dynamic performance of the DAC can be evaluated. –9– AD7868 MICROCONTROLLER AD7868 DAC LOW-PASS FILTER quencies at an update rate of 83 kHz. The plot of Figure 14 is without a sample-and-hold on the DAC output while the plot of Figure 15 is generated with a sample-and-hold on the output. 16-BIT DIGITIZER R2 2k2 Figure 11. AD7868 DAC Dynamic Performance Test Circuit The digitizer sampling is synchronized with the DAC update rate to ease FFT calculations. The digitizer samples the DAC output after the output has settled to its new value. Therefore, if the digitizer were to sample the output directly it would effectively be sampling a dc value each time. As a result, the dynamic performance of the DAC would not be measured correctly. Using the digitizer directly on the DAC output would give better results than the actual performance of the DAC. Using a filter between the DAC and the digitizer means that the digitizer samples a continuously moving signal and the true dynamic performance of the AD7868 DAC output is measured. ADG201HS VOUT C9 330pF R1 2k2 AD7868* S1 D1 AD711 LDAC IN1 1µs ONE Q SHOT DELAY LDAC *ADDITIONAL PINS OMITTED FOR CLARITY Figure 13. DAC Sample-and-Hold Circuit 80 Figure 12 shows a typical 2048 point Fast Fourier Transform plot for the AD7868 DAC with an update rate of 83 kHz and an output frequency of 1 kHz. The SNR obtained from the graph is 73 dBs. 70 60 SNR – dBs 50 40 30 20 TA = +25°C 10 0 0 2 3 FREQUENCY – kHz 1 4 5 Figure 14. DAC Performance vs. Frequency (No Sampleand-Hold) 80 70 60 Figure 12. AD7868 DAC FFT Plot SNR – dBs 50 Some applications will require improved performance versus frequency from the AD7868 DAC. In these applications, a simple sample-and-hold circuit such as that outlined in Figure 13 will extend the very good performance of the DAC to 20 kHz. Other applications will already have an inherent sample-and-hold function following the AD7868 DAC output. An example of this type of application is driving a switched-capacitor filter where the updating of the DAC is synchronized with the switched-capacitor filter. This inherent sample-and-hold function also extends the frequency range performance. 40 30 20 TA = +25°C 10 0 0 5 10 FREQUENCY – kHz 15 20 Figure 15. DAC Performance vs. Frequency (Sample-andHold) Performance versus Frequency The typical performance plots of Figures 14 and 15 show the AD7868’s DAC performance over a wide range of input fre- –10– REV. B AD7868 MICROPROCESSOR INTERFACING Microprocessor interfacing to the AD7868 is via a serial bus that uses standard protocol compatible with DSP machines. The communication interface consists of separate transmit (DAC) and receive (ADC) sections whose operations can be either synchronous or asynchronous with respect to each other. Each section has a clock signal, a data signal and a frame or strobe pulse. Synchronous operation means that data is transmitted from the ADC and to the DAC at the same time. In this mode only one interface clock is needed and this has to be the ADC clock out, so RCLK must be connected to TCLK. For asynchronous operation, DAC and ADC data transfers are independent of each other, the ADC provides the receive clock (RCLK) while the transmit clock (TCLK) may be provided by the processor or the ADC or some other external clock source. DSP56000 internal serial control registers have to be configured for a 16-bit data word with valid data on the first falling clock edge. Conversion starts and DAC updating are controlled by an external timer. Data transfers, which occur during ADC conversions, are between the processor receive and transmit shift registers and the AD7868’s ADC and DAC. At the end of each 16-bit transfer the DSP56000 receives an internal interrupt indicating the transmit register is empty and the receive register is full. TIMER CONTROL Another option to be considered with serial interfacing is the use of a gated clock. A gated clock means that the device that is sending the data switches on the clock when data is ready to be transmitted and three states the clock output when transmission is complete. Only 16 clock pulses are transmitted with the first data bit getting latched into the receiving device on the first falling clock edge. Ideally, there is no need for frame pulses, however, the AD7868 DAC frame input (TFS) has to be driven high between data transmissions. The easiest method is to use RFS to drive TFS and use only synchronous interfacing. This avoids the use of interconnects between the processor and AD7868 frame signals. Not all processors have a gated clock facility, Figure 16 shows an example with the DSP56000. Table I below shows the number of interconnect lines between the processor and the AD7868 for the different interfacing options. The AD7868 has the facility to use different clocks for transmitting and receiving data. This option, however, only exists on some processors and normally just one clock (ADC clock) is used for all communication with the AD7868. For simplicity, all the interface examples in this data sheet use synchronous interfacing and use the ADC clock (RCLK) as an input for the DAC clock (TCLK). For a better understanding of each of these interfaces, consult the relevant processor data sheet. Table I. Interconnect Lines for Different Interfacing Options Configuration No. of Interconnects Signals Synchronous 4 CONVST LDAC + 5V DSP56000 AD7868* 4.7kΩ 2kΩ 4.7kΩ RFS SC0 TFS SCK RCLK SRD DR DT STD TCLK *ADDITIONAL PINS OMITTED FOR CLARITY Figure 16. AD7868—DSP56000 Interface AD7868—ADSP-2101/ADSP-2102 Interface An interface which is suitable for the ADSP-2101 or the ADSP2102 is shown in Figure 17. The interface is configured for synchronous, continuous clock operation. The LDAC is tied low so the DAC gets updated on the sixteenth falling clock after TFS goes low. Alternatively LDAC may be driven from a timer as shown in Figure 16. As with the previous interface the processor receives an interrupt after reading or writing to the AD7868 and updates its own internal registers in preparation for the next data transfer. TIMER CONVST CONTROL – 5V Asynchronous* Synchronous Gated Clock 5 or 6 3 RCLK, DR, DT and RFS (TCLK = RCLK, TFS = RFS) RCLK, DR, RFS, DT, TFS (TCLK = RCLK or µP serial CLK) RCLK, DR and DT (TCLK = RCLK, TFS = RFS) ADSP-2101/ ADSP-2102 + 5V AD7868* 4.7kΩ RFS SCLK DR TFS *5 LINES OF INTERCONNECT WHEN TCLK = RCLK 6 LINES OF INTERCONNECT WHEN TCLK = µP SERIAL CLK 2kΩ 4.7kΩ RFS RCLK DR TFS TCLK DT DT AD7868—DSP56000 Interface LDAC Figure 16 shows a typical interface between the AD7868 and DSP56000. The interface arrangement is synchronous with a gated clock requiring only three lines of interconnect. The REV. B *ADDITIONAL PINS OMITTED FOR CLARITY Figure 17. AD7868—ADSP-2101/ADSP-2102 Interface –11– AD7868 analog circuitry from digital noise. The circuit layout of Figures 22 and 23 have both analog and digital ground planes which are kept separated and only joined together at the AD7868 AGND pins. AD7868—TMS32020/TMS320C25 Interface Figure 18 shows an interface which is suitable for the TMS32020/TMS320C25 processors. This interface is configured for synchronous, continuous clock operation. Note, the AD7868 will not interface correctly to these processors if the AD7868 is configured for a noncontinuous clock. Conversion starts and DAC updating are controlled by an external timer. NOISE Keep the input signal leads to VIN and signal return leads from AGND as short as possible to minimize input noise coupling. In applications where this is not possible, use a shielded cable between the source and the ADC. Reduce the ground circuit impedance as much as possible since any potential difference in grounds between the signal source and the ADC appears as an error voltage in series with the input signal. CONVST TIMER LDAC – 5V TMS32020 TMS320C25 CONTROL + 5V AD7868* 4.7kΩ FSR CLKR 2kΩ RCLK DR FSX TFS DX Figure 19 shows an analog I/O board based on the AD7868. The corresponding printed circuit board (PCB) layout and silkscreen are shown in Figures 21 to 23. RFS DR CLKX INPUT/OUTPUT BOARD 4.7kΩ The analog input to the AD7868 is buffered with an AD711 op amp. There is a component grid provided near the analog input on the PCB which may be used for an antialiasing filter for the ADC or a reconstruction filter for the DAC or any other conditioning circuitry. To facilitate this option, there are two wire links (labeled LK1 and LK2) required on the analog input and output tracks. TCLK DT *ADDITIONAL PINS OMITTED FOR CLARITY Figure 18. AD7868—TMS32020/TMS320C25 Interface APPLICATION HINTS Good printed circuit board (PCB) layout is as important as the circuit design itself in achieving high speed A/D performance. The AD7868’s comparator is required to make bit decisions on an LSB size of 1.465 mV. To achieve this, the designer has to be conscious of noise both in the ADC itself and in the preceding analog circuitry. Switching mode power supplies are not recommended as the switching spikes will feed through to the comparator causing noisy code transitions. Other causes of concern are ground loops and digital feedthrough from microprocessors. These are factors which influence any ADC, and a proper PCB layout which minimizes these effects is essential for best performance. LAYOUT HINTS Ensure that the layout for the printed circuit board has the digital and analog signal lines separated as much as possible. Take care not to run any digital track alongside an analog signal track. Guard (screen) the analog input with AGND. Establish a single point analog ground (star ground) separate from the logic system ground as close as possible to the AD7868 AGND pins. Connect all other grounds and the AD7868 DGND to this single analog ground point. Do not connect any other digital grounds to this analog ground point. Low impedance analog and digital power supply common returns are essential to low noise operation of the ADC, so make the foil width for these tracks as wide as possible. The use of ground planes minimizes impedance paths and also guards the The board contains a SHA circuit which can be used on the output of the AD7868 DAC to extend the very good performance of the part over a wider frequency range. The increased performance from the SHA can be seen in Figures 14 and 15 of this data sheet. A wire link (labeled LK3) connects the board output to either the SHA output or directly to the AD7868 DAC output. There are three LDAC link options on the board; LDAC can be driven from an external source independent of CONVST, LDAC can be tied to CONVST or LDAC can be tied to GND. Choosing the latter option of tying LDAC to GND disables the SHA operation, and places the SHA permanently in the track mode. Microprocessor connections to the board are made by a 9-way D-type connector. The pinout is shown in Figure 20. The ADC’s digital outputs are buffered with 74HC4050s. These buffers provide a higher current output capability for high capacitance loads or cables. Normally, these buffers are not required as the AD7868 will be sitting on the same board as the processor. POWER SUPPLY CONNECTIONS The PCB requires two analog power supplies and one 5 V digital supply. Connections to the analog supply are made directly to the PCB as shown on the silkscreen in Figure 21. The connections are labeled V+ and V– and the range for both of these supplies is 12 V to 15 V. Connections to the 5 V digital supply are made through the D-type connector SKT6. The ± 5 V analog supply required by the AD7868 are generated from two voltage regulators on the V+ and V– supplies. –12– REV. B AD7868 5V V+ IN ANALOG INPUT ±3V RANGE GND C6 0.1µF VDD LK1 A B IC2 C VDD R7 200 AD711 + SKT1 C1 10µF C2 0.1µF IC5 78L05 V+ C5 10µF OUT RO ADC VIN COMPONENT GRID RI DAC C7 10µF C8 0.1µF C24 0.1µF A B V– LK4 C RO DAC IC1 AD7868 –5V A B CONTROL LK2 AGND SKT6 9-WAY D-TYPE CONNECTOR B C AGND B 5V A A C ANALOG OUTPUT ±3V RANGE LK5 C COMPONENT GRID SKT2 C23 10µF DGND LK3 V+ R3 4.7kΩ R5 4.7kΩ IC7 1/2 74HC4050 5V DR DGND C10 0.1µF R4 2kΩ DR C9 10µF RCLK RCLK AD711 IC4 ADG201HS + RFS RFS R1 2kΩ IC3 LK9 VOUT V– LK8 C12 0.1µF TFS C11 10µF TFS TCLK TCLK C21 330pF DT DT R2 2kΩ DGND CLK 5V LDAC R6 15k VCC CONVST Q VSS REXT /C EXT C22 68pF VSS A CEXT –5V B IC8 1/2 74HC221 OUT 5V C4 0.1µF CLR C GND A C3 10µF B IC6 79L05 IN V– A B C LK7 –5V GND LK6 SKT3 SKT4 CONVST LDAC SKT5 EXT CLK RCLK DR 4 5 6 7 8 9 5V DT 3 NC RFS 2 TFS 1 DGND TCLK Figure 19. Input/Output Circuit Based on the AD7868 WIRE LINK OPTIONS LK1, Analog Input Link LK1 connects the analog input to a component grid or to a buffer amplifier which drives the ADC input. LK2, Analog Output Link LK2 connects the analog output to the component grid or to either the SHA or DAC output (see LK3). NC = NO CONNECT LK3, SHA or DAC Select Figure 20. SKT6, D-Type Connector Pinout REV. B The analog output may be taken directly from the DAC or from a SHA at the output of the DAC. –13– AD7868 LK4, DAC Reference Selection COMPONENT LIST The DAC reference may be connected to either the ADC reference output (RO ADC) or to the DAC reference (RO DAC). IC1 IC2, IC3 IC4, IC5, IC6, IC7, IC8, AD7868 2X AD711 ADG201HS MC78L05 MC79L05 74HC4050 74HC221 C1, C3, C5, C7 C9, C11, C13, C15 C17, C19, C23 10 µF Capacitor C2, C4, C6, C8 C10, C12, C14, C16 C18, C20, C24 0.1 µF Capacitor C21 C22 330 pF Capacitor 68 pF Capacitor R1, R2, R4 R3, R5 2 kΩ Resistor 4.7 kΩ Resistor R6 R7 15 kΩ Resistor 200 Ω Resistor LK5, ADC Internal Clock Selection This link configures the ADC for continuous or noncontinuous internal clock operation. LK6, DAC Updating The DAC, LDAC input may asserted independently of the ADC CONVST signal or it may be tied to CONVST or it may tied to GND. LK7, ADC Clock Source This link provides the option for the ADC to use its own internal clock oscillator or an external TTL compatible clock. LK8 Frame Synchronous Option LK8 provides the option of tying the ADC RFS output to the DAC TFS input. LK9 Transmit/Receive Clock Option LK9 provides the option to connect the ADC RCLK to the DAC TCLK. LK1, LK2, LK3, LK4, LK5, LK6, LK7, LK8 LK9 Shorting Plugs SKT1, SKT2, SKT3, SKT4, SKT5 BNC Sockets SKT6 9-Contact D-Type Connector Figure 21. Silkscreen for the Circuit Diagram of Figure 19 –14– REV. B AD7868 Figure 22. Component Side Layout for the Circuit Diagram of Figure 19 Figure 23. Solder Side Layout for the Circuit Diagram of Figure 19 REV. B –15– AD7868 OUTLINE DIMENSIONS Dimensions shown in inches and (mm). 24-Pin Plastic (N-24) C1410–10–7/90 24-Pin Cerdip (Q-24) PRINTED IN U.S.A. 28-Pin Plastic SOIC (R-28) –16– REV. B