1 MHz to 10 GHz, 55 dB
Log Detector/Controller
AD8317
Data Sheet
FEATURES
FUNCTIONAL BLOCK DIAGRAM
APPLICATIONS
VPOS
GAIN
BIAS
DET
DET
DET
TADJ
SLOPE
I
V
VSET
I
V
VOUT
DET
CLPF
INHI
INLO
COMM
RF transmitter PA setpoint control and level monitoring
Power monitoring in radio link transmitters
RSSI measurement in base stations, WLANs, WiMAX, and radars
05541-001
Wide bandwidth: 1 MHz to 10 GHz
High accuracy: ±1.0 dB over temperature
55 dB dynamic range up to 8 GHz ± 3 dB error
Stability over temperature: ±0.5 dB
Low noise measurement/controller output, VOUT
Pulse response time: 6 ns/10 ns (fall/rise)
Small footprint, 2 mm × 3 mm LFCSP
Supply operation: 3.0 V to 5.5 V at 22 mA
Fabricated using high speed SiGe process
Figure 1.
GENERAL DESCRIPTION
The AD8317 is a demodulating logarithmic amplifier, capable
of accurately converting an RF input signal to a corresponding
decibel-scaled output. It employs the progressive compression
technique over a cascaded amplifier chain, each stage of which
is equipped with a detector cell. The device can be used in either
measurement or controller modes. The AD8317 maintains
accurate log conformance for signals of 1 MHz to 8 GHz and
provides useful operation to 10 GHz. The input dynamic range
is typically 55 dB (referenced to 50 Ω) with less than ±3 dB
error. The AD8317 has 6 ns/10 ns response time (fall time/rise
time) that enables RF burst detection to a pulse rate of beyond
50 MHz. The device provides unprecedented logarithmic intercept
stability vs. ambient temperature conditions. A supply of 3.0 V
to 5.5 V is required to power the device. Current consumption is
typically 22 mA, and it decreases to 200 μA when the device is
disabled.
The feedback loop through an RF amplifier is closed via VOUT,
the output of which regulates the output of the amplifier to a
magnitude corresponding to VSET. The AD8317 provides 0 V to
(VPOS − 0.1 V) output capability at the VOUT pin, suitable for
controller applications. As a measurement device, VOUT is
externally connected to VSET to produce an output voltage,
VOUT, that is a decreasing linear-in-dB function of the RF input
signal amplitude.
The logarithmic slope is 22 mV/dB, determined by the VSET
interface. The intercept is 15 dBm (referenced to 50 Ω, CW
input) using the INHI input. These parameters are very stable
against supply and temperature variations.
The AD8317 is fabricated on a SiGe bipolar IC process and is
available in a 2 mm × 3 mm, 8-lead LFCSP with an operating
temperature range of −40°C to +85°C.
The AD8317 can be configured to provide a control voltage to a
power amplifier or a measurement output from the VOUT pin.
Because the output can be used for controller applications, special
attention has been paid to minimize wideband noise. In this
mode, the setpoint control voltage is applied to the VSET pin.
Rev. D
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Tel: 781.329.4700 ©2005–2019 Analog Devices, Inc. All rights reserved.
Technical Support
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AD8317
Data Sheet
TABLE OF CONTENTS
Features .............................................................................................. 1
Input Signal Coupling ................................................................ 11
Applications ....................................................................................... 1
Output Interface ......................................................................... 11
Functional Block Diagram .............................................................. 1
Setpoint Interface ....................................................................... 11
General Description ......................................................................... 1
Temperature Compensation of Output Voltage ..................... 12
Revision History ............................................................................... 2
Measurement Mode ................................................................... 12
Specifications..................................................................................... 3
Setting the Output Slope in Measurement Mode .................. 13
Absolute Maximum Ratings............................................................ 5
Controller Mode ......................................................................... 13
ESD Caution .................................................................................. 5
Output Filtering .......................................................................... 15
Pin Configuration and Function Descriptions ............................. 6
Operation Beyond 8 GHz ......................................................... 15
Typical Performance Characteristics ............................................. 7
Evaluation Board ............................................................................ 16
Theory of Operation ...................................................................... 10
Die Information .............................................................................. 18
Using the AD8317 .......................................................................... 11
Outline Dimensions ....................................................................... 19
Basic Connections ...................................................................... 11
Ordering Guide .......................................................................... 19
REVISION HISTORY
9/2019—Rev. C to Rev. D
Changes to Table 6 .......................................................................... 18
Updated Outline Dimensions ....................................................... 19
8/2017—Rev. B to Rev. C
Change to Figure 2 and Table 3 ...................................................... 6
Updated Outline Dimensions ....................................................... 19
Changes to Ordering Guide ......................................................... 19
3/2008—Rev. A to Rev. B
Changes to Features.......................................................................... 1
Changes to General Description .................................................... 1
Changes to Measurement Mode Section ..................................... 12
Changes to Equation 12 ................................................................. 15
8/2007—Rev. 0 to Rev. A
Changes to f = 8.0 GHz, ±1 dB Dynamic Range Parameter ........4
Changes to Table 2.............................................................................6
Changes to Figure 20...................................................................... 10
Changes to Setpoint Interface Section and Figure 22 ................ 12
Changes Figure 27 .......................................................................... 13
Changes to Table 5.......................................................................... 17
Added Die Information Section ................................................... 19
Changes to Ordering Guide .......................................................... 21
10/2005—Revision 0: Initial Version
Rev. D | Page 2 of 19
Data Sheet
AD8317
SPECIFICATIONS
VPOS = 3 V, CLPF = 1000 pF, TA = 25°C, 52.3 Ω termination resistor at INHI, unless otherwise noted.
Table 1.
Parameter
SIGNAL INPUT INTERFACE
Specified Frequency Range
DC Common-Mode Voltage
MEASUREMENT MODE
f = 900 MHz
Input Impedance
±1 dB Dynamic Range
Maximum Input Level
Minimum Input Level
Slope1
Intercept1
Output Voltage, High Power In
Output Voltage, Low Power In
f = 1.9 GHz
Input Impedance
±1 dB Dynamic Range
Maximum Input Level
Minimum Input Level
Slope1
Intercept1
Output Voltage, High Power In
Output Voltage, Low Power In
f = 2.2 GHz
Input Impedance
±1 dB Dynamic Range
Maximum Input Level
Minimum Input Level
Slope1
Intercept1
Output Voltage, High Power In
Output Voltage, Low Power In
f = 3.6 GHz
Input Impedance
±1 dB Dynamic Range
Maximum Input Level
Minimum Input Level
Slope1
Intercept1
Output Voltage, High Power In
Output Voltage, Low Power In
Conditions
INHI (Pin 1)
Min
Typ
Max
Unit
10
VPOS − 0.6
GHz
V
−25
12
0.42
1.00
1500||0.33
50
46
−3
−53
−22
15
0.58
1.27
−19.5
21
0.78
1.40
Ω||pF
dB
dB
dBm
dBm
mV/dB
dBm
V
V
−25
10
0.35
0.75
950||0.38
50
48
−4.00
−54
−22
14
0.54
1.21
−19.5
20
0.80
1.35
Ω||pF
dB
dB
dBm
dBm
mV/dB
dBm
V
V
0.001
VOUT (Pin 5) shorted to VSET (Pin 4), sinusoidal
input signal
RTADJ = 18 kΩ
TA = 25°C
−40°C < TA < +85°C
±1 dB error
±1 dB error
PIN = −10 dBm
PIN = −40 dBm
RTADJ = 8 kΩ
TA = 25°C
−40°C < TA < +85°C
±1 dB error
±1 dB error
PIN = −10 dBm
PIN = −35 dBm
RTADJ = 8 kΩ
TA = 25°C
−40°C < TA < +85°C
±1 dB error
±1 dB error
PIN = −10 dBm
PIN = −40 dBm
RTADJ = 8 kΩ
TA = 25°C
−40°C < TA < +85°C
±1 dB error
±1 dB error
PIN = −10 dBm
PIN = −40 dBm
Rev. D | Page 3 of 19
810||0.39
50
47
−5
−55
−22
14
0.53
1.20
Ω||pF
dB
dB
dBm
dBm
mV/dB
dBm
V
V
300||0.33
42
40
−6
−48
−22
11
0.47
1.16
Ω||pF
dB
dB
dBm
dBm
mV/dB
dBm
V
V
AD8317
Parameter
f = 5.8 GHz
Input Impedance
±1 dB Dynamic Range
Maximum Input Level
Minimum Input Level
Slope1
Intercept1
Output Voltage, High Power In
Output Voltage, Low Power In
f = 8.0 GHz
Input Impedance
±1 dB Dynamic Range
Maximum Input Level
Minimum Input Level
Slope2
Intercept2
Output Voltage, High Power In
Output Voltage, Low Power In
OUTPUT INTERFACE
Voltage Swing
Output Current Drive
Small Signal Bandwidth
Output Noise
Fall Time
Rise Time
Video Bandwidth (or Envelope Bandwidth)
VSET INTERFACE
Nominal Input Range
Data Sheet
Conditions
RTADJ = 500 Ω
Min
TA = 25°C
−40°C < TA < +85°C
±1 dB error
±1 dB error
PIN = −10 dBm
PIN = −40 dBm
RTADJ = open
TA = 25°C
−40°C < TA < +85°C
±1 dB error
±1 dB error
PIN = −10 dBm
PIN = −40 dBm
VOUT (Pin 5)
VSET = 0 V, RFIN = open
VSET = 1.7 V, RFIN = open
VSET = 0 V, RFIN = open
RFIN = −10 dBm, from CLPF to VOUT
RFIN = 2.2 GHz, −10 dBm, fNOISE = 100 kHz,
CLPF = open
Input level = no signal to −10 dBm, 90% to 10%,
CLPF = 8 pF
Input level = no signal to −10 dBm, 90% to 10%,
CLPF = open, ROUT = 150 Ω
Input level = −10 dBm to no signal, 10% to 90%,
CLPF = 8 pF
Input level = −10 dBm to no signal, 10% to 90%,
CLPF = open, ROUT = 150 Ω
VSET (Pin 4)
RFIN = 0 dBm, measurement mode
RFIN = −50 dBm, measurement mode
Typ
Ω||pF
dB
dB
dBm
dBm
mV/dB
dBm
V
V
28||0.79
44
35
−2
−46
−22
21
0.70
1.39
Ω||pF
dB
dB
dBm
dBm
mV/dB
dBm
V
V
VPOS − 0.1
10
10
140
90
V
mV
mA
MHz
nV/√Hz
18
ns
6
ns
20
ns
10
ns
50
MHz
V
V
dB/V
kΩ
kΩ
V
RFIN = −20 dBm, controller mode, VSET = 1 V
TADJ INTERFACE
Input Resistance
Disable Threshold Voltage
TADJ (Pin 6)
TADJ = 0.9 V, sourcing 50 μA
TADJ = open
13
VPOS − 0.4
POWER INTERFACE
Supply Voltage
Quiescent Current
vs. Temperature
Disable Current
VPOS (Pin 7)
1
2
3.0
18
−40°C ≤ TA ≤ +85°C
TADJ = VPOS
22
60
200
5.5
30
Slope and intercept are determined by calculating the best-fit line between the power levels of −40 dBm and −10 dBm at the specified input frequency.
Slope and intercept are determined by calculating the best-fit line between the power levels of −34 dBm and −16 dBm at 8.0 GHz.
Rev. D | Page 4 of 19
Unit
110||0.05
50
48
−4
−54
−22
16
0.59
1.27
0.35
1.40
−45
40
Logarithmic Scale Factor
Input Resistance
Max
V
mA
μA/°C
μA
Data Sheet
AD8317
ABSOLUTE MAXIMUM RATINGS
Table 2.
Parameter
Supply Voltage, VPOS
VSET Voltage
Input Power (Single-Ended, Referenced
to 50 Ω)
Internal Power Dissipation
θJA
Maximum Junction Temperature
Operating Temperature Range
Storage Temperature Range
Lead Temperature (Soldering, 60 sec)
Rating
5.7 V
0 V to VPOS
12 dBm
0.73 W
55°C/W
125°C
−40°C to +85°C
−65°C to +150°C
260°C
Stresses at or above those listed under Absolute Maximum
Ratings may cause permanent damage to the product. This is a
stress rating only; functional operation of the product at these
or any other conditions above those indicated in the
operational section of this specification is not implied.
Operation beyond the maximum operating conditions for
extended periods may affect product reliability.
ESD CAUTION
Rev. D | Page 5 of 19
AD8317
Data Sheet
PIN CONFIGURATION AND FUNCTION DESCRIPTIONS
8 INLO
AD8317
7 VPOS
CLPF 3
TOP VIEW
(Not to Scale)
6 TADJ
VSET 4
5 VOUT
NOTES
1. EXPOSED PAD MUST BE
CONNECTED TO GROUND VIA
A LOW IMPEDANCE PATH.
05541-002
INHI 1
COMM 2
Figure 2. Pin Configuration
Table 3. Pin Function Descriptions
Pin No.
1
2
3
Mnemonic
INHI
COMM
CLPF
4
5
VSET
VOUT
6
TADJ
7
8
VPOS
INLO
EPAD
Description
RF Input. Nominal input range of −50 dBm to 0 dBm, referenced to 50 Ω; ac-coupled RF input.
Device Common. Connect to a low impedance ground plane.
Loop Filter Capacitor. In measurement mode, this capacitor sets the pulse response time and video bandwidth.
In controller mode, the capacitance on this node sets the response time of the error amplifier/integrator.
Setpoint Control Input for Controller Mode or Feedback Input for Measurement Mode.
Measurement and Controller Output. In measurement mode, VOUT provides a decreasing linear-in-dB
representation of the RF input signal amplitude. In controller mode, VOUT is used to control the gain of a VGA or
VVA with a positive gain sense (increasing voltage increases gain).
Temperature Compensation Adjustment. Frequency-dependent temperature compensation is set by connecting
a ground-referenced resistor to this pin.
Positive Supply Voltage: 3.0 V to 5.5 V.
RF Common for INHI. AC-coupled RF common.
Exposed Pad. Exposed pad must be connected to ground via a low impedance path.
Rev. D | Page 6 of 19
Data Sheet
AD8317
TYPICAL PERFORMANCE CHARACTERISTICS
1.75
1.5
1.75
1.5
1.50
1.0
1.50
1.0
1.25
0.5
1.25
0.5
1.00
0
1.00
0
0.75
–0.5
0.75
–0.5
0.50
–1.0
0.50
–1.0
0.25
–1.5
0.25
–1.5
0
–60 –55 –50 –45 –40 –35 –30 –25 –20 –15 –10 –5
PIN (dBm)
–2.0
Figure 6. VOUT and Log Conformance vs. Input Amplitude at 3.6 GHz,
RTADJ = 8 kΩ
2.00
2.0
1.75
1.5
1.75
1.5
1.50
1.0
1.50
1.0
1.25
0.5
1.25
0.5
1.00
0
1.00
0
0.75
–0.5
0.75
–0.5
0.50
–1.0
0.50
–1.0
0.25
–1.5
0.25
–1.5
0
–60 –55 –50 –45 –40 –35 –30 –25 –20 –15 –10 –5
0
5
–2.0
PIN (dBm)
VOUT (V)
2.0
ERROR (dB)
2.00
0
–60 –55 –50 –45 –40 –35 –30 –25 –20 –15 –10 –5
05541-004
VOUT (V)
5
PIN (dBm)
Figure 3. VOUT and Log Conformance vs. Input Amplitude at 900 MHz,
RTADJ = 18 kΩ
0
5
–2.0
PIN (dBm)
Figure 4. VOUT and Log Conformance vs. Input Amplitude at 1.9 GHz,
RTADJ = 8 kΩ
Figure 7. VOUT and Log Conformance vs. Input Amplitude at 5.8 GHz,
RTADJ = 500 Ω
2.00
2.0
1.75
1.5
1.75
1.5
1.50
1.0
1.50
1.0
1.25
0.5
1.25
0.5
1.00
0
1.00
0
0.75
–0.5
0.75
–0.5
0.50
–1.0
0.50
–1.0
0.25
–1.5
0.25
–1.5
0
–60 –55 –50 –45 –40 –35 –30 –25 –20 –15 –10 –5
–2.0
0
5
VOUT (V)
2.0
ERROR (dB)
2.00
05541-005
VOUT (V)
0
ERROR (dB)
–2.0
05541-007
5
0
–60 –55 –50 –45 –40 –35 –30 –25 –20 –15 –10 –5
0
5
–2.0
PIN (dBm)
PIN (dBm)
Figure 5. VOUT and Log Conformance vs. Input Amplitude at 2.2 GHz,
RTADJ = 8 kΩ
Figure 8. VOUT and Log Conformance vs. Input Amplitude at 8.0 GHz,
RTADJ = Open, Error Calculated from PIN = −34 dBm to PIN = −16 dBm
Rev. D | Page 7 of 19
ERROR (dB)
0
05541-008
0
–60 –55 –50 –45 –40 –35 –30 –25 –20 –15 –10 –5
ERROR (dB)
2.0
05541-006
2.00
VOUT (V)
2.0
ERROR (dB)
2.00
05541-003
VOUT (V)
VPOS = 3 V; TA = +25°C, −40°C, +85°C; CLPF = 1000 pF, unless otherwise noted. Black: +25°C; Blue: −40°C; Red: +85°C. Error is calculated
by using the best-fit line between PIN = −40 dBm and PIN = −10 dBm at the specified input frequency, unless otherwise noted
2.00
2.0
1.75
1.5
1.75
1.5
1.50
1.0
1.50
1.0
1.25
0.5
1.25
0.5
1.00
0
1.00
0
0.75
–0.5
0.75
–0.5
0.50
–1.0
0.50
–1.0
0.25
–1.5
0.25
–1.5
0
–60 –55 –50 –45 –40 –35 –30 –25 –20 –15 –10 –5
PIN (dBm)
10
–2.0
Figure 12. VOUT and Log Conformance vs. Input Amplitude at 3.6 GHz,
Multiple Devices, RTADJ = 8 kΩ
2.00
2.0
1.75
1.5
1.75
1.5
1.50
1.0
1.50
1.0
1.25
0.5
1.25
0.5
1.00
0
1.00
0
0.75
–0.5
0.75
–0.5
0.50
–1.0
0.50
–1.0
0.25
–1.5
0.25
–1.5
0
–60 –55 –50 –45 –40 –35 –30 –25 –20 –15 –10 –5
–2.0
0
5
VOUT (V)
2.0
ERROR (dB)
2.00
0
–60 –55 –50 –45 –40 –35 –30 –25 –20 –15 –10 –5
05541-010
VOUT (V)
5
PIN (dBm)
Figure 9. VOUT and Log Conformance vs. Input Amplitude at 900 MHz,
Multiple Devices, RTADJ = 18 kΩ
10
PIN (dBm)
–2.0
0
5
10
PIN (dBm)
Figure 10. VOUT and Log Conformance vs. Input Amplitude at 1.9 GHz,
Multiple Devices, RTADJ = 8 kΩ
Figure 13. VOUT and Log Conformance vs. Input Amplitude at 5.8 GHz,
Multiple Devices, RTADJ = 500 Ω
2.00
2.0
1.75
1.5
1.75
1.5
1.50
1.0
1.50
1.0
1.25
0.5
1.25
0.5
1.00
0
1.00
0
0.75
–0.5
0.75
–0.5
0.50
–1.0
0.50
–1.0
0.25
–1.5
0.25
–1.5
0
–60 –55 –50 –45 –40 –35 –30 –25 –20 –15 –10 –5
0
5
–2.0
VOUT (V)
2.0
ERROR (dB)
2.00
0
–60 –55 –50 –45 –40 –35 –30 –25 –20 –15 –10 –5
05541-011
VOUT (V)
0
05541-012
–2.0
PIN (dBm)
Figure 11. VOUT and Log Conformance vs. Input Amplitude at 2.2 GHz,
Multiple Devices, RTADJ = 8 kΩ
ERROR (dB)
10
05541-013
5
0
5
ERROR (dB)
0
–2.0
10
PIN (dBm)
Figure 14. VOUT and Log Conformance vs. Input Amplitude at 8.0 GHz,
Multiple Devices, RTADJ = Open,
Error Calculated from PIN = −34 dBm to PIN = −16 dBm
Rev. D | Page 8 of 19
05541-014
0
–60 –55 –50 –45 –40 –35 –30 –25 –20 –15 –10 –5
VOUT (V)
2.0
ERROR (dB)
2.00
ERROR (dB)
Data Sheet
05541-009
VOUT (V)
AD8317
Data Sheet
AD8317
j1
10000
j0.2
1
2
100MHz
–j0.2
900MHz
1900MHz
8000MHz
–j2
–j0.5
–20dBm
–10dBm
100
0dBm
2200MHz
10
1k
3600MHz
5800MHz
10000
NOISE SPECTRAL DENSITY (nV/ Hz)
Δ : 1.86V
@ : 1.69V
05541-017
3
Ch3 500mV Ch4 200mV
M4.00µs
A Ch3
T
12.7560µs
1000
100
10
1k
620mV
10k
100k
10M
1M
FREQUENCY (Hz)
Figure 19. Noise Spectral Density of Output Buffer (from CLPF to VOUT);
CLPF = 0.1 μF
Figure 16. Power-On/Power-Off Response Time; VPOS = 3.0 V;
Input AC-Coupling Capacitors = 10 pF; CLPF = Open
VOUT (V)
CH1 RISE
10.44ns
05541-016
CH1 FALL
6.113ns
M20.0ns
A CH1
T
943.600ns
10M
1M
Figure 18. Noise Spectral Density of Output; CLPF = Open
Figure 15. Input Impedance vs. Frequency; No Termination Resistor on INHI
(Impedance De-Embedded to Input Pins), Z0 = 50 Ω
CH1 200mV
100k
FREQUENCY (Hz)
05541-015
10000MHz
4
10k
–j1
START FREQUENCY = 0.05GHz
STOP FREQUENCY = 10GHz
RF OFF
2.00
2.0
1.75
1.5
1.50
1.0
1.25
0.5
1.00
0
0.75
–0.5
0.50
–1.0
0.25
1.40V
0
–65
Figure 17. VOUT Pulse Response Time; Pulsed RF Input 0.1 GHz, −10 dBm;
CLPF = Open; RLOAD = 150 Ω
Rev. D | Page 9 of 19
3.3V
3.0V
3.6V
–55
ERROR (dB)
0.5
–40dBm
–1.5
–45
–35
–25
–15
PIN (dBm)
–5
5
15
–2.0
Figure 20. Output Voltage Stability vs. Supply Voltage at 1.9 GHz
When VPOS Varies by 10%
05541-020
0.2
1000
05541-019
0
–60dBm
05541-018
NOISE SPECTRAL DENSITY (nV/ Hz)
j2
j0.5
AD8317
Data Sheet
THEORY OF OPERATION
The AD8317 is a 6-stage demodulating logarithmic amplifier,
specifically designed for use in RF measurement and power
control applications at frequencies up to 10 GHz. A block
diagram is shown in Figure 21. Sharing much of its design
with the AD8318 logarithmic detector/controller, the AD8317
maintains tight intercept variability vs. temperature over a 50 dB
range. Additional enhancements over the AD8318, such as a
reduced RF burst response time of 6 ns to 10 ns, 22 mA supply
current, and board space requirements of only 2 mm × 3 mm,
add to the low cost and high performance benefits of the AD8317.
VPOS
GAIN
BIAS
DET
DET
DET
TADJ
SLOPE
V
I
VSET
I
V
VOUT
DET
CLPF
INHI
COMM
05541-021
INLO
Figure 21. Block Diagram
A fully differential design, using a proprietary, high speed SiGe
process, extends high frequency performance. Input INHI receives
the signal with a low frequency impedance of nominally 500 Ω in
parallel with 0.7 pF. The maximum input with ±1 dB logconformance error is typically 0 dBm (referenced to 50 Ω). The
noise spectral density referred to the input is 1.15 nV/Hz,
which is equivalent to a voltage of 118 μV rms in a 10.5 GHz
bandwidth or a noise power of −66 dBm (referenced to 50 Ω).
This noise spectral density sets the lower limit of the dynamic
range. However, the low end accuracy of the AD8317 is
enhanced by specially shaping the demodulating transfer
characteristic to partially compensate for errors due to internal
noise. The common pin, COMM, provides a quality low
impedance connection to the printed circuit board (PCB)
ground. The package paddle, which is internally connected to the
COMM pin, must also be grounded to the PCB to reduce thermal
impedance from the die to the PCB.
The logarithmic function is approximated in a piecewise
fashion by six cascaded gain stages. (For a more comprehensive
explanation of the logarithm approximation, see the AD8307
data sheet.) The cells have a nominal voltage gain of 9 dB each
and a 3 dB bandwidth of 10.5 GHz. Using precision biasing, the
gain is stabilized over temperature and supply variations. The
overall dc gain is high, due to the cascaded nature of the gain
stages. An offset compensation loop is included to correct for
offsets within the cascaded cells. At the output of each of the
gain stages, a square-law detector cell is used to rectify the signal.
The RF signal voltages are converted to a fluctuating differential
current having an average value that increases with signal level.
Along with the six gain stages and detector cells, an additional
detector is included at the input of the AD8317, providing a
50 dB dynamic range in total. After the detector currents are
summed and filtered, the following function is formed at the
summing node:
ID × log10(VIN/VINTERCEPT)
(1)
where:
ID is the internally set detector current.
VIN is the input signal voltage.
VINTERCEPT is the intercept voltage (that is, when VIN = VINTERCEPT,
the output voltage would be 0 V, if it were capable of going to 0 V).
Rev. D | Page 10 of 19
Data Sheet
AD8317
USING THE AD8317
The AD8317 is specified for operation up to 10 GHz; as a result,
low impedance supply pins with adequate isolation between
functions are essential. A power supply voltage of between 3.0 V
and 5.5 V must be applied to VPOS. Power supply decoupling
capacitors of 100 pF and 0.1 μF must be connected close to this
power supply pin.
VS (3.0V TO 5.5V)
C5
0.1µF
R2
0Ω
C4
100pF
C2
VOUT
8
INLO
7
VPOS
R1
52.3Ω
6
TADJ
5
VOUT
R4
0Ω
AD8317
INHI
1
C1
SIGNAL
INPUT
COMM
2
CLPF
3
47nF
VSET
4
2
1SEE THE TEMPERATURE COMPENSATION OF OUTPUT VOLTAGE SECTION.
2SEE THE OUTPUT FILTERING SECTION.
05541-022
47nF
1
Figure 22. Basic Connections
Figure 22) combines with the relatively high input impedance to
give an adequate broadband 50 Ω match.
The coupling time constant, 50 × CC/2, forms a high-pass
corner with a 3 dB attenuation at fHP = 1/(2π × 50 × CC ), where
C1 = C2 = CC. Using the typical value of 47 nF, this high-pass
corner is ~68 kHz. In high frequency applications, fHP must be
as large as possible to minimize the coupling of unwanted low
frequency signals. In low frequency applications, add a simple
RC network forming a low-pass filter at the input for similar
reasons. This low-pass filter network must generally be placed at
the generator side of the coupling capacitors, thereby lowering the
required capacitance value for a given high-pass corner
frequency.
OUTPUT INTERFACE
The VOUT pin is driven by a PNP output stage. An internal
10 Ω resistor is placed in series with the output and the VOUT
pin. The rise time of the output is limited mainly by the slew
on CLPF. The fall time is an RC-limited slew given by the load
capacitance and the pull-down resistance at VOUT. There is an
internal pull-down resistor of 1.6 kΩ. A resistive load at VOUT
is placed in parallel with the internal pull-down resistor to
provide additional discharge current.
The paddle of the LFCSP package is internally connected to
COMM. For optimum thermal and electrical performance, the
paddle must be soldered to a low impedance ground plane.
VPOS
CLPF
10Ω
+
0.8V
–
INPUT SIGNAL COUPLING
The RF input (INHI) is single-ended and must be ac-coupled.
The INLO (input common) must be ac-coupled to ground.
Suggested coupling capacitors are 47 nF ceramic 0402-style
capacitors for input frequencies of 1 MHz to 10 GHz. The
coupling capacitors must be mounted close to the INHI and
INLO pins. The coupling capacitor values can be increased to
lower the high-pass cutoff frequency of the input stage. The
high-pass corner is set by the input coupling capacitors and the
internal 10 pF high-pass capacitor. The dc voltage on INHI and
INLO is approximately one diode voltage drop below VPOS.
CURRENT
VPOS
5pF
18.7kΩ
VOUT
1200Ω
05541-024
BASIC CONNECTIONS
400Ω
COMM
Figure 24. Output Interface
To reduce the fall time, load VOUT with a resistive load of