50 MHz, Precision, Low Distortion, Low Noise CMOS Amplifiers AD8651/AD8652
FEATURES
Bandwidth: 50 MHz @ 5 V Low noise: 4.5 nV/√Hz Offset voltage: 100 μV typical, specified over entire common-mode range Slew rate: 41 V/μs Rail-to-rail input and output swing Input bias current: 1 pA Single-supply operation: 2.7 V to 5.5 V Space-saving MSOP and SOIC_N packaging
NC 1 –IN 2 +IN 3 V–
4
PIN CONFIGURATIONS
8
AD8651
TOP VIEW (Not to Scale)
NC V+ OUT
03301-001
OUT A 1 –IN A 2 +IN A 3 V– 4
8
7 6 5
AD8652
TOP VIEW (Not to Scale)
V+ OUT B +IN B
03301-003
03301-004
7 6 5
–IN B
NC
NC = NO CONNECT
Figure 1. 8-Lead MSOP (RM-8)
NC 1 –IN 2
8
Figure 2. 8-Lead MSOP (RM-8)
OUT A 1 –IN A 2 +IN A 3 V+ OUT B
NC V+
AD8651
7
8
APPLICATIONS
Optical communications Laser source drivers/controllers Broadband communications High speed ADCs and DACs Microwave link interface Cell phone PA control Video line drivers Audio
+IN 3
NC = NO CONNECT
Figure 3. 8-Lead SOIC_N (R-8)
03301-002
6 OUT TOP VIEW V– 4 (Not to Scale) 5 NC
AD8652
7
6 –IN B TOP VIEW V– 4 (Not to Scale) 5 +IN B
Figure 4. 8-Lead SOIC_N (R-8)
GENERAL DESCRIPTION
The AD865x family consists of high precision, low noise, low distortion, rail-to-rail CMOS operational amplifiers that run from a single-supply voltage of 2.7 V to 5.5 V. The AD865x family is made up of rail-to-rail input and output amplifiers with a gain bandwidth of 50 MHz and a typical voltage offset of 100 μV across common mode from a 5 V supply. It also features low noise—4.5 nV/√Hz. The AD865x family can be used in communications applications, such as cell phone transmission power control, fiber optic networking, wireless networking, and video line drivers.
The AD865x family features the newest generation of DigiTrim® in-package trimming. This new generation measures and corrects the offset over the entire input common-mode range, providing less distortion from VOS variation than is typical of other rail-to-rail amplifiers. Offset voltage and CMRR are both specified and guaranteed over the entire common-mode range as well as over the extended industrial temperature range. The AD865x family is offered in the narrow 8-lead SOIC package and the 8-lead MSOP package. The amplifiers are specified over the extended industrial temperature range (−40°C to +125°C).
Rev. C
Information furnished by Analog Devices is believed to be accurate and reliable. However, no responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. Specifications subject to change without notice. No license is granted by implication or otherwise under any patent or patent rights of Analog Devices. Trademarks and registered trademarks are the property of their respective owners.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A. Tel: 781.329.4700 www.analog.com Fax: 781.461.3113 ©2006 Analog Devices, Inc. All rights reserved.
AD8651/AD8652 TABLE OF CONTENTS
Features .............................................................................................. 1 Applications....................................................................................... 1 Pin Configurations ........................................................................... 1 General Description ......................................................................... 1 Specifications..................................................................................... 3 Electrical Characteristics............................................................. 3 Absolute Maximum Ratings............................................................ 5 Thermal Resistance ...................................................................... 5 ESD Caution.................................................................................. 5 Typical Performance Characteristics ............................................. 6 Applications..................................................................................... 14 Theory of Operation .................................................................. 14 Rail-to-Rail Output Stage...................................................... 14 Rail-to-Rail Input Stage ......................................................... 14 Input Protection ..................................................................... 15 Overdrive Recovery ............................................................... 15 Layout, Grounding, and Bypassing Considerations .............. 15 Power Supply Bypassing........................................................ 15 Grounding............................................................................... 15 Leakage Currents.................................................................... 15 Input Capacitance .................................................................. 16 Output Capacitance ............................................................... 16 Settling Time........................................................................... 16 THD Readings vs. Common-Mode Voltage ...................... 16 Driving a 16-Bit ADC............................................................ 17 Outline Dimensions ....................................................................... 18 Ordering Guide .......................................................................... 19
REVISION HISTORY
8/06—Rev. B. to Rev. C Changes to Figure 1 to Figure 4 ...................................................... 1 Changes to Figure 7 and Figure 9................................................... 6 Changes to Figure 23........................................................................ 9 Changes to Figure 53...................................................................... 14 Updated Outline Dimensions ....................................................... 18 Changes to Ordering Guide .......................................................... 19 9/04—Rev. A to Rev. B Added AD8652 ....................................................................Universal Change to General Description ....................................................... 1 Changes to Electrical Characteristics ............................................. 3 Changes to Absolute Maximum Ratings ........................................ 5 Change to Figure 23 .......................................................................... 9 Change to Figure 26 .......................................................................... 9 Change to Figure 36 ........................................................................ 11 Change to Figure 42 ........................................................................ 12 Change to Figure 49 ........................................................................ 13 Change to Figure 51 ........................................................................ 13 Inserted Figure 52............................................................................ 13 Change to Theory of Operation section....................................... 14 Change to Input Protection section .............................................. 15 Changes to Ordering Guide ........................................................... 20 6/04—Rev. 0 to Rev. A Change to Figure 18 .............................................................................8 Change to Figure 21 .............................................................................9 Change to Figure 29 .............................................................................10 Change to Figure 30 .............................................................................10 Change to Figure 43 .............................................................................12 Change to Figure 44 .............................................................................12 Change to Figure 47 .............................................................................13 Change to Figure 57 .............................................................................17 10/03 Revision 0: Initial Version
Rev. C | Page 2 of 20
AD8651/AD8652 SPECIFICATIONS
ELECTRICAL CHARACTERISTICS
V+ = 2.7 V, V– = 0 V, VCM = V+/2, TA = 25°C, unless otherwise specified. Table 1.
Parameter
INPUT CHARACTERISTICS Offset Voltage AD8651
Symbol
VOS
Conditions
Min
Typ
Max
Unit
AD8652 Offset Voltage Drift Input Bias Current Input Offset Current TCVOS IB
0 V ≤ VCM ≤ 2.7 V –40°C ≤ TA ≤ +85°C, 0 V ≤ VCM ≤ 2.7 V –40°C ≤ TA ≤ +125°C, 0 V ≤ VCM ≤ 2.7 V 0 V ≤ VCM ≤ 2.7 V –40°C ≤ TA ≤ +125°C, 0 V ≤ VCM ≤ 2.7 V
100
90 0.4 4 1 1
350 1.4 1.6 300 1.3 10 600 10 30 600 +2.8
–40°C ≤ TA ≤ +125°C IOS –40°C ≤ TA ≤ +85°C –40°C ≤ TA ≤ +125°C Input Voltage Range Common-Mode Rejection Ratio AD8651 VCM CMRR V+ = 2.7 V, –0.1 V < VCM < +2.8 V –40°C ≤ TA ≤ +85°C, –0.1 V < VCM < +2.8 V –40°C ≤ TA ≤ +125°C, –0.1 V < VCM < +2.8 V V+ = 2.7 V, –0.1 V < VCM < +2.8 V –40°C ≤ TA ≤ +125°C, –0.1 V < VCM < +2.8 V RL = 1 kΩ, 200 mV < VO < 2.5 V RL = 1 kΩ, 200 mV < VO < 2.5 V, TA = 85°C RL = 1 kΩ, 200 mV < VO < 2.5 V, TA = 125°C IL = 250 μA, –40°C ≤ TA ≤ +125°C IL = 250 μA, –40°C ≤ TA ≤ +125°C Sourcing Sinking –0.1 75 70 65 77 73 100 100 95 2.67 95 88 85 95 90 115 114 108
μV mV mV μV mV μV/°C pA pA pA pA pA V dB dB dB dB dB dB dB dB V mV mA mA mA dB dB
AD8652 Large Signal Voltage Gain AVO
OUTPUT CHARACTERISTICS Output Voltage High Output Voltage Low Short-Circuit Limit Output Current POWER SUPPLY Power Supply Rejection Ratio Supply Current AD8651 AD8652 INPUT CAPACITANCE Differential Common Mode DYNAMIC PERFORMANCE Slew Rate Gain Bandwidth Product Settling Time, 0.01% Overload Recovery Time Total Harmonic Distortion + Noise NOISE PERFORMANCE Voltage Noise Density Current Noise Density
VOH VOL ISC IO PSRR ISY
30 80 80 40 76 74 94 93 9 17.5 12 14.5 19.5 22.5
VS = 2.7 V to 5.5 V, VCM = 0 V –40°C ≤ TA ≤ +125°C IO = 0 –40°C ≤ TA ≤ +125°C IO = 0 –40°C ≤ TA ≤ +125°C
mA mA mA mA pF pF V/μs MHz μs μs % nV/√Hz nV/√Hz fA/√Hz
CIN 6 9 SR GBP G = 1, RL = 10 kΩ G=1 G = ±1, 2 V step VIN × G = 1.48 V+ G = 1, RL = 600 Ω, f = 1 kHz, VIN = 2 V p-p f = 10 kHz f = 100 kHz f = 10 kHz 41 50 0.2 0.1 0.0006 5 4.5 4
THD + N en in
Rev. C | Page 3 of 20
AD8651/AD8652
V+ = 5 V, V– = 0 V, VCM = V+/2, TA = 25°C, unless otherwise specified. Table 2.
Parameter
INPUT CHARACTERISTICS Offset Voltage AD8651
Symbol
VOS
Conditions
Min
Typ
Max
Unit
AD8652 Offset Voltage Drift Input Bias Current TCVOS IB
0 V ≤ VCM ≤ 5 V –40°C ≤ TA ≤ +85°C, 0 V ≤ VCM ≤ 5 V –40°C ≤ TA ≤ +125°C, 0 V ≤ VCM ≤ 5 V 0 V ≤ VCM ≤ 5 V –40°C ≤ TA ≤ +125°C, 0 V ≤ VCM ≤ 5 V
100
90 0.4 4 1
350 1.4 1.7 300 1.4 10 30 600 10 30 600 +5.1
–40°C ≤ TA ≤ +85°C –40°C ≤ TA ≤ +125°C Input Offset Current IOS –40°C ≤ TA ≤ +85°C –40°C ≤ TA ≤ +125°C Input Voltage Range Common-Mode Rejection Ratio AD8651 VCM CMRR 0.1 V < VCM < 5.1 V –40°C ≤ TA ≤ +85°C, 0.1 V < VCM < 5.1 V –40°C ≤ TA ≤ +125°C, 0.1 V < VCM < 5.1 V 0.1 V < VCM < 5.1 V –40°C ≤ TA ≤ +125°C, 0.1 V < VCM < 5.1 V RL = 1 kΩ, 200 mV < VO < 4.8 V RL = 1 kΩ, 200 mV < VO < 4.8 V, TA = 85°C RL = 1 kΩ, 200 mV < VO < 4.8 V, TA = 125°C IL = 250 μA, –40°C ≤ TA ≤ +125°C IL = 250 μA, –40°C ≤ TA ≤ +125°C Sourcing Sinking –0.1 80 75 70 84 76 100 98 95 4.97 95 94 90 100 95 115 114 111 1
μV mV mV μV mV μV/°C pA pA pA pA pA pA V dB dB dB dB dB dB dB dB V mV mA mA mA dB dB
AD8652 Large Signal Voltage Gain AVO
OUTPUT CHARACTERISTICS Output Voltage High Output Voltage Low Short-Circuit Limit Output Current POWER SUPPLY Power Supply Rejection Ratio Supply Current AD8651 AD8652 INPUT CAPACITANCE Differential Common Mode DYNAMIC PERFORMANCE Slew Rate Gain Bandwidth Product Settling Time, 0.01% Overload Recovery Time Total Harmonic Distortion + Noise NOISE PERFORMANCE Voltage Noise Density Current Noise Density
VOH VOL ISC IO PSRR ISY
30 80 80 40 76 74 94 93 9.5 17.5 14.0 15 20.0 23.5
VS = 2.7 V to 5.5 V, VCM = 0 V –40°C ≤ TA ≤ +125°C IO = 0 –40°C ≤ TA ≤ +125°C IO = 0 –40°C ≤ TA ≤ +125°C
mA mA mA mA pF pF V/μs MHz μs μs % nV/√Hz nV/√Hz fA/√Hz
CIN 6 9 SR GBP G = 1, RL = 10 kΩ G=1 G = ±1, 2 V step VIN × G = 1.2 V+ G = 1, RL = 600 Ω, f = 1 kHz, VIN = 2 V p-p f = 10 kHz f = 100 kHz f = 10 kHz 41 50 0.2 0.1 0.0006 5 4.5 4
THD + N en in
Rev. C | Page 4 of 20
AD8651/AD8652 ABSOLUTE MAXIMUM RATINGS
Absolute maximum ratings apply at 25°C, unless otherwise noted. Table 3.
Parameter Supply Voltage Input Voltage Differential Input Voltage Output Short-Circuit Duration to GND Electrostatic Discharge (HBM) Storage Temperature Range RM, R Package Operating Temperature Range Junction Temperature Range RM, R Package Lead Temperature (Soldering, 10 sec) Rating 6.0 V GND to VS + 0.3 V ±6.0 V Indefinite 4000 V −65°C to +150°C −40°C to +125°C −65°C to +150°C 300°C
THERMAL RESISTANCE
JA is specified for the worst-case conditions, that is, a device soldered in a circuit board for surface-mount packages. Table 4. Thermal Resistance
Package Type 8-Lead MSOP (RM) 8-Lead SOIC_N (R) θJA 210 158 θJC 45 43 Unit °C/W °C/W
Stresses above those listed under Absolute Maximum Ratings may cause permanent damage to the device. This is a stress rating only; functional operation of the device at these or any other conditions above those indicated in the operational section of this specification is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability.
ESD CAUTION
ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily accumulate on the human body and test equipment and can discharge without detection. Although this product features proprietary ESD protection circuitry, permanent damage may occur on devices subjected to high energy electrostatic discharges. Therefore, proper ESD precautions are recommended to avoid performance degradation or loss of functionality.
Rev. C | Page 5 of 20
AD8651/AD8652 TYPICAL PERFORMANCE CHARACTERISTICS
60 VS = ±2.5V VCM = 0V 50
NUMBER OF AMPLIFIERS
80 100 VS = 5V
40
VOS (µV)
60
30
40
20
20
10
0
40
–80
–40
80
120
160
–200
–160
–120
200
VOS (µV)
Figure 5. Input Offset Voltage Distribution
300 VS = ±2.5V VCM = 0V 200
03301-005
0
1
2 3 4 COMMON-MODE VOLTAGE (V)
5
6
Figure 8. Input Offset Voltage vs. Common-Mode Voltage
500 VS = ±2.5V 400
100
INPUT BIAS CURRENT (pA)
300
VOS (µV)
0
200
–100
–200
100
03301-006
0
50 TEMPERATURE (°C)
100
150
0
20
40
60 80 100 TEMPERATURE (°C)
120
140
Figure 6. Input Offset Voltage vs. Temperature
60 VS = ±2.5V VCM = 0V TA: –40°C TO +125°C
Figure 9. Input Bias Current vs. Temperature
10
50
8
NUMBER OF AMPLIFIERS
40
SUPPLY CURRENT (mA)
6
30
4
20
10
2
0
1
2
3
4
5 6 7 TCVOS (µV/°C)
8
9
10
11
03301-007
0
1
2 3 4 SUPPLY VOLTAGE (V)
5
6
Figure 7. TCVOS Distribution
Figure 10. Supply Current vs. Supply Voltage
Rev. C | Page 6 of 20
03301-010
0
0
03301-009
–300 –50
0
03301-008
0
0
–20
AD8651/AD8652
12 VS = ±2.5V 11
2.50 VS = 5V IL = 250µA 2.00
OUTPUT SWING LOW (mV)
03301-011
SUPPLY CURRENT (mA)
10
1.50
9
1.00
8
7
0.50
0
50 TEMPERATURE (°C)
100
150
0
50 TEMPERATURE (°C)
100
150
Figure 11. Supply Current vs. Temperature
500 VS = ±2.5V 400 80 100
Figure 14. Output Voltage Swing Low vs. Temperature
VS = ±2.5V
(VSY – VOUT) (mV)
VOH 200 VOL 100
CMRR (dB)
300
60
40
20
03301-012
0
20
40 60 CURRENT LOAD (mA)
80
100
100
1k
10k 100k FREQUENCY (Hz)
1M
10M
Figure 12. Output Voltage to Supply Rail vs. Load Current
4.997 4.996 VS = 5V IL = 250µA 105 110
Figure 15. CMRR vs. Frequency
VS = ±2.5V
OUTPUT SWING HIGH (V)
4.995 4.994 4.993 4.992 4.991 4.990 –50
CMRR (dB)
100
95
03301-013
0
50 TEMPERATURE (°C)
100
150
0
50 TEMPERATURE (°C)
100
150
Figure 13. Output Voltage Swing High vs. Temperature
Figure 16. CMRR vs. Temperature
Rev. C | Page 7 of 20
03301-016
90 –50
03301-015
0
0 10
03301-014
6 –50
0 –50
AD8651/AD8652
100 100 VS = ±2.5V
94
91
VOLTAGE NOISE DENSITY (nV/√Hz)
97
CMRR (dB)
10
88
85
0
50 TEMPERATURE (°C)
100
150
100
1k FREQUENCY (Hz)
10k
100k
Figure 17. CMRR vs. Temperature
100 VS = ±2.5V 80 +PSRR 60 –PSRR 40 80
Figure 20. Voltage Noise Density vs. Frequency
VS = ±2.5V
CURRENT NOISE DENSITY (fA/√Hz)
60
PSRR (dB)
40
20
20
03301-018
1
10
100
1k 10k 100k FREQUENCY (Hz)
1M
10M
100M
1k FREQUENCY (Hz)
10k
100k
Figure 18. PSRR vs. Frequency
100 VS = ±2.5V
Figure 21. Current Noise Density vs. Frequency
VS = ±2.5V VIN = 6.4V VIN
95
VOLTAGE (1V/DIV)
VOUT 0
PSRR (dB)
90
85
0
50 TEMPERATURE (°C)
100
150
03301-019
TIME (200µs/DIV)
Figure 19. PSRR vs. Temperature
Figure 22. No Phase Reversal
Rev. C | Page 8 of 20
03301-022
80 –50
03301-021
0
0 100
03301-020
03301-017
82 –50
1 10
AD8651/AD8652
140 VS = ±2.5V 120
40
0
60
VS = ±2.5V RL = 1MΩ CL = 47pF G = 100
PHASE (Degrees)
80 60 40 20 0 –135 –90
CLOSED-LOOP GAIN (dB)
100
–45
OPEN-LOOP GAIN (dB)
20 G = 10 0 G=1 –20
03301-023
100
1k
10k 100k 1M FREQUENCY (Hz)
10M
100M
50k
500k 5M FREQUENCY (Hz)
50M
300M
Figure 23. Open-Loop Gain and Phase vs. Frequency
117 VS = ±2.5V RL = 1kΩ
6
Figure 26. Closed-Loop Gain vs. Frequency
MAXIMUM OUTPUT SWING (V)
116
5 VS = 5V 4
OPEN-LOOP GAIN (dB)
115
3 VS = 2.7V 2
114
113
1
03301-024
0
50 TEMPERATURE (°C)
100
150
1M
10M FREQUENCY (Hz)
100M
Figure 24. Open-Loop Gain vs. Temperature
140 VS = ±2.5V 130 120 110 100 90 80 70
03301-025
Figure 27. Maximum Output Swing vs. Frequency
VS = ±2.5V CL = 47pF AV = 1
IL = 250µA IL = 2.5mA
OPEN-LOOP GAIN (dB)
0
100 150 200 50 OUTPUT VOLTAGE SWING FROM THE RAILS (mV)
250
TIME (100µs/DIV)
Figure 25. Open-Loop Gain vs. Output Voltage Swing
Figure 28. Large Signal Response
Rev. C | Page 9 of 20
03301-028
60
VOLTAGE (1V/DIV)
IL = 4.2mA
03301-027
112 –50
0 100k
03301-026
–20 10
–180
–40 5k
AD8651/AD8652
VS = ±2.5V VIN = 200mV AV = 1
VS = ±2.5V VIN = 200mV GAIN = –15 OUTPUT
0V
VOLTAGE (100mV/DIV)
–2.5V 200mV INPUT 0V
03301-029
TIME (10µs/DIV)
TIME (200ns/DIV)
Figure 29. Small Signal Response
30 VS = ±2.5V VIN = 200mV AV = 1 OUTPUT IMPEDANCE (Ω) 30 40
Figure 32. Positive Overload Recovery Time
VS = ±2.5V
SMALL SIGNAL OVERSHOOT (%)
25
20 –OS 15 +OS 10
20 GAIN = 10 10 GAIN = 100 0 10 GAIN = 1
5
0
10
20
30 40 CAPACITANCE (pF)
50
60
70
100
1k FREQUENCY (Hz)
10k
100k
Figure 30. Small Signal Overshoot vs. Load Capacitance
2.5V VS = ±2.5V VIN = 200mV GAIN = –15 60
Figure 33. Output Impedance vs. Frequency
VS = ±1.35V VCM = 0V 50
NUMBER OF AMPLIFIERS
0V
40
30
0V –200mV
20
10
03301-031
0
0
40
–80
–40
80
120
160
–200
–160
–120
200
TIME (200ns/DIV)
VOS (µV)
Figure 31. Negative Overload Recovery Time
Figure 34. Input Offset Voltage Distribution
Rev. C | Page 10 of 20
03301-034
03301-033
03301-030
0
03301-032
AD8651/AD8652
300 VS = ±1.35V VCM = 0V 200 400 500 VS = ±1.35V
(VSY – VOUT) (mV)
100
300 VOH 200 VOL 100
VOS (µV)
0
–100
–200
0
50 TEMPERATURE (°C)
100
150
0
20
40 60 CURRENT LOAD (mA)
80
100
Figure 35. Input Offset Voltage vs. Temperature
80 VS = 2.7V
Figure 38. Output Voltage to Supply Rail vs. Load Current
2.697 2.696 VS = 2.7V IL = 250µA
INPUT OFFSET VOLTAGE (µV)
60
40
OUTPUT SWING HIGH (V)
2.695 2.694 2.693 2.692 2.691
20
0
03301-036
0
1 2 INPUT COMMON-MODE VOLTAGE (V)
3
0
50 TEMPERATURE (°C)
100
150
Figure 36. Input Offset Voltage vs. Common-Mode Voltage
11 VS = ±1.35V 10 2.50 3.00
Figure 39. Output Voltage Swing High vs. Temperature
VS = 2.7V IL = 250µA
OUTPUT SWING LOW (mV)
SUPPLY CURRENT (mA)
2.00
9
1.50
8
1.00
7
0.50
03301-037
0
50 TEMPERATURE (°C)
100
150
0
50 TEMPERATURE (°C)
100
150
Figure 37. Supply Current vs. Temperature
Figure 40. Output Voltage Swing Low vs. Temperature
Rev. C | Page 11 of 20
03301-040
6 –50
0 –50
03301-039
–20
2.690 –50
03301-038
03301-035
–300 –50
0
AD8651/AD8652
VS = ±1.35V AV = 1 30 VS = ±1.35V VIN = 200mV
SMALL SIGNAL OVERSHOOT (%)
25
VOLTAGE (1V/DIV)
20
15
–OS
10 +OS
5
03301-041
0
10
20
TIME (200µs/DIV)
30 40 CAPACITANCE (pF)
50
60
70
Figure 41. No Phase Reversal
VS = ±1.35V CL = 47pF AV = 1
Figure 44. Small Signal Overshoot vs. Load Capacitance
VS = ±1.35V VIN = 200mV GAIN = –10 1.35V
VOLTAGE (500mV/DIV)
0V
0V –200mV
03301-042
TIME (100µs/DIV)
TIME (200ns/DIV)
Figure 42. Large Signal Response
VS = ±1.35V VIN = 200mV CL = 47pF AV = 1
Figure 45. Negative Overload Recovery Time
VS = ±1.35V VIN = 200mV GAIN = –10
0V
VOLTAGE (100mV/DIV)
–1.35V
200mV 0V
03301-043
TIME (10µs/DIV)
TIME (200ns/DIV)
Figure 43. Small Signal Response
Figure 46. Positive Overload Recovery Time
Rev. C | Page 12 of 20
03301-046
03301-045
03301-044
0
AD8651/AD8652
100 VS = ±1.35V 120 VS = ±1.35V RL = 1kΩ 118
80
116
CMRR (dB)
60
AVO (dB)
03301-047
114
40
112 20
110
100
1k
10k 100k FREQUENCY (Hz)
1M
10M
0
50 TEMPERATURE (°C)
100
150
Figure 47. CMRR vs. Frequency
100 60 VS = ±1.35V 40
Figure 50. Open-Loop Gain vs. Temperature
VS = ±1.35V RL = 1MΩ CL = 47pF G = 100
80
CLOSED-LOOP GAIN (dB)
+PSRR 60 –PSRR
20
PSRR (dB)
G = 10
40
0
G=1
20
–20
03301-048
1
10
100
1k 10k FREQUENCY (Hz)
100k
1M
10M
50k
500k 5M FREQUENCY (Hz)
50M
300M
Figure 48. PSRR vs. Frequency
140 VS = ±1.35V 120 100 –45 0
Figure 51. Closed-Loop Gain vs. Frequency
0 –20 +2.5V VIN –40 –60 –80 –100 –120
–180
R1 10kΩ V– VOUT V+ R2 100Ω
V+ V– –2.5V
CHANNEL SEPARATION (dB)
OPEN-LOOP GAIN (dB)
28mV p-p
80 60 40 20 0 –135 –90
PHASE (Degrees)
03301-049
100
1k
10k 100k 1M FREQUENCY (Hz)
10M
100M
1k
10k 100k FREQUENCY (Hz)
1M
10M
Figure 49. Open-Loop Gain and Phase vs. Frequency
Figure 52. Channel Separation vs. Frequency.
Rev. C | Page 13 of 20
03301-052
–20 10
–140 100
VS = ±2.5V
03301-051
0
–40 5k
03301-050
0 10
108 –50
AD8651/AD8652 APPLICATIONS
THEORY OF OPERATION
The AD865x family consists of voltage feedback, rail-to-rail input and output precision CMOS amplifiers that operate from 2.7 V to 5.5 V of power supply voltage. These amplifiers use Analog Devices, Inc. DigiTrim technology to achieve a higher degree of precision than is available from most CMOS amplifiers. DigiTrim technology, used in a number of Analog Devices amplifiers, is a method of trimming the offset voltage of the amplifier after it has been assembled. The advantage of post-package trimming is that it corrects any offset voltages caused by the mechanical stresses of assembly. The AD865x family is available in standard op amp pinouts, making DigiTrim completely transparent to the user. The input stage of the amplifiers is a true rail-to-rail architecture, allowing the input common-mode voltage range of the op amp to extend to both positive and negative supply rails. The open-loop gain of the AD865x with a load of 1 kΩ is typically 115 dB. The AD865x can be used in any precision op amp application. The amplifiers do not exhibit phase reversal for common-mode voltages within the power supply. With voltage noise of 4.5 nV/√Hz and –105 dB distortion for 10 kHz, 2 V p-p signals, the AD865x is a great choice for high resolution data acquisition systems. Their low noise, sub-pA input bias current, precision offset, and high speed make them superb preamps for fast photodiode applications. The speed and output drive capabilities of the AD865x also make the amplifiers useful in video applications. The NMOS and PMOS input stages are separately trimmed using DigiTrim to minimize the offset voltage in both differential pairs. Both NMOS and PMOS input differential pairs are active in a 500 mV transition region when the input commonmode voltage is approximately 1.5 V below the positive supply voltage. A special design technique improves the input offset voltage in the transition region that traditionally exhibits a slight VOS variation. As a result, the common-mode rejection ratio is improved within this transition band. Compared to the Burr Brown OPA350 amplifier, shown in Figure 53, the AD865x, shown in Figure 54, exhibits much lower offset voltage shift across the entire input common-mode range, including the transition region.
600
400
200
VOS (µV)
0
–200
–400
0
1
2 3 4 COMMON-MODE VOLTAGE (V)
5
6
Figure 53. Input Offset Distribution over Common-Mode Voltage for the OPA350
Rail-to-Rail Output Stage
The voltage swing of the output stage is rail-to-rail and is achieved by using an NMOS and PMOS transistor pair connected in a common source configuration. The maximum output voltage swing is proportional to the output current, and larger currents will limit how close the output voltage can get to the proximity of the output voltage to the supply rail. This is a characteristic of all rail-to-rail output amplifiers. With 40 mA of output current, the output voltage can reach within 5 mV of the positive and negative rails. At light loads of >100 kΩ, the output swings within ~1 mV of the supplies.
600
400
200
VOS (µV)
0
–200
Rail-to-Rail Input Stage
The input common-mode voltage range of the AD865x extends to both positive and negative supply voltages. This maximizes the usable voltage range of the amplifier, an important feature for single-supply and low voltage applications. This rail-to-rail input range is achieved by using two input differential pairs, one NMOS and one PMOS, placed in parallel. The NMOS pair is active at the upper end of the common-mode voltage range, and the PMOS pair is active at the lower end of the common-mode range.
–400
0
1
2 3 4 COMMON-MODE VOLTAGE (V)
5
6
Figure 54. Input Offset Distribution over Common-Mode Input Protection for the AD865x
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03301-061
–600
03301-053
–600
AD8651/AD8652
Input Protection
As with any semiconductor device, if a condition exists for the input voltage to exceed the power supply, the device input overvoltage characteristic must be considered. The inputs of the AD865x family are protected with ESD diodes to either power supply. Excess input voltage energizes internal PN junctions in the AD865x, allowing current to flow from the input to the supplies. This results in an input stage with picoamps of input current that can withstand up to 4000 V ESD events (human body model) with no degradation. Excessive power dissipation through the protection devices destroys or degrades the performance of any amplifier. Differential voltages greater than 7 V result in an input current of approximately (| VCC – VEE | – 0.7 V)/RI, where RI is the resistance in series with the inputs. For input voltages beyond the positive supply, the input current is approximately (VIN – VCC – 0.7)/RI. For input voltages beyond the negative supply, the input current is about (VIN – VEE + 0.7)/RI. If the inputs of the amplifier sustain differential voltages greater than 7 V or input voltages beyond the amplifier power supply, limit the input current to 10 mA by using an appropriately sized input resistor (RI), as shown in Figure 55.
RI > (| VCC – VEE | – 0.7V) 30mA RI > RI > (VIN – VEE – 0.7V) 30mA (VIN – VEE + 0.7V) 30mA FOR VIN BEYOND SUPPLY VOLTAGES
03301-054
Bypassing schemes are designed to minimize the supply impedance at all frequencies with a parallel combination of capacitors of 0.1 μF and 4.7 μF. Chip capacitors of 0.1 μF (X7R or NPO) are critical and should be as close as possible to the amplifier package. The 4.7 μF tantalum capacitor is less critical for high frequency bypassing, and, in most cases, only one is needed per board at the supply inputs.
Grounding
A ground plane layer is important for densely packed PC boards to spread the current-minimizing parasitic inductances. However, an understanding of where the current flows in a circuit is critical to implementing effective high speed circuit design. The length of the current path is directly proportional to the magnitude of parasitic inductances and, therefore, the high frequency impedance of the path. High speed currents in an inductive ground return create an unwanted voltage noise. The length of the high frequency bypass capacitor leads is critical. A parasitic inductance in the bypass grounding works against the low impedance created by the bypass capacitor. Place the ground leads of the bypass capacitors at the same physical location. Because load currents also flow from the supplies, the ground for the load impedance should be at the same physical location as the bypass capacitor grounds. For the larger value capacitors, intended to be effective at lower frequencies, the current return path distance is less critical.
FOR LARGE | VCC – VEE |
+
AD865x
– VIN +
–
RI
+ VO
Leakage Currents
Poor PC board layout, contaminants, and the board insulator material can create leakage currents that are much larger than the input bias current of the AD865x family. Any voltage differential between the inputs and nearby traces sets up leakage currents through the PC board insulator, for example 1 V/100 G = 10 pA. Similarly, any contaminants on the board can create significant leakage (skin oils are a common problem). To significantly reduce leakages, put a guard ring (shield) around the inputs and the input leads that are driven to the same voltage potential as the inputs. This ensures that there is no voltage potential between the inputs and the surrounding area to set up any leakage currents. To be effective, the guard ring must be driven by a relatively low impedance source and should completely surround the input leads on all sides, above and below, using a multilayer board. Another effect that can cause leakage currents is the charge absorption of the insulator material itself. Minimizing the amount of material between the input leads and the guard ring helps to reduce the absorption. Also, low absorption materials, such as Teflon® or ceramic, may be necessary in some instances.
Figure 55. Input Protection Method
Overdrive Recovery
Overdrive recovery is defined as the time it takes for the output of an amplifier to come off the supply rail after an overload signal is initiated. This is usually tested by placing the amplifier in a closedloop gain of 15 with an input square wave of 200 mV p-p while the amplifier is powered from either 5 V or 3 V. The AD865x family has excellent recovery time from overload conditions (see Figure 31 and Figure 32). The output recovers from the positive supply rail within 200 ns at all supply voltages. Recovery from the negative rail is within 100 ns at 5 V supply.
LAYOUT, GROUNDING, AND BYPASSING CONSIDERATIONS
Power Supply Bypassing
Power supply pins can act as inputs for noise, so care must be taken that a noise-free, stable dc voltage is applied. The purpose of bypass capacitors is to create low impedances from the supply to ground at all frequencies, thereby shunting or filtering most of the noise.
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AD8651/AD8652
Input Capacitance
Along with bypassing and grounding, high speed amplifiers can be sensitive to parasitic capacitance between the inputs and ground. A few picofarads of capacitance reduces the input impedance at high frequencies, which in turn increases the amplifier gain, causing peaking in the frequency response or oscillations. With the AD865x, additional input damping is required for stability with capacitive loads greater than 47 pF with direct input to output feedback (see the Output Capacitance section). • Another way to stabilize an op amp driving a large capacitive load is to use a snubber network, as shown in Figure 57. Because there is not any isolation resistor in the signal path, this method has the significant advantage of not reducing the output swing. The exact values of RS and CS are derived experimentally. In Figure 57, an optimum RS and CS combination for a capacitive load drive ranging from 50 pF to 1 nF was chosen. For this, RS = 3 Ω and CS = 10 nF were chosen.
V+
Output Capacitance
When using high speed amplifiers, it is important to consider the effects of the capacitive loading on amplifier stability. Capacitive loading interacts with the output impedance of the amplifier, causing reduction of the BW as well as peaking and ringing of the frequency response. To reduce the effects of the capacitive loading and allow higher capacitive loads, there are two commonly used methods. • As shown in Figure 56, place a small value resistor (RS) in series with the output to isolate the load capacitor from the amplifier output. Heavy capacitive loads can reduce the phase margin of an amplifier and cause the amplifier response to peak or become unstable. The AD865x is able to drive up to 47 pF in a unity gain buffer configuration without oscillation or external compensation. However, if an application requires a higher capacitive load drive when the AD865x is in unity gain, the use of external isolation networks can be used. The effect produced by this resistor is to isolate the op amp output from the capacitive load. The required amount of series resistance has been tabulated in Table 5 for different capacitive loads. While this technique improves the overall capacitive load drive for the amplifier, its biggest drawback is that it reduces the output swing of the overall circuit.
VCC 3 VIN 2 U1
+
V+ VOUT RS
03301-056
AD865x
–
200mV V– V– CS CL RL
Figure 57. Snubber Network
Settling Time
The settling time of an amplifier is defined as the time it takes for the output to respond to a step change of input and enter and remain within a defined error band, as measured relative to the 50% point of the input pulse. This parameter is especially important in measurements and control circuits where amplifiers are used to buffer A/D inputs or DAC outputs. The design of the AD865x family combines a high slew rate and a wide gain bandwidth product to produce an amplifier with very fast settling time. The AD865x is configured in the noninverting gain of 1 with a 2 V p-p step applied to its input. The AD865x family has a settling time of about 130 ns to 0.01% (2 mV). The output is monitored with a 10×, 10 M, 11.2 pF scope probe.
THD Readings vs. Common-Mode Voltage
Total harmonic distortion of the AD865x family is well below 0.0004% with any load down to 600 Ω. The distortion is a function of the circuit configuration, the voltage applied, and the layout, in addition to other factors. The AD865x family outperforms its competitor for distortion, especially at frequencies below 20 kHz, as shown in Figure 58.
0.1 0.05 VSY = +3.5V/–1.5V VOUT = 2.0V p-p
+
V+ V–
AD865x
–
RS
VOUT
CL 0 0
RL
03301-055
0.02 0.01
0
Figure 56. Driving Large Capacitive Loads
THD + NOISE (%)
0.005 0.002 0.001 OPA350
Table 5. Optimum Values for Driving Large Capacitive Loads
CL 100 pF 500 pF 1.0 nF RS 50 Ω 35 Ω 25 Ω
0.0005 0.0002 0.0001 20 50 100 AD8651
03301-057
500 1k 2k FREQUENCY (Hz)
5k
20k
Figure 58. Total Harmonic Distortion
Rev. C | Page 16 of 20
AD8651/AD8652
+3.5V
5V
+
10kΩ
AD865x
–
VIN 2V p-p –1.5V 600Ω 47pF
VOUT
1µF
03301-058
3
U1
+
10kΩ 2 VIN 0V TO 5V fIN = 45kHz 1kΩ
AD865x
– –V
V+
33Ω
VCC IN 2.7nF
03301-060
AD7685
Figure 59. THD + N Test Circuit
1kΩ
Driving a 16-Bit ADC
The AD865x family is an excellent choice for driving high speed, high precision ADCs. The driver amplifier for this type of application needs low THD + N as well as quick settling time. Figure 61 shows a complete single-supply data acquisition solution. The AD865x family drives the AD7685, a 250 kSPS, 16-bit data converter. 1 The AD865x is configured in an inverting gain of 1 with a 5 V single supply. Input of 45 kHz is applied, and the ADC samples at 250 kSPS. The results of this solution are listed in Table 6. The advantage of this circuit is that the amplifier and ADC can be powered with the same power supply. For the case of a noninverting gain of 1, the input common-mode voltage encompasses both supplies.
1
Figure 61. AD865x Driving a 16-Bit ADC
Table 6. Data Acquisition Solution of Figure 60
Parameter THD + N SFDR 2nd Harmonics 3rd Harmonics Reading (dB) 105.2 106.6 107.7 113.6
For more information about the AD7685 data converter, go to http://www.analog.com/Analog_Root/productPage/productHome/0%2C21 21%2CAD7685%2C00.html
0 –20 fSAMPLE = 250kSPS fIN = 45kHz INPUT RANGE = 0V TO 5V
AMPLITUDE (dB of Full Scale)
–40 –60 –80 –100 –120 –140 –160
0
10
20
30 40
50 60 70 80 FREQUENCY (kHz)
90
100 110 120
Figure 60. Frequency Response of AD865x Driving a 16-Bit ADC
03301-059
Rev. C | Page 17 of 20
AD8651/AD8652 OUTLINE DIMENSIONS
3.20 3.00 2.80
3.20 3.00 2.80 PIN 1
8
5
1
5.15 4.90 4.65
4
0.65 BSC 0.95 0.85 0.75 0.15 0.00 0.38 0.22 SEATING PLANE 1.10 MAX 8° 0° 0.80 0.60 0.40
0.23 0.08
COPLANARITY 0.10
COMPLIANT TO JEDEC STANDARDS MO-187-AA
Figure 62. 8-Lead Mini Small Outline Package [MSOP] (RM-8) Dimensions shown in millimeters
5.00 (0.1968) 4.80 (0.1890)
4.00 (0.1574) 3.80 (0.1497)
8 1
5 4
6.20 (0.2440) 5.80 (0.2284)
1.27 (0.0500) BSC 0.25 (0.0098) 0.10 (0.0040) COPLANARITY 0.10 SEATING PLANE
1.75 (0.0688) 1.35 (0.0532)
0.50 (0.0196) 0.25 (0.0099) 8° 0° 0.25 (0.0098) 0.17 (0.0067) 1.27 (0.0500) 0.40 (0.0157)
45°
0.51 (0.0201) 0.31 (0.0122)
COMPLIANT TO JEDEC STANDARDS MS-012-A A CONTROLLING DIMENSIONS ARE IN MILLIMETERS; INCH DIMENSIONS (IN PARENTHESES) ARE ROUNDED-OFF MILLIMETER EQUIVALENTS FOR REFERENCE ONLY AND ARE NOT APPROPRIATE FOR USE IN DESIGN.
Figure 63. 8-Lead Standard Small Outline Package [SOIC_N] Narrow Body (R-8) Dimensions shown in millimeters and (inches)
Rev. C | Page 18 of 20
060506-A
AD8651/AD8652
ORDERING GUIDE
Model AD8651ARM-REEL AD8651ARM-R2 AD8651ARMZ-REEL1 AD8651ARMZ-R21 AD8651AR AD8651AR-REEL AD8651AR-REEL7 AD8651ARZ1 AD8651ARZ-REEL1 AD8651ARZ-REEL71 AD8652ARMZ-R21 AD8652ARMZ-REEL1 AD8652ARZ1 AD8652ARZ-REEL1 AD8652ARZ-REEL71
1
Temperature Range –40°C to +125°C –40°C to +125°C –40°C to +125°C –40°C to +125°C –40°C to +125°C –40°C to +125°C –40°C to +125°C –40°C to +125°C –40°C to +125°C –40°C to +125°C –40°C to +125°C –40°C to +125°C –40°C to +125°C –40°C to +125°C –40°C to +125°C
Package Description 8-Lead MSOP 8-Lead MSOP 8-Lead MSOP 8-Lead MSOP 8-Lead SOIC_N 8-Lead SOIC_N 8-Lead SOIC_N 8-Lead SOIC_N 8-Lead SOIC_N 8-Lead SOIC_N 8-Lead MSOP 8-Lead MSOP 8-Lead SOIC_N 8-Lead SOIC_N 8-Lead SOIC_N
Package Option RM-8 RM-8 RM-8 RM-8 R-8 R-8 R-8 R-8 R-8 R-8 RM-8 RM-8 R-8 R-8 R-8
Branding BEA BEA BEA# BEA#
A05 A05
Z = Pb-free part; # denotes lead-free product may be top or bottom marked.
Rev. C | Page 19 of 20
AD8651/AD8652 NOTES
©2006 Analog Devices, Inc. All rights reserved. Trademarks and registered trademarks are the property of their respective owners. C03301-0-8/06(C)
Rev. C | Page 20 of 20
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