25 MHz Direct Digital Synthesizer,
Waveform Generator
AD9832
Data Sheet
FEATURES
GENERAL DESCRIPTION
25 MHz speed
On-chip SIN lookup table
On-chip, 10-bit DAC
Serial loading
Power-down option
Temperature range: −40°C to +85°C
200 mW power consumption
16-Lead TSSOP
The AD9832 is a numerically controlled oscillator employing
a phase accumulator, a sine look-up table, and a 10-bit digitalto-analog converter (DAC) integrated on a single CMOS chip.
Modulation capabilities are provided for phase modulation and
frequency modulation.
Clock rates up to 25 MHz are supported. Frequency accuracy can
be controlled to one part in 4 billion. Modulation is effected by
loading registers through the serial interface.
A power-down bit allows the user to power down the AD9832
when it is not in use, the power consumption being reduced to
5 mW (5 V) or 3 mW (3 V). The part is available in a 16-lead
TSSOP package.
APPLICATIONS
Frequency stimulus/waveform generation
Frequency phase tuning and modulation
Low power RF/communications systems
Liquid and gas flow measurement
Sensory applications: proximity, motion, and defect
detection
Test and medical equipment
Similar DDS products can be found at www.analog.com/DDS.
FUNCTIONAL BLOCK DIAGRAM
DVDD
FSELECT
BIT
FSELECT
AVDD
AGND
REFOUT
FS ADJUST
REFIN
SELSRC
ON-BOARD
REFERENCE
MUX
MCLK
DGND
FULL-SCALE
CONTROL
SYNC
FREQ0 REG
12
MUX
PHASE
ACCUMULATOR
(32 BIT)
FREQ1 REG
SIN
ROM
10-BIT DAC
COMP
IOUT
PHASE0 REG
PHASE1 REG
AD9832
MUX
PHASE2 REG
SYNC
PHASE3 REG
SYNC
16-BIT DATA REGISTER
SYNC
8 LSBs
8 MSBs
DEFER REGISTER
SELSRC
CONTROL REGISTER
DECODE LOGIC
FSELECT/PSEL REGISTER
MUX
PSEL0
BIT
MUX
PSEL1
BIT
FSYNC
SCLK
PSEL0 PSEL1
SDATA
09090-001
SERIAL REGISTER
Figure 1.
Rev. E
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Tel: 781.329.4700 ©1999–2013 Analog Devices, Inc. All rights reserved.
Technical Support
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AD9832
Data Sheet
TABLE OF CONTENTS
Features .............................................................................................. 1
Latency ......................................................................................... 16
Applications ....................................................................................... 1
Flowcharts ................................................................................... 16
General Description ......................................................................... 1
Applications Information .............................................................. 19
Functional Block Diagram .............................................................. 1
Grounding and Layout .............................................................. 19
Revision History ............................................................................... 2
Interfacing the AD9832 to Microprocessors .............................. 19
Specifications..................................................................................... 3
AD9832 to ADSP-2101 Interface ............................................. 19
Timing Characteristics ................................................................ 5
AD9832 to 68HC11/68L11 Interface ....................................... 20
Absolute Maximum Ratings ............................................................ 6
AD9832 to 80C51/80L51 Interface .......................................... 20
ESD Caution .................................................................................. 6
AD9832 to DSP56002 Interface ............................................... 20
Pin Configuration and Function Descriptions ............................. 7
Evaluation Board ............................................................................ 21
Typical Performance Characteristics ............................................. 8
System Demonstration Platform .............................................. 21
Terminology .................................................................................... 11
AD9832 to SPORT Interface ..................................................... 21
Theory of Operation ...................................................................... 12
XO vs. External Clock................................................................ 21
Circuit Description ......................................................................... 13
Power Supply............................................................................... 21
Numerical Controlled Oscillator and Phase Modulator ....... 13
Evaluation Board Schematics ................................................... 22
Sine Look-Up Table (LUT)........................................................ 13
Evaluation Board Layout ........................................................... 24
Digital-to-Analog Converter .................................................... 13
Ordering Information .................................................................... 25
Functional Description .................................................................. 14
Bill of Materials ........................................................................... 25
Serial Interface ............................................................................ 14
Outline Dimensions ....................................................................... 26
Direct Data Transfer and Deferred Data Transfer ................. 14
Ordering Guide .......................................................................... 26
REVISION HISTORY
2/13—Rev. D to Rev. E
Changes to Table 10 ........................................................................ 15
Changes to Flowcharts Section ..................................................... 16
7/12—Rev. C to Rev. D
Changed On-Chip COS Lookup Table to On-Chip SIN Lookup
Table in Features Section ................................................................. 1
9/11—Rev. B to Rev. C
Changes to Features and Applications ........................................... 1
Changes to Specification Statement ............................................... 3
Changes to Timing Characteristics Statement ............................. 5
Replaced Evaluation Board Section; Renumbered
Sequentially ..................................................................................... 21
Changes to Ordering Guide .......................................................... 26
6/10—Rev. A to Rev. B
Updated Format .................................................................. Universal
Changed CMOS Complete DDS to 3 V to 5.0 V Programmable
Waveform Generator.........................................................................1
Changes to Serial Interface Section.............................................. 14
Updated Outline Dimensions ....................................................... 23
Changes to Ordering Guide .......................................................... 23
7/99—Rev 0 to Rev. A
Rev. E | Page 2 of 28
Data Sheet
AD9832
SPECIFICATIONS
VDD = +5 V ± 5%; AGND = DGND = 0 V; TA = TMIN to TMAX; REFIN = REFOUT; RSET = 3.9 kΩ; RLOAD = 300 Ω for IOUT, unless otherwise
noted. Also, see Figure 2.
Table 1.
Parameter 1
SIGNAL DAC SPECIFICATIONS
Resolution
Update Rate (fMAX)
IOUT Full Scale
Output Compliance
DC Accuracy
Integral Nonlinearity
Differential Nonlinearity
DDS SPECIFICATIONS 2
Dynamic Specifications
Signal-to-Noise Ratio
Total Harmonic Distortion
Spurious-Free Dynamic Range (SFDR) 3
Narrow Band (±50 kHz)
Wideband (±2 MHz)
Clock Feedthrough
Wake-Up Time 4
Power-Down Option
VOLTAGE REFERENCE
Internal Reference @ 25°C
TMIN to TMAX
REFIN Input Impedance
Reference Temperature Coefficient (TC)
REFOUT Output Impedance
LOGIC INPUTS
Input High Voltage, VINH
Input Low Voltage, VINL
Input Current, IINH
Input Capacitance, CIN
POWER SUPPLIES
AVDD
DVDD
IAA
IDD
IAA + IDD 5
Low Power Sleep Mode
AD9832B
Unit
Test Conditions/Comments
10
25
4
4.5
1.35
Bits
MSPS nom
mA nom
mA max
V max
3 V power supply
±1
±0.5
LSB typ
LSB typ
50
−53
dB min
dBc max
−72
−70
−50
−60
1
Yes
dBc min
dBc min
dBc min
dBc typ
ms typ
1.21
1.21 ± 7%
10
100
300
V typ
V min/V max
MΩ typ
ppm/°C typ
Ω typ
VDD − 0.9
0.9
10
10
V min
V max
µA max
pF max
2.97/5.5
2.97/5.5
5
2.5 + 0.4/MHz
15
24
350
V min/V max
V min/V max
mA max
mA typ
mA max
mA max
µA max
fMCLK = 25 MHz, fOUT = 1 MHz
fMCLK = 25 MHz, fOUT = 1 MHz
fMCLK = 6.25 MHz, fOUT = 2.11 MHz
5 V power supply
3 V power supply
5 V power supply
5 V power supply
3 V power supply
5 V power supply
Operating temperature range is −40°C to +85°C.
100% production tested.
fMCLK = 6.25 MHz, frequency word = 0x5671C71C, and fOUT = 2.11 MHz.
4
See Figure 13. To reduce the wake-up time at low power supplies and low temperature, the use of an external reference is suggested.
5
Measured with the digital inputs static and equal to 0 V or DVDD. The AD9832 is tested with a capacitive load of 50 pF. The part can operate with higher capacitive
loads, but the magnitude of the analog output will be attenuated. For example, a 5 MHz output signal is attenuated by 3 dB when the load capacitance equals 85 pF.
1
2
3
Rev. E | Page 3 of 28
AD9832
Data Sheet
RSET
3.9kΩ
10nF
ON-BOARD
REFERENCE
12
SIN
ROM
REFIN
FS
ADJUST
FULL-SCALE
CONTROL
10-BIT DAC
COMP
AVDD
10nF
IOUT
300Ω
50pF
AD9832
Figure 2. Test Circuit by Which Specifications Were Tested
Rev. E | Page 4 of 28
09090-002
REFOUT
Data Sheet
AD9832
TIMING CHARACTERISTICS
VDD = +5 V ± 5%; AGND = DGND = 0 V, unless otherwise noted.
Table 2.
Parameter
t1
t2
t3
t4
t5
t6
t7
t8
t9
t10
t11
t11A 1
1
Limit at TMIN to TMAX (B Version)
40
16
16
50
20
20
15
20
SCLK − 5
15
5
8
8
Unit
ns min
ns min
ns min
ns min
ns min
ns min
ns min
ns min
ns max
ns min
ns min
ns min
ns min
Test Conditions/Comments
MCLK period
MCLK high duration
MCLK low duration
SCLK period
SCLK high duration
SCLK low duration
FSYNC to SCLK falling edge setup time
FSYNC to SCLK hold time
Data setup time
Data hold time
FSELECT, PSEL0, PSEL1 setup time before MCLK rising edge
FSELECT, PSEL0, PSEL1 setup time after MCLK rising edge
See the Pin Configuration and Function Descriptions section.
Timing Diagrams
t1
09090-003
MCLK
t2
t3
Figure 3. Master Clock
t5
t4
SCLK
t7
t8
t6
FSYNC
t10
D15
D14
D2
D1
D0
D15
Figure 4. Serial Timing
MCLK
t11A
t11
FSELECT
PSEL0, PSEL1
VALID DATA
VALID DATA
Figure 5. Control Timing
Rev. E | Page 5 of 28
VALID DATA
09090-005
SDATA
D14
09090-004
t9
AD9832
Data Sheet
ABSOLUTE MAXIMUM RATINGS
TA = 25°C, unless otherwise noted.
Table 3.
Parameter
AVDD to AGND
DVDD to DGND
AVDD to DVDD
AGND to DGND
Digital I/O Voltage to DGND
Analog I/O Voltage to AGND
Operating Temperature Range
Industrial (B Version)
Storage Temperature Range
Maximum Junction Temperature
TSSOP θJA Thermal Impedance
Lead Temperature, Soldering
Vapor Phase (60 sec)
Infrared (15 sec)
ESD Rating
Rating
−0.3 V to +7 V
−0.3 V to +7 V
−0.3 V to +0.3 V
−0.3 V to +0.3 V
−0.3 V to DVDD + 0.3 V
−0.3 V to AVDD + 0.3 V
Stresses above those listed under Absolute Maximum Ratings
may cause permanent damage to the device. This is a stress
rating only; functional operation of the device at these or any
other conditions above those indicated in the operational
section of this specification is not implied. Exposure to absolute
maximum rating conditions for extended periods may affect
device reliability.
ESD CAUTION
−40°C to +85°C
−65°C to +150°C
150°C
158°C/W
215°C
220°C
>4500 V
Rev. E | Page 6 of 28
Data Sheet
AD9832
FS ADJUST 1
16
COMP
REFIN 2
15
AVDD
REFOUT 3
14
IOUT
DVDD 4
AD9832
13
AGND
DGND 5
TOP VIEW
(Not to Scale)
12
PSEL0
MCLK 6
11
PSEL1
SCLK 7
10
FSELECT
SDATA 8
9
FSYNC
09090-006
PIN CONFIGURATION AND FUNCTION DESCRIPTIONS
Figure 6. Pin Configuration
Table 4. Pin Function Descriptions
Pin No.
1
Mnemonic
FS ADJUST
2
REFIN
3
REFOUT
4
DVDD
5
6
DGND
MCLK
7
8
9
SCLK
SDATA
FSYNC
10
FSELECT
11, 12
PSEL1,
PSEL0
13
14
15
AGND
IOUT
AVDD
16
COMP
Description
Full-Scale Adjust Control. A resistor (RSET) is connected between this pin and AGND. This determines the
magnitude of the full-scale DAC current. The relationship between RSET and the full-scale current is
IOUTFULL-SCALE = 12.5 × VREFIN/RSET, where VREFIN = 1.21 V nominal and RSET = 3.9 kΩ typical.
Voltage Reference Input. The AD9832 can be used with either the on-board reference, which is available from
the REFOUT pin, or an external reference. The reference to be used is connected to the REFIN pin. The AD9832
accepts a reference of 1.21 V nominal.
Voltage Reference Output. The AD9832 has an on-board reference of value 1.21 V nominal. The reference is
available on the REFOUT pin. This reference is used as the reference to the DAC by connecting REFOUT to REFIN.
REFOUT should be decoupled with a 10 nF capacitor to AGND.
Positive Power Supply for the Digital Section. A 0.1 µF decoupling capacitor should be connected between
DVDD and DGND. DVDD can have a value of 5 V ± 10% or 3.3 V ± 0%.
Digital Ground.
Digital Clock Input. DDS output frequencies are expressed as a binary fraction of the frequency of MCLK. This
clock determines the output frequency accuracy and phase noise.
Serial Clock, Logic Input. Data is clocked into the AD9832 on each falling SCLK edge.
Serial Data In, Logic Input. The 16-bit serial data-word is applied to this input.
Data Synchronization Signal, Logic Input. When this input goes low, the internal logic is informed that
a new word is being loaded into the device.
Frequency Select Input. FSELECT controls which frequency register, FREQ0 or FREQ1, is used in the phase
accumulator. The frequency register to be used can be selected using the FSELECT pin or the FSELECT bit. FSELECT
is sampled on the rising MCLK edge. FSELECT needs to be in steady state when an MCLK rising edge occurs. If
FSELECT changes value when a rising edge occurs, there is an uncertainty of one MCLK cycle as to when control is
transferred to the other frequency register. To avoid any uncertainty, a change on FSELECT should not coincide with an
MCLK rising edge. When the bit is being used to select the frequency register, the FSELECT pin should be tied to DGND.
Phase Select Input. The AD9832 has four phase registers. These registers can be used to alter the value being
input to the SIN ROM. The contents of the phase register are added to the phase accumulator output, the inputs
PSEL0 and PSEL1 selecting the phase register to be used. Alternatively, the phase register to be used can be
selected using the PSEL0 and PSEL1 bits. Like the FSELECT input, PSEL0 and PSEL1 are sampled on the rising
MCLK edge. Therefore, these inputs need to be in steady state when an MCLK rising edge occurs or there is an
uncertainty of one MCLK cycle as to when control is transferred to the selected phase register. When the phase
registers are being controlled by the PSEL0 and PSEL1 bits, the pins should be tied to DGND.
Analog Ground.
Current Output. This is a high impedance current source. A load resistor should be connected between IOUT and AGND.
Positive Power Supply for the Analog Section. A 0.1 µF decoupling capacitor should be connected between
AVDD and AGND. AVDD can have a value of 5 V ± 10% or 3.3 V ± 10%.
Compensation Pin. This is a compensation pin for the internal reference amplifier. A 10 nF decoupling ceramic
capacitor should be connected between COMP and AVDD.
Rev. E | Page 7 of 28
AD9832
Data Sheet
TYPICAL PERFORMANCE CHARACTERISTICS
25
–40
TA = 25°C
AVDD = DVDD = 3.3V
–45
–50
SFDR (±2MHz) (dB)
TOTAL CURRENT (mA)
20
15
5V
10
3.3V
25MHz
–55
10MHz
–60
–65
–70
5
5
15
10
20
25
MCLK FREQUENCY (MHz)
–80
09090-007
0
0
0.1
0.2
0.4
0.3
fOUT/fMCLK
09090-010
–75
Figure 10. Wideband SFDR vs. fOUT/fMCLK for Various MCLK Frequencies
Figure 7. Typical Current Consumption vs. MCLK Frequency
–50
60
AVDD = DVDD = 3.3V
fOUT = fMCLK/3
fOUT/fMCLK = 1/3
AVDD = DVDD = 3.3V
–55
SNR (dB)
SFDR (±50kHz) (dB)
55
–60
–65
50
–70
45
20
25
MCLK FREQUENCY (MHz)
40
10
15
20
25
09090-011
15
09090-008
–80
10
0.4
09090-012
–75
MCLK FREQUENCY (MHz)
Figure 8. Narrow-Band SFDR vs. MCLK Frequency
Figure 11. SNR vs. MCLK Frequency
60
–40
AVDD = DVDD = 3.3V
fOUT/fMCLK = 1/3
AVDD = DVDD = 3.3V
–45
10MHz
SNR (dB)
–50
–55
25MHz
50
45
–60
–65
10
15
20
MCLK FREQUENCY (MHz)
25
40
09090-009
SFDR (±2MHz) (dB)
55
0
0.1
0.2
0.3
fOUT/fMCLK
Figure 9. Wideband SFDR vs. MCLK Frequency
Figure 12. SNR vs. fOUT/fMCLK for Various MCLK Frequencies
Rev. E | Page 8 of 28
Data Sheet
AD9832
0
10.0
AVDD = DVDD = 2.97V
–10
–20
–30
10dB/DIV
WAKE-UP TIME (ms)
7.5
5.0
–40
–50
–60
–70
2.5
–80
–30
–20
–10
0
TEMPERATURE (°C)
–100
09090-013
0
–40
0
–10
–20
–20
–30
–30
–40
–40
10dB/DIV
–50
–60
–50
–60
–70
–70
–80
–80
VBW 1kHz
STOP 12.5MHz
ST 277 SEC
09090-014
START 0Hz
RBW 300Hz
–100
Figure 14. fMCLK = 25 MHz, fOUT = 1.1 MHz, Frequency Word = 0xB439581
START 0Hz
RBW 300Hz
VBW 1kHz
STOP 12.5MHz
ST 277 SEC
09090-017
–90
–90
Figure 17. fMCLK = 25 MHz, fOUT = 4.1 MHz, Frequency Word = 0x29FBE76D
0
0
–10
–10
–20
–20
–30
–30
–40
–40
10dB/DIV
10dB/DIV
STOP 12.5MHz
ST 277 SEC
–50
–60
–50
–60
–70
–70
–80
–80
–90
START 0Hz
RBW 300Hz
VBW 1kHz
STOP 12.5MHz
ST 277 SEC
09090-015
–90
–100
Figure 15. fMCLK = 25 MHz, fOUT = 2.1 MHz, Frequency Word = 0x15810625
START 0Hz
RBW 300Hz
VBW 1kHz
STOP 12.5MHz
ST 277 SEC
09090-018
10dB/DIV
0
–10
–100
VBW 1kHz
Figure 16. fMCLK = 25 MHz, fOUT = 3.1 MHz, Frequency Word = 0x1FBE76C9
Figure 13. Wake-Up Time vs. Temperature
–100
START 0Hz
RBW 300Hz
09090-016
–90
Figure 18. fMCLK = 25 MHz, fOUT = 5.1 MHz, Frequency Word = 0x34395810
Rev. E | Page 9 of 28
Data Sheet
0
0
–10
–10
–20
–20
–30
–30
–40
–40
10dB/DIV
–50
–60
–60
–70
–70
–80
–80
–90
START 0Hz
RBW 300Hz
VBW 1kHz
STOP 12.5MHz
ST 277 SEC
–100
Figure 19. fMCLK = 25 MHz, fOUT = 6.1 MHz, Frequency Word = 0x3E76C8B4
–10
–10
–20
–20
–30
–30
–40
–40
10dB/DIV
0
–50
–60
–60
–80
–80
–90
–90
STOP 12.5MHz
ST 277 SEC
09090-020
–70
VBW 1kHz
–100
Figure 20. fMCLK = 25 MHz, fOUT = 7.1 MHz, Frequency Word = 0x48B43958
STOP 12.5MHz
ST 277 SEC
–50
–70
START 0Hz
RBW 300Hz
VBW 1kHz
Figure 21. fMCLK = 25 MHz, fOUT = 8.1 MHz, Frequency Word = 0x52F1A9FC
0
–100
START 0Hz
RBW 300Hz
09090-021
–90
09090-019
–100
10dB/DIV
–50
START 0Hz
RBW 300Hz
VBW 1kHz
STOP 12.5MHz
ST 277 SEC
09090-022
10dB/DIV
AD9832
Figure 22. fMCLK = 25 MHz, fOUT = 9.1 MHz, Frequency Word = 0x5D2F1AA0
Rev. E | Page 10 of 28
Data Sheet
AD9832
TERMINOLOGY
Integral Nonlinearity
This is the maximum deviation of any code from a straight line
passing through the endpoints of the transfer function. The
endpoints of the transfer function are zero scale, a point 0.5 LSB
below the first code transition (000 . . . 00 to 000 . . . 01) and full
scale, a point 0.5 LSB above the last code transition (111 . . . 10
to 111 . . . 11). The error is expressed in LSBs.
Differential Nonlinearity
This is the difference between the measured and ideal 1 LSB
change between two adjacent codes in the DAC.
Signal-to-Noise-and-Distortion Ratio
It is measured signal to noise at the output of the DAC. The
signal is the rms magnitude of the fundamental. Noise is the
rms sum of all the nonfundamental signals up to half the
sampling frequency (fMCLK/2) but excluding the dc component.
The signal-to-noise-and-distortion ratio is dependent on the
number of quantization levels used in the digitization process;
the more levels, the smaller the quantization noise. The theoretical
signal-to-noise-and-distortion ratio for a sine wave input is
Signal-to-Noise-and-Distortion = (6.02N + 1.76) dB
Output Compliance
The output compliance refers to the maximum voltage that can
be generated at the output of the DAC to meet the specifications.
When voltages greater than those specified for the output
compliance are generated, the AD9832 may not meet the
specifications listed in the data sheet.
Spurious-Free Dynamic Range (SFDR)
Along with the frequency of interest, harmonics of the fundamental
frequency and images of the MCLK frequency are present at the
output of a DDS device. SFDR refers to the largest spur or harmonic
present in the band of interest. The wide-band SFDR gives the
magnitude of the largest harmonic or spur relative to the magnitude
of the fundamental frequency in the bandwidth ±2 MHz about
the fundamental frequency. The narrowband SFDR gives the
attenuation of the largest spur or harmonic in a bandwidth of
±50 kHz about the fundamental frequency.
Clock Feedthrough
There is feedthrough from the MCLK input to the analog output.
Clock feedthrough refers to the magnitude of the MCLK signal
relative to the fundamental frequency in the output spectrum of
the AD9832.
where N is the number of bits. Thus, for an ideal 10-bit converter,
the signal-to-noise-and-distortion ratio = 61.96 dB.
Total Harmonic Distortion (THD)
THD is the ratio of the rms sum of harmonics to the rms value of
the fundamental. For the AD9832, THD is defined as
THD = 20 log
V22 + V32 + V4 2 + V52 + V62
V1
where:
V1 is the rms amplitude of the fundamental.
V2, V3, V4, V5, and V6 are the rms amplitudes of the second
through the sixth harmonic.
Rev. E | Page 11 of 28
AD9832
Data Sheet
THEORY OF OPERATION
Sine waves are typically thought of in terms of their magnitude
form a(t) = sin (ωt). However, these are nonlinear and not easy
to generate except through piecewise construction. On the
other hand, the angular information is linear in nature. That is,
the phase angle rotates through a fixed angle for each unit of
time. The angular rate depends on the frequency of the signal
by the traditional rate of ω = 2 πf.
Knowing that the phase of a sine wave is linear and given a
reference interval (clock period), the phase rotation for that
period can be determined by
ΔPhase = ωδt
Solving for ω,
ω = ΔPhase/δt = 2 πf
Solving for f and substituting the reference clock frequency for
the reference period (1/fMCLK = δt),
MAGNITUDE
+1
f = ΔPhase × fMCLK/2 π
0
The AD9832 builds the output based on this simple equation. A
simple DDS chip can implement this equation with three major
subcircuits.
–1
PHASE
09090-023
2
0
Figure 23. Sine Wave
Rev. E | Page 12 of 28
Data Sheet
AD9832
CIRCUIT DESCRIPTION
The input to the phase accumulator (that is, the phase step) can
be selected from either the FREQ0 register or the FREQ1 register
and can be controlled by the FSELECT pin or the FSELECT bit.
NCOs inherently generate continuous phase signals, thus
avoiding any output discontinuity when switching between
frequencies.
The AD9832 provides an exciting new level of integration
for the RF/communications system designer. The AD9832
combines the numerical controlled oscillator (NCO), a sine
look-up table, frequency and phase modulators, and a DAC
on a single integrated circuit.
The internal circuitry of the AD9832 consists of three main
sections. They are:
•
•
•
Numerical controlled oscillator (NCO) and phase modulator
Sine look-up table
DAC
The AD9832 is a fully integrated direct digital synthesis (DDS)
chip. The chip requires a reference clock, a low precision resistor,
and eight decoupling capacitors to provide digitally created sine
waves up to 12.5 MHz. In addition to the generation of this RF
signal, the chip is fully capable of a broad range of simple and
complex modulation schemes. These modulation schemes are
fully implemented in the digital domain, allowing accurate and
simple realization of complex modulation algorithms using DSP
techniques.
NUMERICAL CONTROLLED OSCILLATOR AND
PHASE MODULATOR
The NCO and phase modulator consists of two frequency select
registers, a phase accumulator, and four phase offset registers.
The main component of the NCO is a 32-bit phase accumulator
that assembles the phase component of the output signal. Continuous
time signals have a phase range of 0 to 2 π. Outside this range of
numbers, the sinusoid functions repeat themselves in a periodic
manner. The digital implementation is no different. The accumulator
simply scales the range of phase numbers into a multibit digital
word. The phase accumulator in the AD9832 is implemented
with 32 bits. Therefore, in the AD9832, 2π = 232. Likewise, the
ΔPhase term is scaled into this range of numbers 0 < ΔPhase <
232 − 1.
f = ΔPhase × fMCLK/232
where 0 < ΔPhase < 232.
Following the NCO, a phase offset can be added to perform
phase modulation using the 12-bit PHASEx registers. The contents
of these registers are added to the most significant bits of the NCO.
The AD9832 has four PHASEx registers, the resolution of these
registers being 2 π/4096.
SINE LOOK-UP TABLE (LUT)
To make the output useful, the signal must be converted from
phase information into a sinusoidal value. Because phase information
maps directly into amplitude, a ROM LUT converts the phase
information into amplitude. To do this, the digital phase
information is used to address a sine ROM LUT. Although the
NCO contains a 32-bit phase accumulator, the output of the
NCO is truncated to 12 bits. Using the full resolution of the phase
accumulator is impractical and unnecessary because this would
require a look-up table of 232 entries.
It is only necessary to have sufficient phase resolution in the
LUTs so that the dc error of the output waveform is dominated
by the quantization error in the DAC. This requires the look-up
table to have two more bits of phase resolution than the 10-bit DAC.
DIGITAL-TO-ANALOG CONVERTER
The AD9832 includes a high impedance current source 10-bit
DAC, capable of driving a wide range of loads at different speeds.
Full-scale output current can be adjusted for optimum power
and external load requirements by using a single external
resistor (RSET).
The DAC is configured for single-ended operation. The load
resistor can be any value required, as long as the full-scale
voltage developed across it does not exceed the voltage compliance
range. Because full-scale current is controlled by RSET, adjustments
to RSET can balance changes made to the load resistor. However,
if the DAC full-scale output current is significantly less than 4 mA,
the linearity of the DAC may degrade.
Rev. E | Page 13 of 28
AD9832
Data Sheet
FUNCTIONAL DESCRIPTION
SERIAL INTERFACE
Table 6. Addressing the Registers
The AD9832 has a serial interface, with 16 bits being loaded
during each write cycle. SCLK, SDATA, and FSYNC are used to
load the word into the AD9832.
A3
0
0
0
0
0
0
0
0
1
1
1
1
1
1
1
1
When FSYNC is taken low, the AD9832 is informed that a word
is being written to the device. The first bit is read into the device
on the next SCLK falling edge with the remaining bits being read
into the device on the subsequent SCLK falling edges. FSYNC
frames the 16 bits; therefore, when 16 SCLK falling edges have
occurred, FSYNC should be taken high again. The SCLK can be
continuous, or alternatively, the SCLK can idle high or low between
write operations.
Table 5. Control Registers
Register
FREQ0 REG
Size
32 bits
FREQ1 REG
32 bits
PHASE0 REG
12 bits
PHASE1 REG
12 bits
PHASE2 REG
12 bits
PHASE3 REG
12 bits
Description
Frequency Register 0. This defines the
output frequency, when FSELECT = 0,
as a fraction of the MCLK frequency.
Frequency Register 1. This defines the
output frequency, when FSELECT = 1,
as a fraction of the MCLK frequency.
Phase Offset Register 0. When PSEL0 =
PSEL1 = 0, the contents of this register
are added to the output of the phase
accumulator.
Phase Offset Register 1. When PSEL0 = 1
and PSEL1 = 0, the contents of this
register are added to the output of the
phase accumulator.
Phase Offset Register 2. When PSEL0 = 0
and PSEL1 = 1, the contents of this
register are added to the output of the
phase accumulator.
Phase Offset Register 3. When PSEL0 =
PSEL1 = 1, the contents of this register
are added to the output of the phase
accumulator.
When writing to a frequency/phase register, the first four bits
identify whether a frequency or phase register is being written to,
the next four bits contain the address of the destination register,
while the 8 LSBs contain the data. Table 6 lists the addresses for
the phase/frequency registers, and Table 7 and Table 8 list the
data structure for each.
For an example on programming the AD9832, see the AN-621
application note, Programming the AD9832/AD9835, at
www.analog.com.
A2
0
0
0
0
1
1
1
1
0
0
0
0
1
1
1
1
A1
0
0
1
1
0
0
1
1
0
0
1
1
0
0
1
1
A0
0
1
0
1
0
1
0
1
0
1
0
1
0
1
0
1
Destination Register
FREQ0 REG 8 L LSBs
FREQ0 REG 8 H LSBs
FREQ0 REG 8 L MSBs
FREQ0 REG 8 H MSBs
FREQ1 REG 8 L LSBs
FREQ1 REG 8 H LSBs
FREQ1 REG 8 L MSBs
FREQ1 REG 8 H MSBs
PHASE0 REG 8 LSBs
PHASE0 REG 8 MSBs
PHASE1 REG 8 LSBs
PHASE1 REG 8 MSBs
PHASE2 REG 8 LSBs
PHASE2 REG 8 MSBs
PHASE3 REG 8 LSBs
PHASE3 REG 8 MSBs
Table 7. 32-Bit Frequency Word
8 H MSBs
16 MSBs
8 L MSBs
8 H LSBs
16 LSBs
8 L LSBs
Table 8. 12-Bit Frequency Word
4 MSBs (The 4 MSBs of the
8-Bit Word Loaded = 0)
8 LSBs
DIRECT DATA TRANSFER AND DEFERRED DATA
TRANSFER
Within the AD9832, 16-bit transfers are used when loading the
destination frequency/phase register. There are two modes for
loading a register, direct data transfer and a deferred data transfer.
With a deferred data transfer, the 8-bit word is loaded into the
defer register (8 LSBs or 8 MSBs). However, this data is not
loaded into the 16-bit data register; therefore, the destination
register is not updated. With a direct data transfer, the 8-bit word is
loaded into the appropriate defer register (8 LSBs or 8 MSBs).
Immediately following the loading of the defer register, the
contents of the complete defer register are loaded into the 16-bit
data register and the destination register is loaded on the next
MCLK rising edge. When a destination register is addressed, a
deferred transfer is needed first followed by a direct transfer.
When all 16 bits of the defer register contain relevant data, the
destination register can then be updated using 8-bit loading
rather than 16-bit loading, that is, direct data transfers can be
used. For example, after a new 16-bit word has been loaded to a
destination register, the defer register will also contain this
word. If the next write instruction is to the same destination
register, the user can use direct data transfers immediately.
Rev. E | Page 14 of 28
Data Sheet
AD9832
When writing to a phase register, the 4 MSBs of the 16-bit word
loaded into the data register should be zero (the phase registers
are 12 bits wide).
Table 10. Controlling the AD9832
D15
1
D14
0
1
1
To alter the entire contents of a frequency register, four write
operations are needed. However, the 16 MSBs of a frequency
word are contained in a separate register to the 16 LSBs.
Therefore, the 16 MSBs of the frequency word can be altered
independent of the 16 LSBs.
Table 9. Commands
C3
0
C2
0
C1
0
C0
0
0
0
0
0
0
1
1
0
0
0
0
1
1
0
1
0
0
1
0
1
0
1
1
0
0
1
1
1
Command
Write 16 phase bits (present 8 bits + 8 bits
in the defer register) to selected PHASEx REG.
Write 8 phase bits to the defer register.
Write 16 frequency bits (present 8 bits +
8 bits in the defer register) to selected the
FREQx REG.
Write 8 frequency bits to the defer register.
Bit D9 (PSEL0) and Bit D10 (PSEL1) are used
to select the PHASEx REG when SELSRC = 1.
When SELSRC = 0, the PHASEx REG is
selected using the PSEL0 and PSEL1 pins.
Bit D11 is used to select the FREQx REG
when SELSRC = 1. When SELSRC = 0, the
FREQx REG is selected using the FSELECT pin.
To control the PSEL0, PSEL1, and FSELECT
bits using only one write, this command is
used. Bit D9 and Bit D10 are used to select
the PHASEx REG, and Bit 11 is used to select
the FREQx REG when SELSRC = 1. When
SELSRC = 0, the PHASEx REG is selected
using the PSEL0 and PSEL1 pins and the
FREQx REG is selected using the FSELECT pin.
Reserved. It configures the AD9832 for
test purposes.
The phase and frequency registers to be used are selected using
the FSELECT, PSEL0, and PSEL1 pins, or the corresponding
bits can be used. Bit SELSRC determines whether the bits or the
pins are used. When SELSRC = 0, the pins are used, and when
SELSRC = 1, the bits are used. When CLR is taken high,
SELSRC is set to 0 so that the pins are the default source. Data
transfers from the serial (defer) register to the 16-bit data register,
and the FSELECT and PSEL registers, occur following the 16th
falling SCLK edge.
Command
Selects source of control for the PHASEx and
FREQx registers and enables synchronization.
Bit D13 is the SYNC bit. When this bit is high,
reading of the FSELECT, PSEL0, and PSEL1 bits/
pins and the loading of the destination register
with data is synchronized with the rising edge of
MCLK. The latency is increased by 2 MCLK cycles
when SYNC = 1. When SYNC = 0, the loading of the
data and the sampling of FSELECT/PSEL0/PSEL1
occurs asynchronously.
Bit D12 is the select source bit (SELSRC). When this
bit equals 1, the PHASEx/FREQx REG is selected
using the FSELECT, PSEL0, and PSEL1 bits. When
SELSRC = 0, the PHASEx/FREQx REG is selected
using the FSELECT, PSEL0, and PSEL1 pins.
SLEEP, RESET, and CLR (clear).
D13 is the SLEEP bit. When this bit equals 1, the
AD9832 is powered down, internal clocks are
disabled, and the current sources and REFOUT of
the DAC are turned off. When SLEEP = 0, the
AD9832 is powered up. When RESET (D12) = 1, the
phase accumulator is set to zero phase that
corresponds to a full-scale output. When CLR
(D11) = 1, SYNC and SELSRC are set to zero. CLR
resets to 0 automatically.
Transfer of the data from the 16-bit data register to the
destination register or from the FSELECT/PSEL register to the
respective multiplexer occurs on the next MCLK rising edge.
Because SCLK and MCLK are asynchronous, an MCLK rising
edge may occur while the data bits are in a transitional state.
This can cause a brief spurious DAC output if the register being
written to is generating the DAC output. To avoid such spurious
outputs, the AD9832 contains synchronizing circuitry.
When the SYNC bit is set to 1, the synchronizer is enabled and
data transfers from the serial register (defer register) to the 16-bit
data register, and the FSELECT/PSEL registers occur following
a two-stage pipeline delay that is triggered on the MCLK falling
edge. The pipeline delay ensures that the data is valid when the
transfer occurs. Similarly, selection of the frequency/phase
registers using the FSELECT/PSELx pins is synchronized with
the MCLK rising edge when SYNC = 1. When SYNC = 0, the
synchronizer is bypassed.
Selecting the frequency/phase registers using the pins is
synchronized with MCLK internally also when SYNC = 1 to
ensure that these inputs are valid at the MCLK rising edge. If
times t11 and t11A are met, then the inputs will be at steady state
at the MCLK rising edge. However, if times t11 and t11A are
violated, the internal synchronizing circuitry will delay the
instant at which the pins are sampled, ensuring that the inputs
are valid at the sampling instant (see Figure 5).
Rev. E | Page 15 of 28
AD9832
Data Sheet
Table 11. Writing to the AD9832 Data Registers
D15
C3
1
D14
C2
D13
C1
D12
C0
D11
A3
D10
A2
D9
A1
D8
A0
D7
MSB
D6
X1
D5
X1
D4
X1
D3
X1
D2
X1
D1
X1
D0
LSB
X = don’t care.
Table 12. Setting SYNC and SELSRC
D15
1
1
D14
0
D13
SYNC
D12
SELSRC
D11
X1
D10
X1
D9
X1
D8
X1
D7
X1
D6
X1
D5
X1
D4
X1
D3
X1
D2
X1
D1
X1
D0
X1
D9
X1
D8
X1
D7
X1
D6
X1
D5
X1
D4
X1
D3
X1
D2
X1
D1
X1
D0
X1
X = don’t care.
Table 13. Power-Down, Resetting and Clearing the AD9832
D15
1
1
D14
1
D13
SLEEP
D12
RESET
D11
CLR
D10
X1
X = don’t care.
LATENCY
FLOWCHARTS
Associated with each operation is a latency. When inputs
FSELECT/PSEL change value, there is a pipeline delay before
control is transferred to the selected register; there is a pipeline
delay before the analog output is controlled by the selected
register. When times t11 and t11A are met, PSEL0, PSEL1, and
FSELECT have latencies of six MCLK cycles when SYNC = 0.
When SYNC = 1, the latency is increased to 8 MCLK cycles.
When times t11 and t11A are not met, the latency can increase by
one MCLK cycle. Similarly, there is a latency associated with
each write operation. If a selected frequency/phase register is
loaded with a new word, there is a delay of 6 to 7 MCLK cycles
before the analog output will change (there is an uncertainty of
one MCLK cycle regarding the MCLK rising edge at which the
data is loaded into the destination register). When SYNC = 1,
the latency is 8 or 9 MCLK cycles.
The flowchart in Figure 24 shows the operating routine for the
AD9832. When the AD9832 is powered up, the part should be
reset, which resets the phase accumulator to zero so that the
analog output is at full scale. To avoid spurious DAC outputs
while the AD9832 is being initialized, the RESET bit should be
set to 1 until the part is ready to begin generating an output.
Taking CLR high sets SYNC and SELSRC to 0 so that the
FSELECT/PSELx pins are used to select the frequency/phase
registers, and the synchronization circuitry is bypassed. A write
operation is needed to the SYNC/SELSRC register to enable the
synchronization circuitry or to change control to the FSELECT/
PSEL bits. RESET does not reset the phase and frequency registers.
These registers will contain invalid data and, therefore, should
be set to a known value by the user. The RESET bit is then set to 0
to begin generating an output. A signal will appear at the DAC
output 6 MCLK cycles after RESET is set to 0.
The analog output is fMCLK/232 × FREG, where FREG is the value
loaded into the selected frequency register. This signal is phase
shifted by the amount specified in the selected phase register
(2π/4096 × PHASEx REG, where PHASEx REG is the value
contained in the selected phase register).
Control of the frequency/phase registers can be interchanged
from the pins to the bits.
Rev. E | Page 16 of 28
Data Sheet
AD9832
DATA WRITE
FREG[0] = fOUT0/fMCLK × 232
FREG[1] = fOUT1/fMCLK × 232
PHASEREG [3:0] = DELTA PHASE[0, 1, 2, 3]
SELECT DATA SOURCES
SET FSELECT
SET PSEL0, PSEL1
INITIALIZATION
WAIT 6 MCLK CYCLES (8 MCLK CYCLES IF SYNC = 1)
DAC OUTPUT
VOUT = VREFIN × 6.25 × ROUT/RSET × (1 + SIN(2π(FREG × fMCLK × t/232 + PHASEREG/212)))
CHANGE PHASE?
YES
NO
NO
CHANGE fOUT?
YES
CHANGE fOUT?
CHANGE PHASEREG?
YES
NO
CHANGE PSEL0, PSEL1
09090-024
NO
YES
Figure 24. Flowchart for the AD9832 Initialization and Operation
INITIALIZATION
CONTROL REGISTER WRITE
SET SLEEP
RESET = 1
CLR = 1
SET SYNC AND/OR SELSRC TO 1
YES
NO
CONTROL REGISTER WRITE
SYNC = 1
AND/OR
SELSRC = 1
WRITE INITIAL DATA
FREG[0] = fOUT0/fMCLK × 232
FREG[1] = fOUT1/fMCLK × 232
PHASEREG[3:0] = DELTA PHASE[0, 1, 2, 3]
SET PINS OR FREQUENCY/PHASE REGISTER WRITE
SET FSELECT, PSEL0 AND PSEL1
CONTROL REGISTER WRITE
SLEEP = 0
RESET = 0
CLR = 0
Figure 25. Initialization
Rev. E | Page 17 of 28
09090-025
CHANGE FSELECT
AD9832
Data Sheet
DATA WRITE
DEFERRED TRANSFER WRITE
WRITE 8 BITS TO DEFER REGISTER
DIRECT TRANSFER WRITE
WRITE PRESENT 8 BITS AND 8 BITS IN
DEFER REGISTER TO DATA REGISTER
CHANGE 16 BITS
YES
WRITE ANOTHER WORD TO THIS YES
REGISTER?
NO
CHANGE
8 BITS ONLY
09090-026
NO
WRITE A WORD TO ANOTHER REGISTER
Figure 26. Data Writes
SELECT DATA SOURCES
NO
YES
SELSRC = 0
SET PINS
SET FSELECT
SET PSEL0
SET PSEL1
SELSRC = 1
FREQUENCY/PHASE REGISTER WRITE
SET FSELECT
SET PSEL0
SET PSEL1
Figure 27. Selecting Data Sources
Rev. E | Page 18 of 28
09090-027
FSELECT/PSEL PINS BEING USED?
Data Sheet
AD9832
APPLICATIONS INFORMATION
The AD9832 has four phase registers; this enables the part to
perform PSK. With phase shift keying, the carrier frequency is
phase shifted, the phase being altered by an amount which is
related to the bit stream being input to the modulator. The
presence of four shift registers eases the interaction needed
between the DSP and the AD9832.
The AD9832 is also suitable for signal generator applications.
With its low current consumption, the part is suitable for
applications where it can be used as a local oscillator. In addition,
the part is fully specified for operation with a 3.3 V ± 10%
power supply. Therefore, in portable applications where current
consumption is an important issue, the AD9832 is perfect.
GROUNDING AND LAYOUT
The printed circuit board (PCB) that houses the AD9832
should be designed so that the analog and digital sections are
separated and confined to certain areas of the board. This
facilitates the use of ground planes that can be easily separated.
A minimum etch technique is generally best for ground planes
because it gives the best shielding. Digital and analog ground
planes should only be joined in one place. If the AD9832 is the
only device requiring an AGND-to-DGND connection, the
ground planes should be connected at the AGND and DGND
pins of the AD9832. If the AD9832 is in a system where multiple
devices require AGND-to-DGND connections, the connection
should be made at one point only, a star ground point that
should be established as close as possible to the AD9832.
Avoid running digital lines under the device as these couple
noise onto the die. The analog ground plane should be allowed
to run under the AD9832 to avoid noise coupling. The power
supply lines to the AD9832 should use as large a track as possible
to provide low impedance paths and reduce the effects of glitches
on the power supply line. Fast switching signals, such as clocks,
should be shielded with digital ground to avoid radiating noise
to other sections of the board. Avoid crossover of digital and analog
signals. Traces on opposite sides of the board should run at right
angles to each other, which reduces the effects of feedthrough
through the board. A microstrip technique is by far the best,
but it is not always possible with a double-sided board. In this
technique, the component side of the board is dedicated to
ground planes, while signals are placed on the other side.
Good decoupling is important. The analog and digital supplies
to the AD9832 are independent and separately pinned out to
minimize coupling between analog and digital sections of the
device. All analog and digital supplies should be decoupled to
AGND and DGND, respectively, with 0.1 µF ceramic capacitors
in parallel with 10 µF tantalum capacitors. To achieve the best
from the decoupling capacitors, they should be placed as close
as possible to the device, ideally right up against the device. In
systems where a common supply is used to drive both the AVDD
and DVDD of the AD9832, it is recommended that the AVDD
supply of the system be used. This supply should have the
recommended analog supply decoupling between the AVDD
pins of the AD9832 and AGND and the recommended digital
supply decoupling capacitors between the DVDD pins and DGND.
INTERFACING THE AD9832 TO MICROPROCESSORS
The AD9832 has a standard serial interface that allows the part
to interface directly with several microprocessors. The device
uses an external serial clock to write the data/control information
into the device. The serial clock can have a frequency of 20 MHz
maximum. The serial clock can be continuous, or it can idle
high or low between write operations. When data/control
information is being written to the AD9832, FSYNC is taken
low and held low while the 16 bits of data are being written into
the AD9832. The FSYNC signal frames the 16 bits of information
being loaded into the AD9832.
AD9832 TO ADSP-2101 INTERFACE
Figure 28 shows the serial interface between the AD9832 and
the ADSP-2101. The ADSP-2101 should be set up to operate
in SPORT transmit alternate framing mode (TFSW = 1). The
ADSP-2101 is programmed through the SPORT control register
and should be configured as follows: internal clock operation
(ISCLK = 1), active low framing (INVTFS = 1), 16-bit word
length (SLEN = 15), internal frame sync signal (ITFS = 1),
and a frame sync for each write operation (TFSR = 1) must
be generated. Transmission is initiated by writing a word to the
Tx register after SPORT is enabled. The data is clocked out on
each rising edge of the serial clock and clocked into the AD9832
on the SCLK falling edge.
Rev. E | Page 19 of 28
ADSP-2101*
AD9832*
TFS
FSYNC
DT
SDATA
SCLK
SCLK
*ADDITIONAL PINS OMITTED FOR CLARITY.
Figure 28. ADSP-2101 to AD9832 Interface
09090-028
The AD9832 contains functions that make it suitable for
modulation applications. The part can be used to perform
simple modulation, such as FSK, and more complex modulation
schemes, such as GMSK and QPSK, can also be implemented
using the AD9832. In an FSK application, the two frequency
registers of the AD9832 are loaded with different values; one
frequency represents the space frequency while the other represents
the mark frequency. The digital data stream is fed to the FSELECT
pin, which causes the AD9832 to modulate the carrier frequency
between the two values.
AD9832
Data Sheet
Figure 29 shows the serial interface between the AD9832 and
the 68HC11/68L11 microcontroller. The microcontroller is
configured as the master by setting bit MSTR in the SPCR to 1,
which provides a serial clock on SCK while the MOSI output
drives the serial data line SDATA. Because the microcontroller does
not have a dedicated frame sync pin, the FSYNC signal is derived
from a port line (PC7). The setup conditions for correct operation
of the interface are as follows: SCK idles high between write
operations (CPOL = 0), and data is valid on SCK falling edge
(CPHA = 1). When data is transmitted to the AD9832, the FSYNC
line is taken low (PC7). Serial data from the 68HC11/68L11 is
transmitted in 8-bit bytes with only 8 falling clock edges occurring
in the transmit cycle. Data is transmitted MSB first. To load
data into the AD9832, PC7 is held low after the first 8 bits are
transferred and a second serial write operation is performed to
the AD9832. Only after the second 8 bits have been transferred
should FSYNC be taken high again.
FSYNC
SDATA
SCK
P3.3
FSYNC
RxD
SDATA
TxD
SCLK
*ADDITIONAL PINS OMITTED FOR CLARITY.
Figure 30. 80C51/80L51 to AD9832 Interface
Figure 31 shows the interface between the AD9832 and the
DSP56002. The DSP56002 is configured for normal mode
asynchronous operation with a gated internal clock (SYN = 0,
GCK = 1, SCKD = 1). The frame sync pin is generated internally
(SC2 = 1), the transfers are 16-bits wide (WL1 = 1, WL0 = 0),
and the frame sync signal frames the 16 bits (FSL = 0). The
frame sync signal is available on Pin SC2, but it needs to be
inverted before being applied to the AD9832. The interface to the
DSP56000/DSP56001 is similar to that of the DSP56002.
SCLK
*ADDITIONAL PINS OMITTED FOR CLARITY.
AD9832*
Figure 29. 68HC11/68L11 to AD9832 Interface
AD9832 TO 80C51/80L51 INTERFACE
Figure 30 shows the serial interface between the AD9832 and
the 80C51/80L51 microcontroller. The microcontroller operates
in Mode 0 so that TXD of the 80C51/80L51 drives SCLK of the
AD9832, while RXD drives the serial data line SDATA. The FSYNC
signal is again derived from a bit programmable pin on the port
(P3.3 being used in the diagram). When data is transmitted to
the AD9832, P3.3 is taken low. The 80C51/80L51 transmits data
in 8-bit bytes; therefore, only 8 falling SCLK edges occur in each
cycle. To load the remaining 8 bits to the AD9832, P3.3 is held
low after the first 8 bits have been transmitted and a second
Rev. E | Page 20 of 28
DSP56002*
AD9832*
SC2
FSYNC
STD
SDATA
SCK
SCLK
*ADDITIONAL PINS OMITTED FOR CLARITY.
Figure 31. AD9832 to DSP56002 Interface
09090-031
PC7
MOSI
80C51/80L51*
AD9832 TO DSP56002 INTERFACE
AD9832*
09090-029
68HC11/68L11*
write operation is initiated to transmit the second byte of data.
P3.3 is taken high following the completion of the second write
operation. SCLK should idle high between the two write operations.
The 80C51/80L51 outputs the serial data in a format that has
LSB first. The AD9832 accepts MSB first (the 4 MSBs being the
control information, the next 4 bits being the address, while the
8 LSBs contain the data when writing to a destination register).
Therefore, the transmit routine of the 80C51/80L51 must consider
this format and rearrange the bits so that the MSB is output first.
09090-030
AD9832 TO 68HC11/68L11 INTERFACE
Data Sheet
AD9832
EVALUATION BOARD
SYSTEM DEMONSTRATION PLATFORM
The system demonstration platform (SDP) is a hardware and
software evaluation tool for use in conjunction with product
evaluation boards. The SDP board is based on the Blackfin® BF527
processor with USB connectivity to the PC through a USB 2.0 high
speed port.
Note that the SDP board is sold separately from the AD9832
evaluation board.
AD9832 TO SPORT INTERFACE
The Analog Devices SDP board has a SPORT serial port that is
used to control the serial inputs to the AD9832. The connections
are shown in Figure 32.
AD9832
SCLK
09090-040
SPORT_DTO
FSYNC
SDATA
ADSP-BF527
Figure 33. AD9832 Evaluation Software
02705-039
SPORT_TFS
SPORT_TSCLK
Figure 32. SDP to AD9832 Interface
The AD9832 evaluation board allows designers to evaluate the
high performance AD9832 DDS modulator with a minimum of
effort. The GUI interface for the AD9832 evaluation board is
shown in Figure 33.
The DDS evaluation kit includes a populated, tested AD9832
PCB. Software is available with the evaluation board that allows
the user to easily program the AD9832. The schematics of the
AD9832 evaluation board are shown in Figure 34 and Figure 35.
The software runs on any IBM-compatible PC that has Microsoft®
Windows® 95, Windows 98, Windows ME, Windows 2000 NT®,
or Windows 7 installed.
Additional details can be found in the EVAL-AD9832SDZ data
sheet that is available on the software CD and on the AD9832
product page.
XO vs. EXTERNAL CLOCK
The AD9832 can operate with master clocks up to 25 MHz. A
25 MHz general oscillator is included on the evaluation board.
However, this oscillator can be removed and, if required, an
external CMOS clock can be connected to the part.
Two options for the general oscillator are
•
AEL 301 series crystals oscillators (AEL Crystals, Ltd.)
•
SG-310SCN oscillators (Epson Toyocom Corporation)
POWER SUPPLY
Power to the AD9832 evaluation board can be provided from
a USB connector or externally through pin connections. The
power leads should be twisted to reduce ground loops.
Rev. E | Page 21 of 28
AD9832
Data Sheet
EVALUATION BOARD SCHEMATICS
09090-034
Figure 34. AD9832 Evaluation Board Schematic, Part A
Rev. E | Page 22 of 28
Data Sheet
AD9832
09090-035
Figure 35. AD9832 Evaluation Board Schematic, Part B—J1 Header Connector
Rev. E | Page 23 of 28
AD9832
Data Sheet
09090-036
EVALUATION BOARD LAYOUT
09090-037
Figure 36. AD9832 Evaluation Board Component Side
09090-038
Figure 37. AD9832 Evaluation Board Silkscreen
Figure 38. AD9832 Evaluation Board Solder Side
Rev. E | Page 24 of 28
Data Sheet
AD9832
ORDERING INFORMATION
BILL OF MATERIALS
Table 14.
Reference Designator
C1, C3, C5, C6, C11, C12, C13
C7
C2, C4
C8,C9
C10
CLK 1, FSEL1, IOUT,
PSEL11, REFIN, PSEL01
FSYNC, IOUT_, MCLK , SCLK,
SDATA
G2
J1
J2, J3
LK3, LK5, LK6
LK1
R71, R81, R91
R121
R14
R15
R17,R18
R1, R21, R3, R41, R61,
R5, R111, R10,R162
R13
U4
U1
U5
Y2
Description
0.1 µF, ±10%, 50 V, X7R, ceramic capacitor
0.01 µF, ±10%, 10 V, 0603, X5R, capacitor
10 µF, ±10%,10 V, SMD tantalum capacitor
1 µF, ±10%,10 V,Y5V, 0603, ceramic capacitor
0.1 µF, ±10%, 16 V, X7R, 0603, capacitor
Straight PCB mount SMB jack, 50 Ω
Manufacturer
Murata
Kemet
AVX
Yageo
Multicomp
Tyco
Part Number
GRM188R71H104KA93D
C0603C103K5RACTU
TAJA106K010R
CC0603ZRY5V6BB105
B0603R104KCT
1-1337482-0
Red test point
Vero
20-313137
Copper short
120-way connector, 0.6 mm pitch receptacle
2-pin terminal block (5 mm pitch)
3-pin SIL header and shorting link
2-pin SIL header and shorting link
10 kΩ, ±1%, 0603, SMD resistor
50 Ω, ±1%, 0603, SMD resistor
3.9 kΩ, ±1%, SMD resistor
300 Ω, ±1%, SMD resistor
100 KΩ, ±1%, SMD resistor
0 Ω, ±1%, 0603, SMD resistor
Not applicable
HRS (Hirose)
Campden
Harwin
Harwin
Multicomp
Multicomp
Multicomp
Multicomp
Multicomp
Multicomp
Not applicable
FX8-120S-SV(21)
CTB5000/2
M20-9990345 and M7567-05
M20-9990246
MC 0.063W 0603 10K
MC 0.063W 0603 50r
MC 0.063W 0603 6K8
MC 0.063W 0603 200r
MC 0.063W 0603 1% 100K
MC 0.063W 0603 0r
330 kΩ, ±5%, SMD resistor
45 mW power, 3 V to 5.5 V, 25 MHz complete DDS
32K I2C serial EEPROM 8-lead MSOP
High accuracy anyCAP® 100 mA low dropout linear regulator
25 MHz, 3 mm × 2 mm SMD clock oscillator
Multicomp
Analog Devices
Micro Chip
Analog Devices
AEL Crystals
MC 0.063W 0603 330KR
AD9832BRUZ
24LC32A-I/MS
ADP3301ARZ-3.3
AEL301 series
Do not install.
DNP
1
2
Rev. E | Page 25 of 28
AD9832
Data Sheet
OUTLINE DIMENSIONS
5.10
5.00
4.90
16
9
4.50
4.40
4.30
6.40
BSC
1
8
PIN 1
1.20
MAX
0.15
0.05
0.20
0.09
0.65
BSC
0.30
0.19
COPLANARITY
0.10
SEATING
PLANE
8°
0°
0.75
0.60
0.45
COMPLIANT TO JEDEC STANDARDS MO-153-AB
Figure 39. 16-Lead Thin Shrink Small Outline Package [TSSOP]
(RU-16)
Dimensions shown in millimeters
ORDERING GUIDE
Model 1
AD9832BRU
AD9832BRU-REEL7
AD9832BRUZ
AD9832BRUZ-REEL
AD9832BRUZ-REEL7
EVAL-AD9832SDZ
1
Temperature Range
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
−40°C to +85°C
Package Description
16-Lead Thin Shrink Small Outline Package [TSSOP]
16-Lead Thin Shrink Small Outline Package [TSSOP]
16-Lead Thin Shrink Small Outline Package [TSSOP]
16-Lead Thin Shrink Small Outline Package [TSSOP]
16-Lead Thin Shrink Small Outline Package [TSSOP]
Evaluation Board
Z = RoHS Compliant Part.
Rev. E | Page 26 of 28
Package Option
RU-16
RU-16
RU-16
RU-16
RU-16
Data Sheet
AD9832
NOTES
Rev. E | Page 27 of 28
AD9832
Data Sheet
NOTES
©1999–2013 Analog Devices, Inc. All rights reserved. Trademarks and
registered trademarks are the property of their respective owners.
D09090-0-2/13(E)
Rev. E | Page 28 of 28
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