Evaluation Board User Guide
UG-366
One Technology Way • P.O. Box 9106 • Norwood, MA 02062-9106, U.S.A. • Tel: 781.329.4700 • Fax: 781.461.3113 • www.analog.com
Evaluation Board for PWM, Step-Down DC-to-DC Controller with
Margining and Tracking
INTRODUCTION
This data sheet describes the design, operation, and test of the
ADP1822 standard evaluation board. In all tests, the board is
operated from an input voltage range of 9 V to 15 V, and
generates up to 10 A at VOUT = 1.8 V. The switching frequency is
fixed at 300 kHz.
GENERAL DESCRIPTION
The ADP1822 is a versatile and inexpensive synchronous buck
PWM controller. The converter power input voltage range is
1 V to 24 V, while the ADP1822 controller is specified from
3.0 V to 5.5 V. The ADP1822 free-running frequency is logicselectable at either 300 kHz or 600 kHz. Alternatively, it can be
synchronized to an external clock at any frequency between
300 kHz and 1.2 MHz. The internal gate drivers control an all
N-channel power stage to regulate a converter output voltage as
low as 0.6 V with up to 20 A load current.
The ADP1822 includes an adjustable soft start to limit input
inrush current and to facilitate sequencing. It provides currentlimit and short-circuit protection, and a power-good logic output.
The ADP1822 is well suited for a wide range of power
applications, such as DSP and processor core power in
telecommunications, medical imaging, high performance
servers, and industrial applications.
SPECIFICATIONS
Table 1. Evaluation Board Specifications
Description
VIN
VOUT
Frequency
Maximum IOUT
Current Limit
High and Low Voltage Margining
Parameter
12 V
1.8 V
300 kHz
10 A
15 A
5%
06388-016
The regulated output of the ADP1822 can track another power
supply and be dynamically adjusted up or down with the
margining control inputs of the controller.
Figure 1. ADP1822 Evaluation Board (ADP1822-EVALZ)
PLEASE SEE THE LAST PAGE FOR AN IMPORTANT
WARNING AND LEGAL TERMS AND CONDITIONS.
Rev. A | Page 1 of 16
UG-366
Evaluation Board User Guide
TABLE OF CONTENTS
Introduction ...................................................................................... 1
Setting the Soft Start .....................................................................5
General Description ......................................................................... 1
Output Voltage Tracking ..............................................................5
Specifications..................................................................................... 1
Output Voltage Margining ...........................................................6
Revision History ............................................................................... 2
Control Loop Design and Equations ..............................................7
Test Instructions ............................................................................... 3
Power Stage Transfer Function ....................................................7
Component Selection ....................................................................... 4
Control Circuit and Transfer Function ......................................7
Input Capacitor ............................................................................. 4
Overall Loop Gain .........................................................................8
Output Inductor ........................................................................... 4
Test Results and Major Waveforms .................................................9
Output Capacitor .......................................................................... 4
PCB Layout Guidelines .................................................................. 11
MOSFET Selection ....................................................................... 4
Evaluation Board Schematic and Layout..................................... 12
Output Voltage .............................................................................. 5
Ordering Information .................................................................... 14
Current Limit Set Resistor ........................................................... 5
Bill of Materials ........................................................................... 14
REVISION HISTORY
12/11—Rev. 0 to Rev. A
Updated Format .................................................................. Universal
Changed EVAL-ADP1822 to ADP1822-EVAL .............. Universal
11/06—Revision 0: Initial Version
Rev. A | Page 2 of 16
Evaluation Board User Guide
UG-366
TEST INSTRUCTIONS
Table 2. Jumper and Connector Descriptions
Test instructions:
1.
Make sure that Jumper 2 is open. Power on the board
(output voltage is at 1.8 V).
2.
If Jumper 1 is shorted, replace the inductor to another
value to fit 600 kHz operation.
3.
If Jumper 3 is shorted, the output high margining is at
1.89 V. If Jumper 4 is open, the output low margining is at
1.71 V.
4.
Verify the output voltage tracking features when
connecting the external generator to the TRKN point.
5.
Use the PWGD point for monitoring operation behavior.
Name
M1
M2
M3
M4
Jumper 1
Jumper 2
Jumper 3
Jumper 4
Description
VIN
GND In
VIN
GND Out
Open: 300 kHz
Short: 600 kHz
Open: enable the board
Short: disable the board
Open: output voltage normal mode.
Short: active voltage margin
Open: high margin
Short: low margin
Default
Status
Open
Open
Open
Open
Table 3. Margining Description
MAR
Low (Jumper 3
open)
High (Jumper 3
shorted)
High (Jumper 3
shorted)
Rev. A | Page 3 of 16
MSEL
X
Voltage Margin
None
High (Jumper 4
open)
Low (Jumper 4
shorted)
High margin (FB
connected to MUP)
Low margin (FB
connected to MDN)
UG-366
Evaluation Board User Guide
COMPONENT SELECTION
INPUT CAPACITOR
In continuous mode, the source current of the high-side
MOSFET is a square wave of duty cycle VOUT/VIN. To prevent
large voltage transients, use a low ESR input capacitor sized for
the maximum rms current. The maximum rms capacitor
current is given by IL√D(1 − D)
OUTPUT INDUCTOR
In high switching applications, if the inductor is too big, the
dI/dt is too low and cannot respond to load changes quickly. If
the inductor is too small, the output ripple would be high.
Therefore, if good transient response is needed, smaller
inductors and larger capacitors are better, within the constraint
of the maximum allowed ripple current in the capacitor and the
maximum dissipation of the core (core temperature).
The output inductor can be chosen according to the following
equation:
L=
VOUT
(1 − D)
IOUT K CR f SW
(1)
C OUT, min2 =
Select an output capacitance that is greater than both COUT, min1
and COUT, min2.
Make sure that the ripple current rating of the output capacitors
is greater than the following current:
For the low-side (synchronous) MOSFET, the dominant loss is
the conduction loss. It can be calculated as
The selection of COUT is determined by the ESR and the
capacitance. The output voltage ripple can be approximated as
(2)
ESR affects the output voltage ripple; thus, an MLCC capacitor
is recommended because of its low ESR.
During a load transient on the output, the amount of
capacitance needed is determined by the maximum energy
stored in the inductor. The capacitance must be sufficient to
absorb the change in inductor current when a high current to
low current transition occurs and to supply the load when a low
current to high current transition occurs.
∆I OUT L
2VOUT ∆Vup
∆I 2
PC , low = (1 − D) I OUT 2 + L
12
R DSON
(6)
The gate charge loss is approximated by the following equation:
PG = VG Q G f SW
Generally, the voltage ripple caused by the capacitance or ESR
depends on the capacitor chosen.
C OUT,min1 =
(5)
12
The choice of MOSFET directly affects the dc-to-dc converter
performance. The MOSFET must have low on resistance
(RDSON) to reduce the conduction loss, and low gate charge to
reduce switching loss.
OUTPUT CAPACITOR
2
∆I L 2
MOSFET SELECTION
Generally, Kcr should be chosen around 20% ~ 40%.
(4)
ΔIOUT is the step load.
ΔVup is the output voltage overshoot when the load is
stepped down.
ΔVdown is the output voltage overshoot when the load is
stepped up.
VIN is the input voltage.
COUT,min1 is the minimum capacitance according to the overshoot
voltage ΔVup.
COUT,min2 is the minimum capacitance according to the overshoot
voltage ΔVdown.
where:
1
∆VOUT = ∆I L ESR +
8 f SW COUT
2(V IN − VO UT ) ∆Vdown
where:
I COUT =
VOUT is the output voltage.
IOUT is the rated output current.
KCR is the ratio of current ripple, ΔIL/IO.
fSW is the switching frequency.
D is the duty cycle
∆I OUT 2 L
(7)
where:
VG is the driver voltage.
QG is the MOSFET total gate charge.
The high-side (switching) MOSFET has to be able to handle
conduction loss and switching loss. The high-side MOSFET
switching loss is approximated by the equation
PT =
V IN I L (t R + t F ) f SW
2
where tR and tF are the rise and fall times of the MOSFET.
(3)
Rev. A | Page 4 of 16
(8)
Evaluation Board User Guide
UG-366
In normal operation, the direction of current flow through the
low-side FET causes a negative voltage to appear on its drain.
This voltage is V = IR, where I is the instantaneous FET current
and R is its RDSON. A +42 μA current source at the ADP1822
CSL pin causes a fixed voltage drop in the current sense resistor
that is connected from the CSL pin to the drain of the low-side
FET. This current through the current limit set resistor produces
a voltage in the opposite direction, thus raising (in the positive
direction) the potential at the CSL pin. The resulting net voltage
on the CSL pin is compared with ground. During normal
operation, the CSL pin stays above ground potential. The
overcurrent protection circuitry is triggered when increased
FET current produces increased negative voltage on the lowside MOSFET drain, thus causing the voltage on the CSL pin to
go negative with respect to ground.
tR and tF can be calculated using
Q GS
+ Q GD
2
tR =
VG − VSP
RG
and
Q GS
+ Q GD
2
tF =
VSP
RG
where:
QGS and QGD are provided in the MOSFET data sheet.
RG is the gate resistance
VSP is approximated using
VSP ≈ VTH +
Therefore, the resistor RCSL can be calculated from the following
equation:
I O UT
gm
RCSL
where gm is the MOSFET transconductance.
The high-side MOSFET conduction loss can be calculated as
PC , high
∆I 2
= D I OUT 2 + L
12
R DSON
(9)
The regulation threshold at the FB pin is 0.6 V, and the
maximum input bias current is 100 nA. This bias current can
introduce significant error if the divider impedance is too high.
In order to get the best accuracy, the bottom resistor, R2, should
be no higher than 50 kΩ. On the other hand, very low values of
R2 will dissipate excess power. For R2, a 1% resistor with a value
between 1 kΩ and 10 kΩ is recommended.
The upper divider is then set using the following formula (it
should also be a 1% type):
VOUT − 0.6
(10)
0. 6
CURRENT LIMIT SET RESISTOR
The voltage on the CSL pin can be calculated by the following
formula:
∆I
VCSL = I CSL RCSL + RDSON _ low − I L + L
2
(
)
(12)
SETTING THE SOFT START
OUTPUT VOLTAGE
R1 = R2
∆I
Ilimit + L RDSON _ low
2
=
ICSL
RDSON _ low (11)
where:
The soft start characteristic is set by the capacitor connected
from SS to GND. The ADP1822 charges CSS to 0.8 V through an
internal resistor. The soft start period (tSS) is achieved when
VCSS = 0.6 V.
CSS =
t SS
0
.6
− ln 1 −
× 100 kΩ
0. 8
(13)
where 100 kΩ is the internal resistor.
OUTPUT VOLTAGE TRACKING
The ADP1822 features an internal comparator that forces the
output voltage to track an external voltage at startup, which
prevents the output voltage from exceeding the tracking voltage.
The comparator turns off the high-side switch if the positive
tracking (TRKP) input voltage exceeds the negative tracking
(TRKN) input voltage. Connect TRKP to the output voltage and
drive TRKN with the voltage to be tracked. If the voltage at
TRKN is below the regulation voltage, the output voltage at
TRKN is below the regulation voltage, and the output voltage is
limited to the voltage at TRKN. If the voltage at TRKN is above
the regulation voltage, the output voltage regulates the desired
voltage set by the voltage divider.
VCSL is the voltage on the CSL pin.
ICSL is the current out from the CSL pin, ICSL = 42 μA.
RCSL is the current limited resistor.
RDSON_low is the conduction resistor of the lower side MOSFET.
IL is the output current.
ΔIL is the output current ripple.
Rev. A | Page 5 of 16
UG-366
Evaluation Board User Guide
OUTPUT VOLTAGE MARGINING
Table 4. Voltage Margining Control
The ADP1822 features output voltage margining. MSEL is the
margin select input. Drive MSEL high to activate the voltage
margining feature. Drive MSEL low to regulate the output
voltage to the nominal value. If not used, connect MSEL to
GND. MAR is the margin control input. MAR is used with
MSEL to control output voltage margining. MAR chooses
between high voltage and low voltage margining when MSEL is
driven high. If not used, connect MAR to GND.
MAR
Low
High
High
The internal switches from FB are connected to MUP and
MSEL terminals to determine the high and low margining. The
high voltage is margined by switching a resistor from FB to
GND, and the low voltage is margined by switching a resistor
from FB to the output voltage.
Rev. A | Page 6 of 16
MSEL
X
High
Low
Voltage Margin
None
High margin (FB connected to MUP)
Low margin (FB connected to MDN)
Evaluation Board User Guide
UG-366
CONTROL LOOP DESIGN AND EQUATIONS
Figure 2 is a simplified schematic diagram of the overall control loop.
VIN
HIGH SIDE
DRIVER
VOUT
L1
RL1
RC
LOW SIDE
DRIVER
C1
R9
R8
C20
C21
OUT
COMP
R11
C22
R10
VREF
06388-002
VFB
OUT
Figure 2. Control Loop
POWER STAGE TRANSFER FUNCTION
The equation for the compensation transfer function is
The power stage transfer function of the ADP1822 is given by
the following equation:
VOUT (s)
GVD (s) =
GVD (s) =
(14)
D( s )
1 + RC × C × s
VIN
×
RL
s
s2
1+
1+
+
R
Q ωO ωO2
(15)
f Z1 =
RL + R
f Z2 =
RC + R
LC
RL
Q=
L
R
R
f P1
+1
+ (RL + RC ) × C +
RC RLC
R
⋅
1
ωO
f P2
RC is the ESR of the output capacitor.
RL is the series resistance of output inductor.
CONTROL CIRCUIT AND TRANSFER FUNCTION
Refer to the compensation circuit shown in Figure 3.
VOUT
C19
R4
R1
R3
C17
VCOMP
06388-003
OUT
VREF
(16)
R3
R1
1
2πR3C17
1
2π(R1 + R 2)C18
1
=
C17 ⋅ C19
2πR3
C17 + C19
1
=
2πR4C18
The switching frequency is 300 kHz. For best performance, set
the crossover frequency to about 1/10 of switching frequency,
fSW, or around 60 kHz. Lower crossover frequencies cause poor
dynamic response, while higher crossover frequencies can cause
instability. The best performance usually results from the
highest possible crossover frequency that allows adequate gain
and phase margins. A phase margin in the range of 40° to 60° is
recommended.
C18
R2
1 + s
2πf Z 2
1 + s
2πf P 2
where:
k=−
where:
ωO =
1 + s
2πf Z1
G EA (s) = k
1 + s
2πf P1
Figure 3. Compensation Circuit
Rev. A | Page 7 of 16
UG-366
Evaluation Board User Guide
OVERALL LOOP GAIN
The transfer function for the overall control loop can be written as
T (s ) =
GVD (s) × G EA (s)
VRAMP
(17)
where VRAMP is the PWM peak ramp voltage (typically 1.25 V) of
the ADP1822 controller.
Use the following guidelines to select the compensation
components:
1.
Set the loop gain cross frequency fC. A good choice is to
place the cross frequency fC at fSW/10 for fast response.
2.
Cancel ESR zero fZ by compensator pole fP1.
3.
Place the high frequency pole fP2 to achieve maximum
attenuation of switching ripple and high frequency noise.
4.
Place two compensator zeros nearby at the power stage
resonant frequency fO. Typically, place fZ1 below fO and
place fZ2 between fO and fC.
5.
Check the phase margin to ensure good regulation
performance.
Rev. A | Page 8 of 16
Evaluation Board User Guide
UG-366
TEST RESULTS AND MAJOR WAVEFORMS
T
T
Δ: 16.8mV
@: –7.60mV
1
Δ: 20.0mV
@: –9.20mV
A CH1
1.20mV
CH1 20.0mV
Figure 4. Output Voltage Ripple, Without Load,
Channel 1: Output Voltage
M4.00µs
T 42.80%
A CH1
1.20mV
06388-005
M4.00µs
T 42.80%
5.20A
06388-007
CH1 20.0V
06388-004
1
Figure 7. Output Voltage Ripple,10 A,
Channel 1: Output Voltage
95
T
VIN = 9V
1
VIN = 15V
85
VIN = 12V
80
3
70
0
2
4
6
IO (A)
8
10
12
06388-006
75
Δ: 62.8mV
@: –32.8mV
CH1 20.0mV
CH3 5.00A Ω
M200µs
A CH3
T
405.200µs
Figure 8. Load Transient Response,
Channel 1: Output Voltage (AC-Coupled), Channel 3: Output Current
Figure 5. Efficiency vs. Load Current
T
T
Δ: 1.76V
@: 4.44V
Δ: 1.32mV
@: 1.78mV
2
3
4
CH1 1.00V
CH3 1.00V
M20.0ms
T 72.60%
A CH3
1.86V
Figure 6. Output Tracking,
Channel 1: Output Voltage, Channel 3: Tracking Input
CH3 2.00V
CH2 2.00V
CH4 100mV
M4.00ms
T 29.80%
A CH3
1.56V
06388-009
1
3
06388-008
EFFICIENCY (%)
90
Figure 9. Output Voltage with Margin Up and Margin Down,
Channel 2: MAR Pin (Blue Trace), Channel 3: MSEL Pin (Pink Trace), Channel
4: Output Voltage
Rev. A | Page 9 of 16
UG-366
Evaluation Board User Guide
T
T
2
3
4
4
CH3 2.00V
CH2 2.00V
CH4 100mV
M1.00ms
T 29.80%
A CH2
1.56V
06388-010
2
3
CH3 2.00V
140
80
120
60
80
60
0
40
–20
PHASE
20
–40
–60
10
100
1k
10k
FREQUENCY (Hz)
100k
1M
0
06388-012
GAIN (dB)
GAIN
20
PHASE (Degrees)
100
40
M1.00ms
T 31.40%
A CH2
1.56V
Figure 12. Output Voltage Margin Up,
Channel 2: MAR Pin, Channel 3: MSEL Pin, Channel 4: Output Voltage
Figure 10. Output Voltage Margin Down,
Channel 2: MAR Pin, Channel 3: MSEL Pin, Channel 4: Output Voltage
100
CH2 2.00V
CH4 100mV
06388-011
Δ: 1.76V
@: 4.44V
Δ: 1.76V
@: 4.44V
Figure 11. Control Loop,
Cross Frequency: 35.4 kHz, Phase Margin: 63.1°
Rev. A | Page 10 of 16
Evaluation Board User Guide
UG-366
PCB LAYOUT GUIDELINES
1.
Use separate analog and power ground planes. Connect the
analog circuitry to analog ground. Connect the power
circuitry to power ground.
2.
To keep the inductance down, the traces from the highside MOSFET and the low-side MOSFET to the DH and
DL pins of the ADP1822, respectively, need to be relatively
short and wide.
3.
Place the source of Q1 and the drain of Q2 very close to
each other to minimize inductance. Use a wide copper
trace for this connection. However, too much copper area
on this switch node can increase capacitive-coupled
common-mode noise.
4.
Place ceramic input decoupling capacitors (C2, C3, and
C4) close to the Q1 drain and the Q2 source.
5.
Place C13 and C14 close to the VIN pin of the IC.
6.
The compensation components should also be placed as
close as possible to the FB pin.
7.
Connect the trace connecting R7 should be directly to the
drain of Q2 to ensure an ideal Kelvin connection,.
Rev. A | Page 11 of 16
UG-366
Evaluation Board User Guide
EVALUATION BOARD SCHEMATIC AND LAYOUT
M1
4
3
CON4
2
R14
DH 0Ω, 1%
1
M2
CON4
4
3
C1
180µF
20V
C2
10µF
16V
C3
1µF
25V
C4
1µF
25V
R15
0Ω, 1%
M3
1
VOUT
L1
2.2µH, 5.5mΩ
SW
DL
2
Q1
IRFR3711Z
2
3
CON4
4
IRFR3711Z
Q2
1
C5
680µF
4V
C6
680µF
4V
C7
22µF
10V
C8
22µF
10V
C9
1µF
10V
C10
1µF
10V
M4
1
2
3
LOW_S
CON4
4
Q3
MMBT2222
R5
1.2kΩ
1%
R6
10Ω
1%
C13
1µF
16V
D1
BZX84C5V6
C15
0.1µF
16V
J1
AGND
PWGD
1
1
R11
10kΩ
1%
R8
10kΩ
1%
U1
1
2
3
4
5
6
7
8
9
10
11
12
DH
SW
PGND
SYNC
R10
10kΩ
1%
J3
J2
R17
10kΩ
5%
BST
DH
SW
SYNC
FREQ
MAR
TRKN
TRKP
SHDN
PWGD
DGND
GND
VOUT
J1: OPEN = 300kHz
SHORT = 600kHz
J2: OPEN = ENABLE
SHORT = DISABLE
J3: OPEN = HIGH MARGIN
SHORT = LOW MARGIN
J4: OPEN = ACTIVE VOLTAGE MARGIN
SHORT = NO MARGIN
C20
1nF
16V
AGND
24
23
22
21
20
19
18
17
16
MSEL
15
COMP
14
FB
13
SS
NC
PVCC
DL
PGND
CSL
VCC
MUP
MDN
ADP1822
DGND AGND
C12
22nF
16V
R16
10Ω
5%
R7
3kΩ
1%
SW
C16
2.2pF
16V
DL
R13
246kΩ
1%
R3
82kΩ
1%
R12
133kΩ
1%
AGND
AGND
VOUT
C17
1nF
16V
R1
20kΩ
1%
C19
18pF
J4
DGND
AGND
1
R4
2.7kΩ
1%
C18
1.8nF
16V
R2
10kΩ
1%
TRKN
06388-001
DGND
R9
10kΩ
1%
C14
1µF
16V
D2
BAT54
Figure 13. Typical Application Schematic Diagram
06388-013
VIN
Figure 14. Top Layer
Rev. A | Page 12 of 16
UG-366
06388-014
Evaluation Board User Guide
06388-015
Figure 15. Bottom Layer
Figure 16. Silkscreen Top
Rev. A | Page 13 of 16
UG-366
Evaluation Board User Guide
ORDERING INFORMATION
BILL OF MATERIALS
Table 5. Bill of Materials for ADP1822 Typical Application Circuit (12 V to 1.8 V @ 10 A, fSW = 300 kHz)
Item
Description
Manufacturer
Part No.
Designator
Qty
1
Sanyo
20SP180M
C1
1
Murata
Murata
Murata
Sanyo
GRM31CR61E106KA12
GRM188R61E105KA12
GRM185R61C105KE44
4SEPC680M
C2
C3, C4
C9, C10
C5, C6
1
2
2
2
6
7
8
9
10
11
12
13
15
16
17
18
19
20
21
Capacitor, OS-CON, 180 μF, 20 V, 20 mΩ,
11 mm × 10 mm × 5 mm
Capacitor, Ceramic, 10 μF, 25 V, X5R,1206
Capacitor, Ceramic, 1 μF, 25 V, X5R, 0603
Capacitor, Ceramic, 1 μF, 16 V, X5R, 0603
Capacitor, OS-CON, 680 μF, 4 V, 7 mΩ,
13 mm × 8 mm × 3.5 mm
Capacitor, Ceramic, 22 μF, 10 V, X5R, 1210
Capacitor, Ceramic, 22 nF, 16 V, X7R, 0603
Capacitor, Ceramic, 1 μF, 16 V, X5R, 0603
Capacitor, Ceramic, 0.1 μF, 16 V, X7R, 0603
Capacitor, Ceramic, 2.2 pF, 16 V, NPO, 0603
Capacitor, Ceramic, 1 nF, 16 V, X7R, 0603
Capacitor, Ceramic, 1.8 nF, 16 V, X7R, 0603
Capacitor, Ceramic, 18 pF, NPO, 0603
Diode, Zener, 5.6 V, SOT-23
Diode, Schottky, 30 V, SOT-23
Inductor, 2.2 μH, 5.2 mΩ, 13 A (rms)
N MOSFET, 30 V, 61 A, 6.5 mΩ, D-PAK, 17 nC
Transistor, BJT-NPN, 40 V, SOT-23
Resistor, 20 kΩ, 1/10 W, 1%, 0603
Resistor, 10 kΩ, 1/10 W, 1%, 0603
Murata
Vishay or equivalent
Murata
Vishay or equivalent
Vishay or equivalent
Vishay or equivalent
Vishay or equivalent
Vishay or equivalent
FairChild
FairChild
Cooper Bussmann
IR
ON Semiconductor
Vishay or equivalent
Vishay or equivalent
GRM32NR61A226KE19
VJ0603Y233KXXA
GRM188R61C105KA93
VJ0603Y104MXQ
VJ0603Y2R2KXXA
VJ0603Y102KXXA
VJ0603Y182KXXA
VJ0603Y180KXXA
BZX84C5V6LT1
BAT54
HC7-2R2
IRFR3709ZPBF
MMBT2222
CRCW06032002F
CRCW06031002F
2
1
2
1
1
2
1
1
1
1
1
2
1
1
5
22
23
24
25
26
27
28
29
30
32
33
Resistor, 82 kΩ, 1/10 W, 1%, 0603
Resistor, 2.7 kΩ, 1/10 W, 1%, 0603
Resistor, 1.2 kΩ, 1/10 W, 1%, 0603
Resistor, 10 Ω, 1/10 W, 1%, 0603
Resistor, 3 kΩ, 1/10 W, 1%, 0603
Resistor, 133 kΩ, 1/10 W, 1%, 0603
Resistor, 246 kΩ, 1/10 W, 1%, 0603
Resistor, 0 Ω, 1/10 W, 1%, 0603
Resistor, 10 kΩ, 1/10 W, 5%, 0603
Input and Output Terminal
Test Point
Vishay or equivalent
Vishay or equivalent
Vishay or equivalent
Vishay or equivalent
Vishay or equivalent
Vishay or equivalent
Vishay or equivalent
Vishay or equivalent
Vishay or equivalent
Keystone Electronics
Any
CRCW06038202F
CRCW06032701F
CRCW06031201F
CRCW060310R0F
CRCW06033001F
CRCW06031334F
CRCW06032464F
CRCW06030R0F
CRCW06031002J
CAT.NO.8191
Any
34
35
Jumper
IC— 20 A Step Down DC-to-DC Controller
with Tracking and Margining
Any
Analog Devices
Any
ADP1822
C7, C8
C12
C13, C14
C15
C16
C17, C20
C18
C19
D1
D2
L1
Q1,Q2
Q3
R1
R2, R8, R9, R10,
R11
R3
R4
R5
R6
R7
R12
R13
R14, R15
R16, R17
M1, M2, M3, M4
PWGD, SYNC,
TRKN, VOUT, GND
J1, J2, J3, J4
U1
2
3
4
5
Rev. A | Page 14 of 16
1
1
1
1
1
1
1
2
2
4
5
4
1
Evaluation Board User Guide
UG-366
NOTES
Rev. A | Page 15 of 16
UG-366
Evaluation Board User Guide
NOTES
ESD Caution
ESD (electrostatic discharge) sensitive device. Charged devices and circuit boards can discharge without detection. Although this product features patented or proprietary protection
circuitry, damage may occur on devices subjected to high energy ESD. Therefore, proper ESD precautions should be taken to avoid performance degradation or loss of functionality.
Legal Terms and Conditions
By using the evaluation board discussed herein (together with any tools, components documentation or support materials, the “Evaluation Board”), you are agreeing to be bound by the terms and conditions
set forth below (“Agreement”) unless you have purchased the Evaluation Board, in which case the Analog Devices Standard Terms and Conditions of Sale shall govern. Do not use the Evaluation Board until you
have read and agreed to the Agreement. Your use of the Evaluation Board shall signify your acceptance of the Agreement. This Agreement is made by and between you (“Customer”) and Analog Devices, Inc.
(“ADI”), with its principal place of business at One Technology Way, Norwood, MA 02062, USA. Subject to the terms and conditions of the Agreement, ADI hereby grants to Customer a free, limited, personal,
temporary, non-exclusive, non-sublicensable, non-transferable license to use the Evaluation Board FOR EVALUATION PURPOSES ONLY. Customer understands and agrees that the Evaluation Board is provided
for the sole and exclusive purpose referenced above, and agrees not to use the Evaluation Board for any other purpose. Furthermore, the license granted is expressly made subject to the following additional
limitations: Customer shall not (i) rent, lease, display, sell, transfer, assign, sublicense, or distribute the Evaluation Board; and (ii) permit any Third Party to access the Evaluation Board. As used herein, the term
“Third Party” includes any entity other than ADI, Customer, their employees, affiliates and in-house consultants. The Evaluation Board is NOT sold to Customer; all rights not expressly granted herein, including
ownership of the Evaluation Board, are reserved by ADI. CONFIDENTIALITY. This Agreement and the Evaluation Board shall all be considered the confidential and proprietary information of ADI. Customer may
not disclose or transfer any portion of the Evaluation Board to any other party for any reason. Upon discontinuation of use of the Evaluation Board or termination of this Agreement, Customer agrees to
promptly return the Evaluation Board to ADI. ADDITIONAL RESTRICTIONS. Customer may not disassemble, decompile or reverse engineer chips on the Evaluation Board. Customer shall inform ADI of any
occurred damages or any modifications or alterations it makes to the Evaluation Board, including but not limited to soldering or any other activity that affects the material content of the Evaluation Board.
Modifications to the Evaluation Board must comply with applicable law, including but not limited to the RoHS Directive. TERMINATION. ADI may terminate this Agreement at any time upon giving written notice
to Customer. Customer agrees to return to ADI the Evaluation Board at that time. LIMITATION OF LIABILITY. THE EVALUATION BOARD PROVIDED HEREUNDER IS PROVIDED “AS IS” AND ADI MAKES NO
WARRANTIES OR REPRESENTATIONS OF ANY KIND WITH RESPECT TO IT. ADI SPECIFICALLY DISCLAIMS ANY REPRESENTATIONS, ENDORSEMENTS, GUARANTEES, OR WARRANTIES, EXPRESS OR IMPLIED, RELATED
TO THE EVALUATION BOARD INCLUDING, BUT NOT LIMITED TO, THE IMPLIED WARRANTY OF MERCHANTABILITY, TITLE, FITNESS FOR A PARTICULAR PURPOSE OR NONINFRINGEMENT OF INTELLECTUAL
PROPERTY RIGHTS. IN NO EVENT WILL ADI AND ITS LICENSORS BE LIABLE FOR ANY INCIDENTAL, SPECIAL, INDIRECT, OR CONSEQUENTIAL DAMAGES RESULTING FROM CUSTOMER’S POSSESSION OR USE OF
THE EVALUATION BOARD, INCLUDING BUT NOT LIMITED TO LOST PROFITS, DELAY COSTS, LABOR COSTS OR LOSS OF GOODWILL. ADI’S TOTAL LIABILITY FROM ANY AND ALL CAUSES SHALL BE LIMITED TO THE
AMOUNT OF ONE HUNDRED US DOLLARS ($100.00). EXPORT. Customer agrees that it will not directly or indirectly export the Evaluation Board to another country, and that it will comply with all applicable
United States federal laws and regulations relating to exports. GOVERNING LAW. This Agreement shall be governed by and construed in accordance with the substantive laws of the Commonwealth of
Massachusetts (excluding conflict of law rules). Any legal action regarding this Agreement will be heard in the state or federal courts having jurisdiction in Suffolk County, Massachusetts, and Customer hereby
submits to the personal jurisdiction and venue of such courts. The United Nations Convention on Contracts for the International Sale of Goods shall not apply to this Agreement and is expressly disclaimed.
©2006–2011 Analog Devices, Inc. All rights reserved. Trademarks and
registered trademarks are the property of their respective owners.
UG06388-0-12/11(A)
Rev. A | Page 16 of 16
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