AAT1141IGV-1.0-T1

PRODUCT DATASHEET AAT1141 SwitchRegTM General Description The AAT1141 SwitchReg is a 2MHz step-down converter with an input voltage range of 2.7V to 5.5V and output voltage as low as 0.6V. It is optimized to react quickly to a load variation. The AAT1141 is available in fixed voltage versions with internal feedback and a programmable version with external feedback resistors. It can deliver 600mA of load current while maintaining a low 35μA no load quiescent current. The 2MHz switching frequency minimizes the size of external components while keeping switching losses low. The AAT1141 is designed to maintain high efficiency throughout the operating range, which is critical for portable applications. The AAT1141 is available in a Pb-free SOT23-5 package and is rated over the -40°C to +85°C temperature range. Fast Transient 600mA Step-Down Converter Features • • • • • • • • • • • • • • VIN Range: 2.7V to 5.5V VOUT Fixed or Adjustable from 0.6V to VIN 35μA No Load Quiescent Current Up to 98% Efficiency 600mA Max Output Current 2MHz Switching Frequency 150μs Soft Start Fast Load Transient Over-Temperature Protection Current Limit Protection 100% Duty Cycle Low-Dropout Operation 0.6V Output From Enable to Output Regulation TA = 25°C 1 588 250 1.2 150 2.0 140 15 2.6 0.1 600 612 0.2 100 1.8 -3.5 0.6 35 +3.5 VIN 70 1.0 Fast Transient 600mA Step-Down Converter Typ Max 5.5 2.7 Units V V mV V % V μA μA mA Ω Ω μA %/V mV μA kΩ μs MHz °C °C V V μA Step-Down Converter VIN Input Voltage VUVLO VOUT VOUT IQ ISHDN ILIM RDS(ON)H RDS(ON)L ILXLEAK ΔVLinereg VOUT IOUT ROUT TS FOSC TSD THYS EN VEN(L) VEN(H) IEN UVLO Threshold Output Voltage Tolerance Output Voltage Range Quiescent Current Shutdown Current P-Channel Current Limit High Side Switch On Resistance Low Side Switch On Resistance LX Leakage Current Line Regulation Out Threshold Voltage Accuracy Out Leakage Current Out Impedance Start-Up Time Oscillator Frequency Over-Temperature Shutdown Threshold Over-Temperature Shutdown Hysteresis Enable Threshold Low Enable Threshold High Input Low Current 0.6 VIN = VOUT = 5.5V 1.4 -1.0 1.0 1. The AAT1141 is guaranteed to meet performance specifications over the -40°C to +85°C operating temperature range and is assured by design, characterization, and correlation with statistical process controls. 4 www.analogictech.com 1141.2008.10.1.6 PRODUCT DATASHEET AAT1141 AAT1141 SwitchRegTM Typical Characteristics Efficiency vs. Load (VOUT = 3.3V; L = 6.8µH) 100 90 Fast Transient 600mA Step-Down Converter DC Regulation (VOUT = 3.3V; L = 6.8µH) 3.0 2.0 1.0 0.0 -1.0 -2.0 -3.0 VIN = 3.6V VIN = 4.2V VIN = 5.0V Output Error (%) Efficiency (%) 80 70 60 50 0.1 VIN = 4.2V VIN = 5.0V VIN = 5.5V 0 100 200 300 400 500 600 1 10 100 1000 Output Current (mA) Output Current (mA) Efficiency vs. Load (VOUT = 2.5V; L = 6.8µH) 100 90 DC Regulation (VOUT = 2.5V; L = 6.8µH) 3.0 2.0 1.0 0.0 -1.0 -2.0 -3.0 VIN = 2.7V Output Error (%) VIN = 5.0V VIN = 4.2V VIN = 3.6V Efficiency (%) 80 70 60 50 0.1 VIN = 5.0V VIN = 3.0V VIN = 3.6V VIN = 4.2V 1 10 100 1000 0 100 200 300 400 500 600 Output Current (mA) Output Current (mA) Efficiency vs. Load (VOUT = 1.8V; L = 4.7µH) 100 90 3.0 DC Regulation (VOUT = 1.8V; L = 4.7μH) VIN = 2.7V Output Error (%) VIN = 3.6V VIN = 4.2V 2.0 1.0 0.0 -1.0 -2.0 -3.0 0 100 200 300 400 500 600 Efficiency (%) 80 70 60 50 0.1 VIN = 2.7V VIN = 3.6V VIN = 4.2V 1 10 100 1000 Output Current (mA) Output Current (mA) 1141.2008.10.1.6 www.analogictech.com 5 PRODUCT DATASHEET AAT1141 AAT1141 SwitchRegTM Typical Characteristics (VIN = 3.6V; VOUT = 1.8V; Load = 3Ω; CFF = 100pF) 0.5 0.4 Fast Transient 600mA Step-Down Converter Soft Start Line Regulation (VOUT = 1.8V) IOUT = 10mA IOUT = 600mA Output Voltage (V) EN (2V/div) VOUT (2V/div) 0V 0.3 0.2 0.1 0.0 -0.1 -0.2 -0.3 -0.4 -0.5 2.5 3.0 3.5 4.0 4.5 5.0 0V IIN (200mA/div) 0mA 5.5 6.0 Time (100μs/div) Input Voltage (V) Output Voltage Error vs. Temperature (VIN = 3.6V; VO = 1.8V; IOUT = 400mA) 2.0 Switching Frequency vs. Temperature (VIN = 3.6V; VOUT = 1.8V) 10.00 Frequency Variation (%) 8.00 6.00 4.00 2.00 0.00 -2.00 -4.00 -6.00 -8.00 -10.00 -40 -20 0 20 40 60 80 100 Output Error (%) 1.0 0.0 -1.0 -2.0 -40 -20 0 20 40 60 80 100 Temperature (°C) Temperature (°C) Frequency vs. Input Voltage 2.0 No Load Quiescent Current vs. Input Voltage (VOUT = 3.0V, L = 6.8µH) 60 Frequency Variation (%) Supply Current (µA) 1.0 0.0 -1.0 -2.0 -3.0 -4.0 VOUT = 1.8V 55 50 45 40 35 30 25 20 3.3 3.8 TA = 85°C TA = 25°C VOUT = 2.5V VOUT = 3.3V TA = -40°C 4.3 4.8 5.3 2.7 3.1 3.5 3.9 4.3 4.7 5.1 5.5 Input Voltage (V) Input Voltage (V) 6 www.analogictech.com 1141.2008.10.1.6 PRODUCT DATASHEET AAT1141 AAT1141 SwitchRegTM Typical Characteristics No Load Quiescent Current vs. Input Voltage (VOUT = 1.8V, L = 4.7µH) 0.060 0.060 0.055 0.050 0.045 0.040 0.035 0.030 0.025 0.020 2.7 3.1 3.5 Fast Transient 600mA Step-Down Converter No Load Quiescent Current vs. Input Voltage (VOUT = 1.2V, L = 2.2µH) 0.055 0.050 0.045 0.040 0.035 0.030 0.025 0.020 2.7 3.1 3.5 3.9 Supply Current (mA) Supply Current (mA) TA = 85°C TA = 25°C TA = 25°C TA = 85°C TA = -40°C 3.9 4.3 4.7 5.1 5.5 TA = -40°C 4.3 4.7 5.1 5.5 Input Voltage (V) Input Voltage (V) P-Channel RDS(ON) vs. Input Voltage 700 600 600 N-Channel RDS(ON) vs. Input Voltage 85°C 25°C -40°C RDS(ON)H (mΩ) RDS(ON)L (mΩ) 5.5 500 400 300 200 100 2.7 85°C 25°C -40°C 550 500 450 400 350 300 250 200 150 100 2.7 3.1 3.5 3.9 4.3 4.7 3.1 3.5 3.9 4.3 4.7 5.1 5.1 5.5 Input Voltage (V) Input Voltage (V) Step-Down Converter Load Transient Response (1mA to 300mA; VIN = 3.6V; VOUT = 1.8V; COUT = 4.7µF; CFF = 100pF) VOUT (100mV/div) Step-Down Converter Load Transient Response (300mA to 400mA; VIN = 3.6V; VOUT = 1.8V; COUT = 4.7µF; CFF = 100pF) VOUT (50mV/div) 1.8V 1.8V 300mA IOUT (100mA/div) 1mA IOUT (100mA/div) 400mA 300mA Time (40µs/div) Time (40µs/div) 1141.2008.10.1.6 www.analogictech.com 7 PRODUCT DATASHEET AAT1141 AAT1141 SwitchRegTM Typical Characteristics Step-Down Converter Load Transient Response (1mA to 300mA; VIN = 3.6V; VOUT = 1.0V; COUT = 10µF; CFF = 0pF) VOUT (100mV/div) VOUT (50mV/div) Fast Transient 600mA Step-Down Converter Step-Down Converter Load Transient Response (300mA to 400mA; VIN = 3.6V; VOUT = 1.0V; COUT = 10µF; CFF = 0pF) 1.0V 1.0V 300mA 400mA IOUT (100mA/div) 1mA IOUT (100mA/div) 300mA Time (40µs/div) Time (40µs/div) Line Response (VOUT = 1.8V @ 400mA) 1.82 1.81 6.0 5.5 Step-Down Converter Output Ripple (VOUT = 1.8V; VIN = 3.6V; IOUT = 1mA; L = 4.7µH; CFF = 100pF; COUT = 4.7µF) Output Ripple (20mV/div) Input Voltage (bottom) (V) LX (2V/div) 1.8V Output Voltage (top) (V) 1.80 1.79 1.78 1.77 1.76 5.0 4.5 4.0 3.5 3.0 1.8V Inductor Current (100mA/div) 0mA Time (25μs/div) Time (10µs/div) Step-Down Converter Output Ripple (VOUT = 1.8V; VIN = 3.6V; IOUT = 600mA; L = 4.7µH; CFF = 100pF; COUT = 4.7µF) Output Ripple (20mV/div) LX (2V/div) 1.8V 0V Inductor Current (100mA/div) 600mA Time (0.5µs/div) 8 www.analogictech.com 1141.2008.10.1.6 PRODUCT DATASHEET AAT1141 SwitchRegTM Functional Block Diagram OUT IN Fast Transient 600mA Step-Down Converter See note Err Amp . DH Voltage Reference Logic LX EN INPUT DL GND Note: For adjustable version, the internal feedback divider is omitted and the OUT pin is tied directly to the internal error amplifier. Functional Description The AAT1141 is a high performance 600mA 2MHz monolithic step-down converter. It has been designed with the goal of minimizing external component size and optimizing efficiency over the complete load range. Apart from the small bypass input capacitor, only a small L-C filter is required at the output. Typically, a 4.7μH inductor and a 4.7μF ceramic capacitor are recommended (see table of values). The fixed output version requires only three external power components (CIN, COUT, and L). The adjustable version can be programmed with external feedback to any voltage, ranging from 0.6V to the input voltage. An addi- tional feed-forward capacitor can also be added to the external feedback to provide improved transient response (see Figure 1). At dropout, the converter duty cycle increases to 100% and the output voltage tracks the input voltage minus the RDS(ON) drop of the P-channel high-side MOSFET. The input voltage range is 2.7V to 5.5V. The converter efficiency has been optimized for all load conditions, ranging from no load to 600mA. The internal error amplifier and compensation provides excellent transient response, load, and line regulation. Soft start eliminates any output voltage overshoot when the enable or the input voltage is applied. 1141.2008.10.1.6 www.analogictech.com 9 PRODUCT DATASHEET AAT1141 SwitchRegTM Fast Transient 600mA Step-Down Converter U1 AAT1141 V IN C1 4.7μF 1 SW IN GND EN LX 5 L1 4.7μH VOUT C3 100pF R1 118k C2 4.7μF 2 Enable 1 2 3 3 OUT 4 R2 59k Figure 1: Enhanced Transient Response Schematic. Control Loop The AAT1141 is a peak current mode step-down converter. The current through the P-channel MOSFET (high side) is sensed for current loop control, as well as short circuit and overload protection. A fixed slope compensation signal is added to the sensed current to maintain stability for duty cycles greater than 50%. The peak current mode loop appears as a voltage-programmed current source in parallel with the output capacitor. The output of the voltage error amplifier programs the current mode loop for the necessary peak switch current to force a constant output voltage for all load and line conditions. Internal loop compensation terminates the transconductance voltage error amplifier output. For fixed voltage versions, the error amplifier reference voltage is internally set to program the converter output voltage. For the adjustable output, the error amplifier reference is fixed at 0.6V. Current Limit and Over-Temperature Protection For overload conditions, the peak input current is limited. To minimize power dissipation and stresses under current limit and short-circuit conditions, switching is terminated after entering current limit for a series of pulses. Switching is terminated for seven consecutive clock cycles after a current limit has been sensed for a series of four consecutive clock cycles. Thermal protection completely disables switching when internal dissipation becomes excessive. The junction over-temperature threshold is 140°C with 15°C of hysteresis. Once an over-temperature or over-current fault condition is removed, the output voltage automatically recovers. Under-Voltage Lockout Internal bias of all circuits is controlled via the IN input. Under-voltage lockout (UVLO) guarantees sufficient VIN bias and proper operation of all internal circuitry prior to activation. Soft Start / Enable Soft start limits the current surge seen at the input and eliminates output voltage overshoot. When pulled low, the enable input forces the AAT1141 into a low-power, non-switching state. The total input current during shutdown is less than 1μA. 10 www.analogictech.com 1141.2008.10.1.6 PRODUCT DATASHEET AAT1141 SwitchRegTM Applications Information Inductor Selection The step-down converter uses peak current mode control with slope compensation to maintain stability for duty cycles greater than 50%. The output inductor value must be selected so the inductor current down slope meets the internal slope compensation requirements. The internal slope compensation for the adjustable and low-voltage fixed versions of the AAT1141 is 0.24A/μsec. This equates to a slope compensation that is 75% of the inductor current down slope for a 1.5V output and 4.7μH inductor. Fast Transient 600mA Step-Down Converter The 4.7μH CDRH2D14 series inductor selected from Sumida has a 135mΩ typical DCR and a 1A DC current rating. At full load, the inductor DC loss is 48mW which gives a 4.5% loss in efficiency for a 600mA, 1.8V output. Input Capacitor Select a 4.7μF to 10μF X7R or X5R ceramic capacitor for the input. To estimate the required input capacitor size, determine the acceptable input ripple level (VPP) and solve for C. The calculated value varies with input voltage and is a maximum when VIN is double the output voltage. 0.75 · VO 0.75 · 1.5V A m= = = 0.24 L 4.7μH μs This is the internal slope compensation for the adjustable (0.6V) version or low-voltage fixed versions. When externally programming the 0.6V version to 2.5V, the calculated inductance is 7.5μH. CIN = V⎞ VO ⎛ · 1- O VIN ⎝ VIN ⎠ ⎛ VPP ⎞ - ESR · FS ⎝ IO ⎠ VO ⎛ V⎞ 1 · 1 - O = for VIN = 2 · VO VIN ⎝ VIN ⎠ 4 CIN(MIN) = 1 ⎛ VPP ⎞ - ESR · 4 · FS ⎝ IO ⎠ 0.75 · VO μs 0.75 · VO ≈ 3 A · VO L= = m A 0.24 μs =3 μs · 2.5V = 7.5μH A In this case, a standard 6.8μH value is selected. For high-voltage fixed versions (≥2.5V), m = 0.48A/ μsec. Table 1 displays inductor values for the AAT1141 fixed and adjustable options. Manufacturer's specifications list both the inductor DC current rating, which is a thermal limitation, and the peak current rating, which is determined by the saturation characteristics. The inductor should not show any appreciable saturation under normal load conditions. Some inductors may meet the peak and average current ratings yet result in excessive losses due to a high DCR. Always consider the losses associated with the DCR and its effect on the total converter efficiency when selecting an inductor. Output Voltage (V) 1, 1.2 1.5, 1.8 2.5, 3.3 Always examine the ceramic capacitor DC voltage coefficient characteristics when selecting the proper value. For example, the capacitance of a 10μF, 6.3V, X5R ceramic capacitor with 5.0V DC applied is actually about 6μF. The maximum input capacitor RMS current is: IRMS = IO · VO ⎛ V⎞ · 1- O VIN ⎝ VIN ⎠ The input capacitor RMS ripple current varies with the input and output voltage and will always be less than or equal to half of the total DC load current. VO ⎛ V⎞ · 1- O = VIN ⎝ VIN ⎠ for VIN = 2 · VO D · (1 - D) = IO 2 0.52 = 1 2 Inductor (μH) 2.2 4.7 6.8 Output Capacitor (μF) 10 4.7 4.7 IRMS(MAX) = VO IN Table 1: Inductor and Output Capacitor Values. The term V ⎝ V ⎠ appears in both the input voltage ripple and input capacitor RMS current equations and is a maximum when VO is twice VIN. This is why the input voltage ripple and the input capacitor RMS current ripple are a maximum at 50% duty cycle. IN ⎛ V⎞ · 1- O 1141.2008.10.1.6 www.analogictech.com 11 PRODUCT DATASHEET AAT1141 SwitchRegTM The input capacitor provides a low impedance loop for the edges of pulsed current drawn by the AAT1141. Low ESR/ESL X7R and X5R ceramic capacitors are ideal for this function. To minimize stray inductance, the capacitor should be placed as closely as possible to the IC. This keeps the high frequency content of the input current localized, minimizing EMI and input voltage ripple. The proper placement of the input capacitor (C2) can be seen in the evaluation board layout in Figure 2. Fast Transient 600mA Step-Down Converter A laboratory test set-up typically consists of two long wires running from the bench power supply to the evaluation board input voltage pins. The inductance of these wires, along with the low-ESR ceramic input capacitor, can create a high Q network that may affect converter performance. This problem often becomes apparent in the form of excessive ringing in the output voltage during load transients. Errors in the loop phase and gain measurements can also result. Figure 2: AAT1141 Sample Layout Top Side. Figure 3: Exploded View of Sample Layout. Figure 4: AAT1141 Sample Layout Bottom Side. 12 www.analogictech.com 1141.2008.10.1.6 PRODUCT DATASHEET AAT1141 SwitchRegTM Since the inductance of a short PCB trace feeding the input voltage is significantly lower than the power leads from the bench power supply, most applications do not exhibit this problem. In applications where the input power source lead inductance cannot be reduced to a level that does not affect the converter performance, a high ESR tantalum or aluminum electrolytic should be placed in parallel with the low ESR, ESL bypass ceramic. This dampens the high Q network and stabilizes the system. Fast Transient 600mA Step-Down Converter Dissipation due to the RMS current in the ceramic output capacitor ESR is typically minimal, resulting in less than a few degrees rise in hot-spot temperature. Adjustable Output Resistor Selection For applications requiring an adjustable output voltage, the 0.6V version can be externally programmed. Resistors R1 and R2 of Figure 5 program the output to regulate at a voltage higher than 0.6V. To limit the bias current required for the external feedback resistor string while maintaining good noise immunity, the minimum suggested value for R2 is 59kΩ. Although a larger value will further reduce quiescent current, it will also increase the impedance of the feedback node, making it more sensitive to external noise and interference. Table 2 summarizes the resistor values for various output voltages with R2 set to either 59kΩ for good noise immunity or 316kΩ for reduced no load input current. Output Capacitor The output capacitor limits the output ripple and provides holdup during large load transitions. A 4.7μF to 10μF X5R or X7R ceramic capacitor typically provides sufficient bulk capacitance to stabilize the output during large load transitions and has the ESR and ESL characteristics necessary for low output ripple. The output voltage droop due to a load transient is dominated by the capacitance of the ceramic output capacitor. During a step increase in load current, the ceramic output capacitor alone supplies the load current until the loop responds. Within two or three switching cycles, the loop responds and the inductor current increases to match the load current demand. The relationship of the output voltage droop during the three switching cycles to the output capacitance can be estimated by: ⎛ VOUT ⎞ ⎛ 1.5V ⎞ R1 = V -1 · R2 = 0.6V - 1 · 59kΩ = 88.5kΩ ⎝ REF ⎠ ⎝ ⎠ The adjustable version of the AAT1141, combined with an external feedforward capacitor (C3 in Figure 1), delivers enhanced transient response for extreme pulsed load applications. The addition of the feedforward capacitor typically requires a larger output capacitor C1 for stability. High Noise Immunity R2 = 59kΩ R1 (kΩ) 19.6 29.4 39.2 49.9 59.0 68.1 78.7 88.7 88.7 137 187 237 267 3 · ΔILOAD COUT = VDROOP · FS Once the average inductor current increases to the DC load level, the output voltage recovers. The above equation establishes a limit on the minimum value for the output capacitor with respect to load transients. The internal voltage loop compensation also limits the minimum output capacitor value to 4.7μF. This is due to its effect on the loop crossover frequency (bandwidth), phase margin, and gain margin. Increased output capacitance will reduce the crossover frequency with greater phase margin. The maximum output capacitor RMS ripple current is given by: VOUT (V) 0.8 0.9 1.0 1.1 1.2 1.3 1.4 1.5 1.8 2.0 2.5 3.0 3.3 Low Input Current (Without Load) R2 = 316kΩ R1 (kΩ) 105 158 210 267 316 365 422 475 634 732 1000 1270 1430 IRMS(MAX) = VOUT · (VIN(MAX) - VOUT) L · F · VIN(MAX) 2· 3 · 1 Table 2: Adjustable Resistor Values For Use With 0.6V Step-Down Converter. 1141.2008.10.1.6 www.analogictech.com 13 PRODUCT DATASHEET AAT1141 SwitchRegTM Thermal Calculations There are three types of losses associated with the AAT1141 step-down converter: switching losses, conduction losses, and quiescent current losses. Conduction losses are associated with the RDS(ON) characteristics of the power output switching devices. Switching losses are dominated by the gate charge of the power output switching devices. At full load, assuming continuous conduction mode (CCM), a simplified form of the LDO losses is given by: Fast Transient 600mA Step-Down Converter Since RDS(ON), quiescent current, and switching losses all vary with input voltage, the total losses should be investigated over the complete input voltage range. Given the total losses, the maximum junction temperature can be derived from the θJA for the SOT23-5 package which is 150°C/W. TJ(MAX) = PTOTAL · ΘJA + TAMB Output Dropout PTOTAL = IO2 · (RDSON(HS) · VO + RDSON(LS) · [VIN - VO]) VIN At dropout, the duty cycle of AAT1141 switching is 100%. The minimum dropout voltage is determined by RDS(ON)H and the inductor copper loss resistor. AAT1141 has 0.35Ω RDS(ON)H. The inductor copper loss resistor varies with different inductor values and manufacturer. The safe dropout voltage is 0.5V for a 600mA load. For example, when load current is 600mA, the voltage dropped across RDS(ON)H is 0.21V; if the inductor copper loss resistor is 135mΩ, the voltage drop across the inductor is 0.08V. So the total voltage drop is 0.29V. Considering manufacturer’s tolerances, the inductor copper loss resistor and RDS(ON)H will vary from part to part, a 0.4V dropout window is safe. + (tsw · F · IO + IQ) · VIN IQ is the step-down converter quiescent current. The term tsw is used to estimate the full load step-down converter switching losses. For the condition where the step-down converter is in dropout at 100% duty cycle, the total device dissipation reduces to: PTOTAL = IO2 · RDSON(HS) + IQ · VIN SW U1 AAT1141 V IN C1 4.7μF 1 IN GND EN LX 5 L1 4.7μH VOUT = 1.8V C3 100pF R1 634k R2 316k C2 4.7μF 2 Enable 1 2 3 3 OUT 4 Figure 5: AAT1141 Adjustable Evaluation Board Schematic. 14 www.analogictech.com 1141.2008.10.1.6 PRODUCT DATASHEET AAT1141 SwitchRegTM Efficiency Besides the AAT1141 device losses including switching losses, conduction losses, and quiescent current losses, the inductor copper loss also affects the efficiency of the buck converter. To the buck converter, the average current of the inductor is equal to output current IO. So the loss in the inductor is: Fast Transient 600mA Step-Down Converter Layout The suggested 2-layer PCB layout for the AAT1141 is shown in Figures 2, 3 and 4. The following guide lines should be used to help ensure a proper layout. 1. The power traces (GND, LX, VIN) should be kept short, direct, and wide to allow large current flow. Place sufficient multiple-layer pads when needed to change the trace layer. The input capacitor (C1) should connect as closely as possible to IN and GND. The output capacitor C2 and L1 should be connected as closely as possible. The connection of L1 to the LX pin should be as short as possible and there should not be any signal lines under the inductor. The feedback trace or OUT pin should be separate from any power trace and connect as closely as possible to the load point. Sensing along a high-current load trace will degrade DC load regulation. If external feedback resistors are used, they should be placed as closely as possible to the OUT pin to minimize the length of the high impedance feedback trace. The resistance of the trace from the load return to GND should be kept to a minimum. This will help to minimize any error in DC regulation due to differences in the potential of the internal signal ground and the power ground. PLOSS_L = IO2 · RL Table 4 shows some recommended inductors. A larger size inductor usually has lower DCR. For example, if selecting CDRH2D14 4.7μH for 1.8V output, the PLoss_L is 48.6mW when the output current is 600mA, so the inductor loses 4.5% power; if selecting CDRH3D23 4.7μH, the PLoss_L should be 19.8mW, and the inductor power loss ratio is only 1.8%. The inductor size and the buck converter efficiency is always a trade-off in the real application. 2. 3. 4. 5. 1141.2008.10.1.6 www.analogictech.com 15 PRODUCT DATASHEET AAT1141 AAT1141 SwitchRegTM Fast Transient 600mA Step-Down Converter Step-Down Converter Design Example Specifications VO = VIN = FS = TAMB = 1.8V @ 600mA (adjustable using 0.6V version), Pulsed Load ΔILOAD = 300mA 2.7V to 4.2V (3.6V nominal) 2MHz 85°C 1.8V Output Inductor µs µs L1 = 3 A · VO2 = 3 A · 1.8V = 5.4µH (use 4.7μH; see Table 1) For Sumida inductor CDRH3D16, 4.7μH, DCR = 105mΩ. ΔIL1 = VO V 1.8V · 1- O = L1 · F VIN 4.7µH · 2MHz ΔIL1 = 0.6A + 0.055A = 0.655A 2 · 1- 1.8V = 109.2mA 4.2V IPKL1 = IO + PL1 = IO2 · DCR = 0.6A2 · 105mΩ = 38mW 1.8V Output Capacitor VDROOP = 0.1V COUT = IRMS = 3 · ΔILOAD 3 · 0.3A = = 4.48µF; use 10µF 0.1V · 2MHz VDROOP · FS (VO) · (VIN(MAX) - VO) 1 1.8V · (4.2V - 1.8V) · = 31.5mArms = L1 · F · VIN(MAX) 2 · 3 4.7µH · 2MHz · 4.2V 2· 3 1 · Pesr = esr · IRMS2 = 5mΩ · (31.5mA)2 = 5µW Input Capacitor Input Ripple VPP = 25mV CIN = 1 VPP - ESR · 4 · FS IO IO = 0.3Arms 2 = 1 25mV - 5mW · 4 · 2MHz 0.6A = 3.4µF; use 4.7µF IRMS = P = esr · IRMS2 = 5mΩ · (0.3A)2 = 0.45mW 16 www.analogictech.com 1141.2008.10.1.6 PRODUCT DATASHEET AAT1141 AAT1141 SwitchRegTM AAT1141 Losses PTOTAL = IO2 · (RDSON(HS) · VO + RDSON(LS) · [VIN -VO]) VIN Fast Transient 600mA Step-Down Converter + (tsw · F · IO + IQ) · VIN = 0.62 · (0.35Ω · 1.8V + 0.3Ω · [4.2V - 1.8V]) 4.2V + (5ns · 2MHz · 0.6A + 70μA) · 4.2V = 141mW TJ(MAX) = TAMB + ΘJA · PLOSS = 85°C + (150°C/W) · 141mW = 106.2°C 1141.2008.10.1.6 www.analogictech.com 17 PRODUCT DATASHEET AAT1141 AAT1141 SwitchRegTM Adjustable Version (0.6V device) VOUT (V) 0.8 0.9 1.0 1.1 1.2 1.3 1.4 1.5 1.8 1.85 2.0 2.5 3.3 Fast Transient 600mA Step-Down Converter R2 = 59kΩ R1 (kΩ) 19.6 29.4 39.2 49.9 59.0 68.1 78.7 88.7 118 124 137 187 267 R2 = 316kΩ1 R1 (kΩ) 105 158 210 267 316 365 422 475 634 732 1000 1270 1430 L1 (μH) 2.2 2.2 2.2 2.2 2.2 2.2 4.7 4.7 4.7 4.7 6.8 6.8 6.8 Fixed Version VOUT (V) 0.6-3.3V R2 Not Used R1 (kΩ) 0 L1 (μH) 4.7 Table 3: Evaluation Board Component Values. Max DC Current (A) 1.20 0.90 0.73 1.5 1.0 0.85 0.40 0.45 0.80 0.98 0.82 1.30 Manufacturer Sumida Sumida Sumida Sumida Murata Murata Coilcraft Coiltronics Coiltronics Coiltronics Part Number CDRH3D16-2R2 CDRH3D16-4R7 CDRH3D16-6R8 CDRH2D14 LQH2MCN4R7M02 LQH32CN4R7M23 LPO3310-472 SD3118-4R7 SD3118-6R8 SDRC10-4R7 Inductance (μH) 2.2 4.7 6.8 2.2 4.7 6.8 4.7 4.7 4.7 4.7 6.8 4.7 DCR (Ω) 0.072 0.105 0.170 75 135 170 0.80 0.20 0.27 0.122 0.175 0.122 Size (mm) LxWxH 3.8x3.8x1.8 3.8x3.8x1.8 3.8x3.8x1.8 3.2x3.2x1.55 2.0x1.6x0.95 2.5x3.2x2.0 3.2x3.2x1.0 3.1x3.1x1.85 3.1x3.1x1.85 5.7x4.4x1.0 Type Shielded Shielded Shielded Shielded Non-Shielded Non-Shielded 1mm Shielded Shielded 1mm Shielded Table 4: Typical Surface Mount Inductors. Manufacturer Murata Murata Murata Part Number GRM219R61A475KE19 GRM21BR60J106KE19 GRM21BR60J226ME39 Value 4.7μF 10μF 22μF Voltage 10V 6.3V 6.3V Temp. Co. X5R X5R X5R Case 0805 0805 0805 Table 5: Surface Mount Capacitors. 1. For reduced quiescent current, R2 = 316kΩ. 18 www.analogictech.com 1141.2008.10.1.6 PRODUCT DATASHEET AAT1141 AAT1141 SwitchRegTM Ordering Information Output Voltage1 Adj 0.6 to VIN Adj 0.6 to VIN 1.0 1.2 1.5 1.8 3.0 3.3 Fast Transient 600mA Step-Down Converter Package TSOT23-5 SOT23-5 SOT23-5 SOT23-5 SOT23-5 SOT23-5 SOT23-5 SOT23-5 Marking2 YJXYY 1AXYY 5AXYY 4VXYY 5BXYY ZEXYY 5CXYY 5DXYY Part Number (Tape and Reel)3 AAT1141ICB-0.6-T1 AAT1141IGV-0.6-T1 AAT1141IGV-1.0-T1 AAT1141IGV-1.2-T1 AAT1141IGV-1.5-T1 AAT1141IGV-1.8-T1 AAT1141IGV-3.0-T1 AAT1141IGV-3.3-T1 All AnalogicTech products are offered in Pb-free packaging. The term “Pb-free” means semiconductor products that are in compliance with current RoHS standards, including the requirement that lead not exceed 0.1% by weight in homogeneous materials. For more information, please visit our website at http://www.analogictech.com/about/quality.aspx. Package Information SOT23-5 2.85 ± 0.15 1.90 BSC 0.95 BSC 1.575 ± 0.125 1.10 ± 0.20 1.20 ± 0.25 0.60 REF 2.80 ± 0.20 0.15 ± 0.07 4° ± 4° GAUGE PLANE 0.10 BSC 10° ± 5° 0.40 ± 0.10 0.075 ± 0.075 0.60 REF 0.45 ± 0.15 All dimensions in millimeters. 1. Contact Sales for other voltage options. 2. XYY = assembly and date code. 3. Sample stock is generally held on part numbers listed in BOLD. 1141.2008.10.1.6 www.analogictech.com 19 PRODUCT DATASHEET AAT1141 AAT1141 SwitchRegTM 1.900 BSC Fast Transient 600mA Step-Down Converter TSOT23-5 Detail "A" 2.800 BSC 1.600 BSC 0.450 ± 0.150 0.950 BSC End View Top View 2.900 BSC 0.127 BSC 0° +10° -0° 0.450 ± 0.150 0.950 ± 0.150 0.050 ± 0.050 Side View All dimensions in millimeters. Detail "A" Advanced Analogic Technologies, Inc. 3230 Scott Boulevard, Santa Clara, CA 95054 Phone (408) 737-4600 Fax (408) 737-4611 © Advanced Analogic Technologies, Inc. AnalogicTech cannot assume responsibility for use of any circuitry other than circuitry entirely embodied in an AnalogicTech product. No circuit patent licenses, copyrights, mask work rights, or other intellectual property rights are implied. AnalogicTech reserves the right to make changes to their products or specifications or to discontinue any product or service without notice. Except as provided in AnalogicTech’s terms and conditions of sale, AnalogicTech assumes no liability whatsoever, and AnalogicTech disclaims any express or implied warranty relating to the sale and/or use of AnalogicTech products including liability or warranties relating to fitness for a particular purpose, merchantability, or infringement of any patent, copyright or other intellectual property right. In order to minimize risks associated with the customer’s applications, adequate design and operating safeguards must be provided by the customer to minimize inherent or procedural hazards. Testing and other quality control techniques are utilized to the extent AnalogicTech deems necessary to support this warranty. Specific testing of all parameters of each device is not necessarily performed. AnalogicTech and the AnalogicTech logo are trademarks of Advanced Analogic Technologies Incorporated. All other brand and product names appearing in this document are registered trademarks or trademarks of their respective holders. 20 www.analogictech.com 1141.2008.10.1.6