AAT2505IWP-AQ-T1

Dual Channel, Step-Down Converter/Linear Regulator General Description The AAT2505 is a member of AnalogicTech's Total Power Management IC™ (TPMIC™) product family. It is a low dropout (LDO) linear regulator and a step-down converter with an input voltage range of 2.7V to 5.5V, making it ideal for applications with single cell lithium-ion / polymer batteries. The LDO has an independent input pin and is capable of delivering up to 300mA of current. The linear regulator has been designed for high-speed turn-on and turn-off performance, fast transient response, and good power supply rejection ratio (PSRR). Other features include low quiescent current, low dropout voltage, and a Power-OK (POK) open drain output signaling when VOUT is in regulation. The 600mA step-down converter is designed to operate with 1.4MHz of switching frequency, minimizing external component size and cost while maintaining a low 27µA no load quiescent current. Peak current mode control with internal compensation provides a stable converter with a low equivalent series resistance (ESR) ceramic output capacitor for extremely low output ripple. For maximum battery life with high voltage outputs, the step-down converter duty cycle increases to 100%. The output voltage is either fixed or adjustable with an integrated P- and N-channel MOSFET power stage and 1.4MHz switching frequency. The AAT2505 is available in a Pb-free, 12-pin TDFN33 package and is rated over a temperature range of -40°C to +85°C. AAT2505 Features • • SystemPower™ • • • • VIN Range: 2.7V to 5.5V 300mA LDO — 400mV Dropout Voltage at 300mA — High Accuracy: ±1.5% — Fast Line / Load Transient Response — Power OK Output 600mA Step-Down Converter — Up To 98% Efficiency — 27µA No Load Quiescent Current — Shutdown Current 0.6V Output From Enable to Output Regulation TA = 25°C 1.0 0.1 591 250 150 1.0 1.4 140 15 0.6 1.4 -1.0 1.0 2.0 600 609 0.2 100 1.8 -3.0 0.6 27 3.0 VIN 70 1.0 AAT2505 Typ Max 5.5 2.7 Units V V mV V % V µA µA mA Ω Ω µA %/V mV µA kΩ µs MHz °C °C V V µA Buck Converter VIN Input Voltage VUVLO VOUT VOUT IQBUCK ISHDN ILIM RDS(ON)H RDS(ON)L ILXLK ΔVLinereg VFB IFB RFB TS FOSC TSD THYS UVLO Threshold Output Voltage Tolerance Output Voltage Range Step-Down Converter Quiescent Current Shutdown Current P-Channel Current Limit High Side Switch On Resistance Low Side Switch On Resistance LX Leakage Current Line Regulation FB Threshold Voltage Accuracy FB Leakage Current FB Impedance Start-Up Time Oscillator Frequency Over-Temperature Shutdown Threshold Over-Temperature Shutdown Hysteresis Logic Signals VEN(L) Enable Threshold Low VEN(H) Enable Threshold High IEN(H) Leakage Current 1. The AAT2505 is guaranteed to meet performance specifications over the -40°C to +85°C operating temperature range and is assured by design, characterization, and correlation with statistical process controls. 2505.2006.06.1.1 5 Dual Channel, Step-Down Converter/Linear Regulator Typical Characteristics Unless otherwise noted, VIN = 5V, TA = 25°C. AAT2505 LDO Dropout Voltage vs. Temperature (EN = GND; ENLDO = VIN) 540 3.20 LDO Dropout Characteristics (EN = GND; ENLDO = VIN) Dropout Voltage (mV) 480 420 360 300 240 180 120 60 0 IL = 300mA Output Voltage (V) 3.00 2.80 2.60 2.40 2.20 2.00 2.70 IOUT = 0mA IL = 150mA IL = 100mA IOUT = 300mA IOUT = 150mA IOUT = 100mA IOUT = 50mA IL = 50mA -40 -30 -20 -10 0 10 20 30 40 50 60 70 80 90 100 110 120 IOUT = 10mA 2.80 2.90 3.00 3.10 3.20 3.30 Temperature (°C) Input Voltage (V) LDO Dropout Voltage vs. Output Current (EN = GND; ENLDO = VIN) 500 90.00 450 80.00 70.00 60.00 50.00 40.00 30.00 20.00 10.00 0.00 0 50 100 150 200 250 300 2 LDO Ground Current vs. Input Voltage (EN = GND; ENLDO = VIN) Dropout Voltage (mV) 400 350 300 250 200 150 100 50 0 Ground Current (μA) 85°C 25°C -40°C IOUT=300mA IOUT=0mA IOUT=150mA IOUT=50mA IOUT=10mA 2.5 3 3.5 4 4.5 5 Output Current (mA) Input Voltage (V) LDO Output Voltage vs. Temperature (EN = GND; ENLDO = VIN) Output Voltage Variation (%) 0.05 0.00 -0.05 -0.10 -0.15 -0.20 -0.25 -0.30 -0.35 -0.40 -0.45 -40 -30 -20 -10 0 10 20 30 40 50 60 70 80 90 100 LDO Initial Power-Up Response Time (EN = GND; ENLDO = VIN) VENLDO (5V/div) VOUT (1V/div) Time (400µs/div) Temperature (°C) 6 2505.2006.06.1.1 Dual Channel, Step-Down Converter/Linear Regulator Typical Characteristics Unless otherwise noted, VIN = 5V, TA = 25°C. AAT2505 LDO Turn-Off Response Time (EN = GND; ENLDO = VIN) LDO Turn-On Time From Enable (VIN present) (EN = GND; ENLDO = VIN) VENLDO = 5V/div VENLDO (5V/div) VOUT (1V/div) Time (50µs/div) VOUT = 1V/div Time (5µs/div) VIN = 4V LDO Line Transient Response (EN = GND; ENLDO = VIN) 6 5 3.04 3.03 3.02 3.01 3.00 2.90 2.85 2.80 2.75 2.70 2.65 LDO Load Transient Response (EN = GND; ENLDO = VIN) 500 Input Voltage (V) VIN Output Voltage (V) VOUT 400 300 200 100 0 Output Current (mA) Output Voltage (V) 4 3 2 VOUT 1 0 2.99 2.98 IOUT 2.60 -100 Time (100µs/div) Time (100µs/div) LDO Load Transient Response 300mA (EN = GND; ENLDO = VIN) 3.00 2.90 800 700 Output Current (mA) Output Voltage (V) 2.80 2.70 2.60 2.50 2.40 2.30 2.20 2.10 VOUT 600 500 400 300 200 IOUT 100 0 -100 Time (10µs/div) 2505.2006.06.1.1 7 Dual Channel, Step-Down Converter/Linear Regulator Typical Characteristics Unless otherwise noted, VIN = 5V, TA = 25°C. AAT2505 LDO Over-Current Protection (EN = GND; ENLDO = VIN) 1200 1.250 1.225 1.200 1.175 1.150 1.125 1.100 1.075 1.050 2.5 3.0 LDO ENLDO vs. VIN Output Current (mA) 1000 800 600 400 200 0 -200 VIH VIL Time (50ms/div) 3.5 4.0 4.5 5.0 5.5 Input Voltage (V) Step-Down Converter Efficiency vs. Load (VOUT = 3.3V; L = 10μH; ENLDO = GND) 100 1.0 Step-Down Converter DC Regulation (VOUT = 3.3V; L = 6.8µH; ENLDO = GND) Output Error (%) Efficiency (%) 90 VIN = 3.9V VIN = 4.2V 0.5 VIN = 5.0V 80 0.0 70 -0.5 VIN = 4.2V 60 0.1 -1.0 1 10 100 1000 0.1 1 10 100 1000 Output Current (mA) Output Current (mA) Step-Down Converter Efficiency vs. Load (VOUT = 2.5V; L = 10μH; ENLDO = GND) 100 1.0 Step-Down Converter DC Regulation (VOUT = 2.5V; L = 6.8µH; ENLDO = GND) VIN = 3.3V Output Error (%) Efficiency (%) 90 0.5 VIN = 5.0V VIN = 4.2V VIN = 3.0V 80 VIN = 3.6V 0.0 70 -0.5 VIN = 3.6V VIN = 3.0V 60 0.1 1 10 100 1000 -1.0 0.1 1 10 100 1000 Output Current (mA) Output Current (mA) 8 2505.2006.06.1.1 Dual Channel, Step-Down Converter/Linear Regulator Typical Characteristics Unless otherwise noted, VIN = 5V, TA = 25°C. AAT2505 Step-Down Converter Efficiency vs. Load (VOUT = 1.5V; L = 4.7μH; ENLDO = GND) 100 90 1.0 Step-Down Converter DC Regulation (VOUT = 1.8V; L = 4.7µH; ENLDO = GND) VIN = 2.7V VIN = 3.6V Output Error (%) Efficiency (%) 0.5 80 70 60 50 0.1 1 VIN = 4.2V 0.0 VIN = 4.2V VIN = 3.6V -0.5 VIN = 2.7V 1 10 100 1000 10 100 1000 -1.0 0.1 Output Current (mA) Output Current (mA) Step-Down Converter Frequency vs. Input Voltage (VOUT = 1.8V; EN = VIN; ENLDO = GND) 1.0 2.0 Step-Down Converter Output Voltage Error vs. Temperature (VIN = 3.6V; VO = 1.5V; EN = VIN; ENLDO = GND) Frequency Variation (%) Output Error (%) 2.7 3.1 3.5 3.9 4.3 4.7 5.1 5.5 0.5 0.0 -0.5 -1.0 -1.5 -2.0 1.0 0.0 -1.0 -2.0 -40 -20 0 20 40 60 80 100 Input Voltage (V) Temperature (°C) Step-Down Converter Switching Frequency vs. Temperature (VIN = 3.6V; VO = 1.5V; EN = VIN; ENLDO = GND) 15.0 35 Step-Down Converter Input Current vs. Input Voltage (VO = 1.8V; EN = VIN; ENLDO = GND) 85°C 30 Frequency Variation (%) 12.0 9.0 6.0 3.0 0.0 -3.0 -6.0 -9.0 -12.0 -15.0 -40 15 -20 0 20 40 60 80 100 2.5 Input Current (μA) 25°C 25 20 -40°C 3.0 3.5 4.0 4.5 5.0 5.5 Temperature (°C) Input Voltage (V) 2505.2006.06.1.1 9 Dual Channel, Step-Down Converter/Linear Regulator Typical Characteristics Unless otherwise noted, VIN = 5V, TA = 25°C. Step-Down Converter P-Channel RDS(ON) vs. Input Voltage (EN = VIN; ENLDO = GND) 750 700 650 750 700 AAT2505 Step-Down Converter N-Channel RDS(ON) vs. Input Voltage (EN = VIN; ENLDO = GND) RDS(ON) (mΩ) RDS(ON) (mΩ) 120°C 100°C 650 600 550 500 450 400 350 300 25°C 120°C 100°C 600 550 500 450 400 350 300 2.5 3 .0 3.5 4 .0 4.5 5 .0 5.5 25°C 85°C 85°C 2.5 3 .0 3.5 4 .0 4.5 5 .0 5.5 Input Voltage (V) Input Voltage (V) Step-Down Converter Load Transient Response (1mA to 300mA; VIN = 3.6V; VOUT = 1.8V; C1 = 4.7µF; ENLDO = GND) 2.0 1.9 1.8 1.7 1.6 1.5 1.4 1.3 1.2 1.1 1.0 1.8 1.6 1.4 1.2 1.0 0.8 0.6 0.4 0.2 0.0 -0.2 Step-Down Converter Load Transient Response (1mA to 300mA; VIN = 3.6V; VOUT = 2.5V; C1 = 4.7µF; ENLDO = GND) 2.9 2.7 2.5 2.3 2.1 1.9 1.7 1.5 1.3 1.1 0.9 1.8 1.6 1.4 1.2 1.0 0.8 0.6 0.4 0.2 0.0 -0.2 Load and Inductor Current (200mA/div) (bottom) Load and Inductor Current (200mA/div) (bottom) Output Voltage (top) (V) Time (50µs/div) Output Voltage (top) (V) Time (50µs/div) Step-Down Converter Line Transient (VOUT = 1.8V @ 400mA) 1.84 1.82 1.80 1.78 1.76 1.74 7.6 6.6 Step-Down Converter Line Regulation (VOUT = 1.8V) 0.40 0.30 Output Voltage (top) (V) Accuracy (%) 0.20 0.10 0.00 -0.10 -0.20 -0.30 -0.40 2.5 3.0 3.5 IOUT = 10mA Input Voltage (bottom) (V) 5.6 4.6 3.6 2.6 IOUT = 1mA IOUT = 400mA 4.0 4.5 5.0 5.5 6.0 Time (25µs/div) Input Voltage (V) 10 2505.2006.06.1.1 Dual Channel, Step-Down Converter/Linear Regulator Typical Characteristics Unless otherwise noted, VIN = 5V, TA = 25°C. AAT2505 Step-Down Converter Soft Start (VIN = 3.6V; VOUT = 1.8V; 400mA; EN = VIN; ENLDO = GND) Step-Down Converter Output Ripple (VIN = 3.6V; VOUT = 1.8V; 400mA; EN = VIN; ENLDO = GND) Output Voltage (AC Coupled) (top) (mV) Enable and Output Voltage (top) (V) 5.0 4.0 3.0 2.0 1.0 0.0 -1.0 -2.0 -3.0 -4.0 -5.0 1.6 40 20 0 -20 -40 -60 -80 -100 -120 0.9 0.8 VEN VO 1.4 1.2 1.0 0.8 0.6 0.4 0.2 Inductor Current (bottom) (A) Inductor Current (bottom) (A) 0.7 0.6 0.5 0.4 0.3 0.2 0.1 IL 0.0 -0.2 -0.4 Time (100μs/div) Time (250ns/div) 2505.2006.06.1.1 11 Dual Channel, Step-Down Converter/Linear Regulator Functional Block Diagram VCC VP AAT2505 FB See Note Error Amp. DH Voltage Reference Logic DL LX EN SGND VLDO Control Logic PGND OUT Over-Current Protection Error Amp. ENLDO Fast Start Control POK Voltage Reference 94% + - GND Note: Internal resistor divider included for ≥ 1.2V versions. For low voltage versions, the feedback pin is tied directly to the error amplifier input. Functional Description The AAT2505 is a high performance power management IC comprised of a buck converter and a linear regulator. The high efficiency buck converter is capable of delivering up to 600mA. Designed to operate at 1.4MHz, the converter requires only three external components (CIN, COUT, and LX) and is stable with a ceramic output capacitor. The linear regulator delivers 300mA and also is stable with a ceramic output capacitor. cuit which accelerates the power-up behavior of fundamental control and feedback circuits within the LDO regulator. Fast turn-off time response is achieved by an active output pull-down circuit, which is enabled when the LDO regulator is placed in shutdown mode. This active fast shutdown circuit has no adverse effect on normal device operation. The LDO regulator output has been specifically optimized to function with low-cost, low-ESR ceramic capacitors; however, the design will allow for operation over a wide range of capacitor types. Other features include an integrated Power-OK comparator which indicates when the output is out of regulation. The POK open-drain output is low when OUT is 6% below its nominal regulation voltage. The open-drain signal is held low when the linear regulator is in shutdown mode. The regulator comes with complete short-circuit and thermal protection. The combination of these two internal protection circuits gives a comprehensive safety system to guard against extreme adverse operating conditions. Linear Regulator The advanced circuit design of the linear regulator has been specifically optimized for very fast start-up and shutdown timing. This proprietary CMOS LDO has also been tailored for superior transient response characteristics. These traits are particularly important for applications that require fast power supply timing. The high-speed turn-on capability is enabled through implementation of a fast-start control cir12 2505.2006.06.1.1 Dual Channel, Step-Down Converter/Linear Regulator The regulator features an enable/disable function. This pin (ENLDO) is active high and is compatible with CMOS logic. To assure the LDO regulator will switch on, the ENLDO turn-on control level must be greater than 1.5V. The LDO regulator will go into the disable shutdown mode when the voltage on the EN pin falls below 0.6V. If the enable function is not needed in a specific application, it may be tied to VIN to keep the LDO regulator in a continuously on state. When the regulator is in shutdown mode, an internal 20kΩ resistor is connected between OUT and GND. This is intended to discharge COUT when the LDO regulator is disabled. The internal 20kΩ resistor has no adverse impact on device turn-on time. either the input power or the enable input is applied. When pulled low, the enable input forces the converter into a low-power, non-switching state with a bias current of less than 1µA. A startup time of 150µs is achieved across the operating range. AAT2505 Low Dropout Operation For conditions where the input voltage drops to the output voltage level, the converter duty cycle increases to 100%. As 100% duty cycle is approached, the minimum off-time initially forces the high side on-time to exceed the 1.4MHz clock cycle and reduce the effective switching frequency. Once the input drops below the level where the output can be regulated, the high side P-channel MOSFET is turned on continuously for 100% duty cycle. At 100% duty cycle, the output voltage tracks the input voltage minus the IR drop of the high side P-channel MOSFET RDS(ON). Step-Down Converter The AAT2505 buck is a constant frequency peak current mode PWM converter with internal compensation. It is designed to operate with an input voltage range of 2.7V to 5.5V. The output voltage ranges from 0.6V to the input voltage for the internally fixed version (see Figure 1) , and up to 3.3V for the externally adjustable version (see Figure 2). The 0.6V fixed model is also the adjustable version and is externally programmable with a resistive divider. The converter MOSFET power stage is sized for 600mA load capability with up to 96% efficiency. Light load efficiency exceeds 80% at a 500µA load. Low Supply The under-voltage lockout (UVLO) guarantees sufficient VIN bias and proper operation of all internal circuitry prior to activation. Fault Protection For overload conditions, the peak inductor current is limited. Thermal protection disables switching when the internal dissipation or ambient temperature becomes excessive. The junction over-temperature threshold is 140°C with 15°C of hysteresis. Soft Start The AAT2505 soft-start control prevents output voltage overshoot and limits inrush current when VIN C3 10µF 3 5 9 4 10 2 11 12 1 VIN C3 10µF 3 5 4 10 2 11 12 1 VP VLDO ENLDO OUT POK GND VCC EN LX FB SGND PGND VP VLDO ENLDO OUT POK GND VCC EN LX FB SGND PGND L1 4.7µH VOUTBUCK VOUTLDO 9 6 7 L1 4.7µH R1 VOUTBUCK VOUTLDO 6 7 C4 4.7µF R3 100kΩ 8 C1 4.7µF C4 4.7µF R3 100kΩ 8 C8 100pF R2 59k U1 AAT2505 U1 AAT2505 C1 4.7µF Figure 1: AAT2505 Fixed Output. Figure 2: AAT2505 with Adjustable Step-Down Output and Enhanced Transient Response. 13 2505.2006.06.1.1 Dual Channel, Step-Down Converter/Linear Regulator Applications Information Linear Regulator Input and Output Capacitors: An input capacitor is not required for basic operation of the linear regulator. However, if the AAT2505 is physically located more than three centimeters from an input power source, a CIN capacitor will be needed for stable operation. Typically, a 1µF or larger capacitor is recommended for CIN in most applications. CIN should be located as closely to the device VIN pin as practically possible. An input capacitor greater than 1µF will offer superior input line transient response and maximize power supply ripple rejection. Ceramic, tantalum, or aluminum electrolytic capacitors may be selected for CIN. There is no specific capacitor ESR requirement for CIN. However, for 300mA LDO regulator output operation, ceramic capacitors are recommended for CIN due to their inherent capability over tantalum capacitors to withstand input current surges from low impedance sources such as batteries in portable devices. For proper load voltage regulation and operational stability, a capacitor is required between OUT and GND. The COUT capacitor connection to the LDO regulator ground pin should be made as directly as practically possible for maximum device performance. Since the regulator has been designed to function with very low ESR capacitors, ceramic capacitors in the 1.0µF to 10µF range are recommended for best performance. Applications utilizing the exceptionally low output noise and optimum power supply ripple rejection should use 2.2µF or greater for COUT. In low output current applications, where output load is less than 10mA, the minimum value for COUT can be as low as 0.47µF. Equivalent Series Resistance: ESR is a very important characteristic to consider when selecting a capacitor. ESR is the internal series resistance associated with a capacitor that includes lead resistance, internal connections, size and area, material composition, and ambient temperature. Typically, capacitor ESR is measured in milliohms for ceramic capacitors and can range to more than several ohms for tantalum or aluminum electrolytic capacitors. Ceramic Capacitor Materials: Ceramic capacitors less than 0.1µF are typically made from NPO or C0G materials. NPO and C0G materials generally have tight tolerance and are very stable over temperature. Larger capacitor values are usually composed of X7R, X5R, Z5U, or Y5V dielectric materials. Large ceramic capacitors (i.e., greater than 2.2µF) are often available in low-cost Y5V and Z5U dielectrics. These two material types are not recommended for use with the regulator, since the capacitor tolerance can vary more than ±50% over the operating temperature range of the device. A 2.2µF Y5V capacitor could be reduced to 1µF over temperature; this could cause problems for circuit operation. X7R and X5R dielectrics are much more desirable. The temperature tolerance of X7R dielectric is better than ±15%. Capacitor area is another contributor to ESR. Capacitors that are physically large in size will have a lower ESR when compared to a smaller sized capacitor of an equivalent material and capacitance value. These larger devices can improve circuit transient response when compared to an equal value capacitor in a smaller package size. Consult capacitor vendor datasheets carefully when selecting capacitors for LDO regulators. AAT2505 Step-Down Converter Inductor Selection: The step-down converter uses peak current mode control with slope compensation to maintain stability for duty cycles greater than 50%. The output inductor value must be selected so the inductor current down slope meets the internal slope compensation requirements. The internal slope compensation for the adjustable and low-voltage fixed versions of the AAT2505 is 0.24A/µsec. This equates to a slope compensation that is 75% of the inductor current down slope for a 1.5V output and 4.7µH inductor. m= 0.75 ⋅ VO 0.75 ⋅ 1.5V A = = 0.24 L 4.7μH μsec 14 2505.2006.06.1.1 Dual Channel, Step-Down Converter/Linear Regulator This is the internal slope compensation for the adjustable (0.6V) version or low-voltage fixed versions. When externally programming the 0.6V version to 2.5V, the calculated inductance is 7.5µH. AAT2505 Input Capacitor Select a 4.7µF to 10µF X7R or X5R ceramic capacitor for the input. To estimate the required input capacitor size, determine the acceptable input ripple level (VPP) and solve for C. The calculated value varies with input voltage and is a maximum when VIN is double the output voltage. L= 0.75 ⋅ VO = m μsec 0.75 ⋅ VO ≈ 3 A ⋅ VO A 0.24A μsec =3 μsec ⋅ 2.5V = 7.5μH A CIN = VOBUCK ⎛ VOBUCK⎞ · 1⎝ VIN VIN ⎠ ⎛ VPP ⎞ - ESR · FS ⎝ IOBUCK ⎠ In this case, a standard 6.8µH value is selected. For high-voltage fixed versions (2.5V and above), m = 0.48A/µsec. Table 1 displays inductor values for the AAT2505 fixed and adjustable options. Manufacturer's specifications list both the inductor DC current rating, which is a thermal limitation, and the peak current rating, which is determined by the saturation characteristics. The inductor should not show any appreciable saturation under normal load conditions. Some inductors may meet the peak and average current ratings yet result in excessive losses due to a high DCR. Always consider the losses associated with the DCR and its effect on the total converter efficiency when selecting an inductor. The 4.7µH CDRH3D16 series inductor selected from Sumida has a 105mΩ DCR and a 900mA DC current rating. At full load, the inductor DC loss is 17mW which gives a 2.8% loss in efficiency for a 400mA, 1.5V output. ⎞1 VOBUCK ⎛ V · 1 - OBUCK = for VIN = 2 × VOBUCK ⎝ VIN VIN ⎠ 4 CIN(MIN) = 1 ⎛ VPP ⎞ - ESR · 4 · FS ⎝ IOBUCK ⎠ Always examine the ceramic capacitor DC voltage coefficient characteristics when selecting the proper value. For example, the capacitance of a 10µF, 6.3V, X5R ceramic capacitor with 5.0V DC applied is actually about 6µF. The maximum input capacitor RMS current is: ⎞ VOBUCK ⎛ V · 1 - OBUCK ⎝ VIN VIN ⎠ IRMS = IOBUCK · Configuration 0.6V Adjustable With External Feedback Fixed Output Output Voltage 1V, 1.2V 1.5V, 1.8V 2.5V, 3.3V 0.6V to 3.3V Table 1: Inductor Values. Inductor 2.2µH 4.7µH 6.8µH 4.7µH 2505.2006.06.1.1 15 Dual Channel, Step-Down Converter/Linear Regulator The input capacitor RMS ripple current varies with the input and output voltage and will always be less than or equal to half of the total DC load current. A laboratory test set-up typically consists of two long wires running from the bench power supply to the evaluation board input voltage pins. The inductance of these wires, along with the low-ESR ceramic input capacitor, can create a high Q network that may affect converter performance. This problem often becomes apparent in the form of excessive ringing in the output voltage during load transients. Errors in the loop phase and gain measurements can also result. Since the inductance of a short PCB trace feeding the input voltage is significantly lower than the power leads from the bench power supply, most applications do not exhibit this problem. In applications where the input power source lead inductance cannot be reduced to a level that does not affect the converter performance, a high ESR tantalum or aluminum electrolytic should be placed in parallel with the low ESR, ESL bypass ceramic. This dampens the high Q network and stabilizes the system. AAT2505 VOBUCK ⎛ VOBUCK⎞ · 1= ⎝ VIN VIN ⎠ for VIN = 2 x VOBUCK D · (1 - D) = 0.52 = 1 2 IRMS(MAX) = VOBUCK ⎛ IOBUCK 2 · 1The term appears in both the ⎝ VIN VIN ⎠ input voltage ripple and input capacitor RMS current equations and is a maximum when VOBUCK is twice VIN. This is why the input voltage ripple and the input capacitor RMS current ripple are a maximum at 50% duty cycle. VOBUCK⎞ The input capacitor provides a low impedance loop for the edges of pulsed current drawn by the AAT2505. Low ESR/ESL X7R and X5R ceramic capacitors are ideal for this function. To minimize stray inductance, the capacitor should be placed as closely as possible to the IC. This keeps the high frequency content of the input current localized, minimizing EMI and input voltage ripple. The proper placement of the input capacitor (C2) can be seen in the evaluation board layout in Figure 3. Output Capacitor The output capacitor limits the output ripple and provides holdup during large load transitions. A 4.7µF to 10µF X5R or X7R ceramic capacitor provides sufficient bulk capacitance to stabilize the output during large load transitions and has the ESR and ESL characteristics necessary for low output ripple. Figure 3: AAT2505 Evaluation Board Top Side. Figure 4: AAT2505 Evaluation Board Bottom Side. 2505.2006.06.1.1 16 Dual Channel, Step-Down Converter/Linear Regulator The output voltage droop due to a load transient is dominated by the capacitance of the ceramic output capacitor. During a step increase in load current, the ceramic output capacitor alone supplies the load current until the loop responds. Within two or three switching cycles, the loop responds and the inductor current increases to match the load current demand. The relationship of the output voltage droop during the three switching cycles to the output capacitance can be estimated by: 3 · ΔILOAD VDROOP · FS AAT2505 To limit the bias current required for the external feedback resistor string while maintaining good noise immunity, the minimum suggested value for R2 is 59kΩ. Although a larger value will further reduce quiescent current, it will also increase the impedance of the feedback node, making it more sensitive to external noise and interference. Table 2 summarizes the resistor values for various output voltages with R2 set to either 59kΩ for good noise immunity or 221kΩ for reduced no load input current. ⎛ VOUT ⎞ ⎛ 1.5V ⎞ R1 = V -1 · R2 = 0.6V - 1 · 59kΩ = 88.5kΩ ⎝ REF ⎠ ⎝ ⎠ COUT = Once the average inductor current increases to the DC load level, the output voltage recovers. The above equation establishes a limit on the minimum value for the output capacitor with respect to load transients. The internal voltage loop compensation limits the minimum output capacitor value to 4.7µF. This is due to its effect on the loop crossover frequency (bandwidth), phase margin, and gain margin. Increased output capacitance will reduce the crossover frequency with greater phase margin. The maximum output capacitor RMS ripple current is given by: VOUT · (VIN(MAX) - VOUT) L · FS · VIN(MAX) 2· 3 · 1 The adjustable version of the AAT2505, combined with an external feedforward capacitor (C8 in Figures 2 and 5), delivers enhanced transient response for extreme pulsed load applications. The addition of the feedforward capacitor typically requires a larger output capacitor C1 for stability. R2 = 59kΩ VOUT (V) 0.8 0.9 1.0 1.1 1.2 1.3 1.4 1.5 1.8 1.85 2.0 2.5 3.3 R2 = 221kΩ R1 (kΩ) 75 113 150 187 221 261 301 332 442 464 523 715 1000 R1 (kΩ) 19.6 29.4 39.2 49.9 59.0 68.1 78.7 88.7 118 124 137 187 267 IRMS(MAX) = Dissipation due to the RMS current in the ceramic output capacitor ESR is typically minimal, resulting in less than a few degrees rise in hot-spot temperature. Adjustable Output Resistor Selection For applications requiring an adjustable output voltage, the 0.6V version can be externally programmed. Resistors R1 and R2 of Figure 5 program the output to regulate at a voltage higher than 0.6V. Table 2: Adjustable Resistor Values For Use With 0.6V Step-Down Converter. 2505.2006.06.1.1 17 Dual Channel, Step-Down Converter/Linear Regulator AAT2505 LX1 VOUTBUCK C7 0.01µF C1 4.7µF1 L1 Table 3 1 2 3 4 3 2 1 5 6 U1 AAT2505 PGND LX VP VCC IN OUT SGND FB EN ENLDO GND POK 12 11 10 9 8 7 C9 n/a R1 Table 3 C81 R2 59k 3 2 1 C2 10µF VIN1 Buck Enable 3 2 1 LDO Input C3 10µF GND C4 4.7µF LDO Enable GND VOUTLDO R3 100k 1 POK Figure 5: AAT2505 Evaluation Board Schematic. Thermal Calculations There are three types of losses associated with the AAT2505 step-down converter: switching losses, conduction losses, and quiescent current losses. Conduction losses are associated with the RDS(ON) characteristics of the power output switching devices. Switching losses are dominated by the gate charge of the power output switching devices. At full load, assuming continuous conduction mode (CCM), a simplified form of the step-down converter and LDO losses is given by: IOBUCK2 · (RDSON(H) · VOBUCK + RDSON(L) · [VIN - VOBUCK]) VIN IQBUCK is the step-down converter quiescent current and IQLDO is the LDO quiescent current. The term tsw is used to estimate the full load step-down converter switching losses. For the condition where the buck converter is in dropout at 100% duty cycle, the total device dissipation reduces to: PTOTAL = IOBUCK2 · RDSON(H) + IOLDO · (VIN - VOLDO) + (IQBUCK + IQLDO) · VIN PTOTAL = + (tsw · FS · IOBUCK + IQBUCK + IQLDO) · VIN + IOLDO · (VIN - VOLDO) Since RDS(ON), quiescent current, and switching losses all vary with input voltage, the total losses should be investigated over the complete input voltage range. 1. For step-down converter, enhanced transient configuration C8 = 100pF and C1 = 10µF. 18 2505.2006.06.1.1 Dual Channel, Step-Down Converter/Linear Regulator Given the total losses, the maximum junction temperature can be derived from the θJA for the TDFN33-12 package which is 50°C/W. TJ(MAX) = PTOTAL · ΘJA + TAMB AAT2505 PCB Layout The following guidelines should be used to ensure a proper layout. 1. The input capacitor C2 should connect as closely as possible to VP and PGND, as shown in Figure 4. 2. The output capacitor and inductor should be connected as closely as possible. The connection of the inductor to the LX pin should also be as short as possible. 3. The feedback trace should be separate from any power trace and connect as closely as possible to the load point. Sensing along a high-current load trace will degrade DC load regulation. If external feedback resistors are used, they should be placed as closely as possible to the FB pin. This prevents noise from being coupled into the high impedance feedback node. 4. The resistance of the trace from the load return to GND should be kept to a minimum. This will help to minimize any error in DC regulation due to differences in the potential of the internal signal ground and the power ground. 5. For good thermal coupling, PCB vias are required from the pad for the TDFN paddle to the ground plane. The via diameter should be 0.3mm to 0.33mm and positioned on a 1.2mm grid. 2505.2006.06.1.1 19 Dual Channel, Step-Down Converter/Linear Regulator Step-Down Converter Design Example Specifications VOBUCK = 1.8V @ 400mA (adjustable using 0.6V version), Pulsed Load ΔILOAD = 300mA VOLDO = 3.3V @ 300mA VIN FS TAMB = 2.7V to 4.2V (3.6V nominal) = 1.4MHz = 85°C AAT2505 1.8V Buck Output Inductor L1 = 3 µsec µsec ⋅ VO2 = 3 ⋅ 1.8V = 5.4µH A A (use 4.7µH; see Table 1) For Sumida inductor CDRH3D16, 4.7µH, DCR = 105mΩ. ⎛ VO V⎞ 1.8V 1.8V ⎞ ⎛ ⋅ 1- O = ⋅ 1= 156mA L1 ⋅ FS ⎝ VIN ⎠ 4.7μH ⋅ 1.4MHz ⎝ 4.2V ⎠ ΔIL1 = IPKL1 = IO + ΔIL1 = 0.4A + 0.068A = 0.468A 2 PL1 = IO2 ⋅ DCR = 0.4A2 ⋅ 105mΩ = 17mW 1.8V Buck Output Capacitor VDROOP = 0.1V 3 · ΔILOAD 3 · 0.3A = = 6.4µF; use 10µF VDROOP · FS 0.1V · 1.4MHz (VO) · (VIN(MAX) - VO) 1 1.8V · (4.2V - 1.8V) · = 45mArms = L1 · FS · VIN(MAX) 2 · 3 4.7µH · 1.4MHz · 4.2V 2· 3 1 · COUT = IRMS = Pesr = esr · IRMS2 = 5mΩ · (45mA)2 = 10µW 20 2505.2006.06.1.1 Dual Channel, Step-Down Converter/Linear Regulator 1.8V Buck Input Capacitor Input Ripple VPP = 25mV AAT2505 CIN = 1 ⎛ VPP ⎞ - ESR · 4 · FS ⎝ IOBUCK ⎠ = 1 = 4.75μF ⎛ 25mV ⎞ - 5mΩ · 4 · 1.4MHz ⎝ 0.4A ⎠ IRMS = IOBUCK = 0.2Arms 2 P = esr · IRMS2 = 5mΩ · (0.2A)2 = 0.2mW AAT2505 Total Losses IOBUCK2 · (RDSON(H) · VOBUCK + RDSON(L) · [VIN - VOBUCK]) VIN PTOTAL = + (tsw · FS · IOBUCK + IQBUCK + IQLDO) · VIN + (VIN - VOLDO) · IOLDO = 0.42 · (0.725Ω · 1.8V + 0.7Ω · [4.2V - 1.8V]) 4.2V + (5ns · 1.4MHz · 0.4A + 50µA +125µA) · 4.2V + (4.2V - 3.3V) · 0.3A = 395mW TJ(MAX) = TAMB + ΘJA · PLOSS = 85°C + (50°C/W) · 395mW = 105°C 2505.2006.06.1.1 21 Dual Channel, Step-Down Converter/Linear Regulator VOUT (V) Adjustable Version (0.6V device) AAT2505 R1 (kΩ) R2 = 59kΩ R1 (kΩ) R2 = 221kΩ1 L1 (µH) 0.8 0.9 1.0 1.1 1.2 1.3 1.4 1.5 1.8 1.85 2.0 2.5 3.3 19.6 29.4 39.2 49.9 59.0 68.1 78.7 88.7 118 124 137 187 267 75.0 113 150 187 221 261 301 332 442 464 523 715 1000 4.7 4.7 4.7 4.7 4.7 4.7 4.7 4.7 4.7 4.7 4.7 or 6.8 10 10 VOUT (V) Fixed Version R1 (kΩ) R2 Not Used L1 (µH) 4.7 0.6-3.3V 0 Table 3: Evaluation Board Component Values. Manufacturer Sumida Sumida MuRata MuRata MuRata Coilcraft Coilcraft Coiltronics Coiltronics Coiltronics Coiltronics Part Number CDRH3D16-4R7 CDRH3D16/HP100 LQH32CN4R7M23 LQH32CN4R7M33 LQH32CN4R7M53 LPO6610-472 LPO3310-472 SDRC10-4R7 SDR10-4R7 SD3118-4R7 SD18-4R7 Inductance (µH) 4.7 10 4.7 4.7 4.7 4.7 4.7 4.7 4.7 4.7 4.7 Max DC Current (A) 0.90 0.84 0.45 0.65 0.65 1.10 0.80 1.53 1.30 0.98 1.77 DCR (Ω) 0.11 0.23 0.20 0.15 0.15 0.20 0.27 0.117 0.122 0.122 0.082 Size (mm) LxWxH 4.0x4.0x1.8 4.0x4.0x1.8 2.5x3.2x2.0 2.5x3.2x2.0 2.5x3.2x1.55 5.5x6.6x1.0 3.3x3.3x1.0 4.5x3.6x1.0 5.7x4.4x1.0 3.1x3.1x1.85 5.2x5.2x1.8 Type Shielded Shielded Non-Shielded Non-Shielded Non-Shielded 1mm 1mm 1mm Shielded 1mm Shielded Shielded Shielded Table 4: Typical Surface Mount Inductors. 1. For reduced quiescent current R2 = 221kΩ. 22 2505.2006.06.1.1 Dual Channel, Step-Down Converter/Linear Regulator Manufacturer MuRata MuRata AAT2505 Part Number GRM219R61A475KE19 GRM21BR60J106KE19 Value 4.7µF 10µF Voltage 10V 6.3V Temp. Co. X5R X5R Case 0805 0805 Table 5: Surface Mount Capacitors. 2505.2006.06.1.1 23 Dual Channel, Step-Down Converter/Linear Regulator Ordering Information Package TDFN33-12 TDFN33-12 AAT2505 Voltage Buck Converter LDO Marking1 POXYY PPXYY Part Number (Tape and Reel)2 AAT2505IWP-AQ-T1 AAT2505IWP-AO-T1 Adj. Adj. 2.8V 2.6V All AnalogicTech products are offered in Pb-free packaging. The term “Pb-free” means semiconductor products that are in compliance with current RoHS standards, including the requirement that lead not exceed 0.1% by weight in homogeneous materials. For more information, please visit our website at http://www.analogictech.com/pbfree. Legend Voltage Adjustable (0.6V) 0.9 1.2 1.5 1.8 1.9 2.5 2.6 2.7 2.8 2.85 2.9 3.0 3.3 4.2 Code A B E G I Y N O P Q R S T W C 1. XYY = assembly and date code. 2. Sample stock is generally held on part numbers listed in BOLD. 24 2505.2006.06.1.1 Dual Channel, Step-Down Converter/Linear Regulator TDFN33-12 AAT2505 Index Area (D/2 x E/2) Detail "B" 3.00 ± 0.05 2.40 ± 0.05 0.3 ± 0.10 0.16 0.375 ± 0.125 0.075 ± 0.075 0.1 REF Top View Bottom View Pin 1 Indicator (optional) 7.5° ± 7.5° + 0.05 0.8 -0.20 0.229 ± 0.051 0.05 ± 0.05 Option A: C0.30 (4x) max Chamfered corner Option B: R0.30 (4x) max Round corner Detail "B" Side View All dimensions in millimeters. Detail "A" 0.23 ± 0.05 0.45 ± 0.05 Detail "A" 3.00 ± 0.05 1.70 ± 0.05 2505.2006.06.1.1 25 Dual Channel, Step-Down Converter/Linear Regulator AAT2505 © Advanced Analogic Technologies, Inc. AnalogicTech cannot assume responsibility for use of any circuitry other than circuitry entirely embodied in an AnalogicTech product. No circuit patent licenses, copyrights, mask work rights, or other intellectual property rights are implied. AnalogicTech reserves the right to make changes to their products or specifications or to discontinue any product or service without notice. Customers are advised to obtain the latest version of relevant information to verify, before placing orders, that information being relied on is current and complete. All products are sold subject to the terms and conditions of sale supplied at the time of order acknowledgement, including those pertaining to warranty, patent infringement, and limitation of liability. AnalogicTech warrants performance of its semiconductor products to the specifications applicable at the time of sale in accordance with AnalogicTech’s standard warranty. Testing and other quality control techniques are utilized to the extent AnalogicTech deems necessary to support this warranty. Specific testing of all parameters of each device is not necessarily performed. AnalogicTech and the AnalogicTech logo are trademarks of Advanced Analogic Technologies Incorporated. All other brand and product names appearing in this document are registered trademarks or trademarks of their respective holders. Advanced Analogic Technologies, Inc. 830 E. Arques Avenue, Sunnyvale, CA 94085 Phone (408) 737-4600 Fax (408) 737-4611 26 2505.2006.06.1.1