AAT2515IWP-AA-T1

PRODUCT DATASHEET AAT2515 SystemPowerTM General Description The AAT2515 is a dual channel synchronous buck converter operating with an input voltage range of 2.7V to 5.5V, making it ideal for applications with single-cell lithium-ion/polymer batteries. Both regulators have independent input and enable pins. Offered with fixed or adjustable output voltages, each channel is designed to operate with 27μA (typical) of quiescent current, allowing for high efficiency under light load conditions. The AAT2515 requires only three external components (CIN, COUT, and LX) for each converter, minimizing cost and real estate. Both channels are designed to deliver 600mA of load current and operate with a switching frequency of 1.4MHz, reducing the size of external components. The AAT2515 is available in a Pb-free, 12-pin TDFN33 package and is rated over the -40°C to +85°C temperature range. Dual 600mA Fast Transient High Frequency Buck Converter Features • VIN Range: 2.7V to 5.5V • Output Current: ▪ Channel 1: 600mA ▪ Channel 2: 600mA • 98% Efficient Step-Down Converter • Integrated Power Switches • 100% Duty Cycle • 1.4MHz Switching Frequency • Internal Soft Start • 150μs Typical Turn-On Time • Over-Temperature Protection • Current Limit Protection • TDFN33-12 Package • -40°C to +85°C Temperature Range Applications • • • • • Cellular Phones Digital Cameras Handheld Instruments Microprocessor / DSP Core / IO Power PDAs and Handheld Computers Typical Application V OUT1 VIN1 LX1 L1 4.7μH V BAT C IN 10μF VIN2 FB1 AAT2515 EN1 LX2 L2 4.7μH EN2 GND FB2 VOUT2 COUT 10μF 10μF 2515.2007.12.1.0 www.analogictech.com 1 PRODUCT DATASHEET AAT2515 AAT2515 SystemPowerTM Pin Descriptions Pin # 1 2 3, 6, 7, 10 4 5 8 9 11 12 Dual 600mA Fast Transient High Frequency Buck Converter Symbol EN1 FB1 GND EN2 FB2 LX2 VIN2 LX1 VIN1 Function Enable pin for Channel 1. Active high. When connected low, it disables the channel and consumes less than 1μA of current. Feedback input pin for Channel 1. This pin is connected to the converter output. It is used to see the output of the converter to regulate to the desired value via an external resistor divider. Ground. Enable pin for Channel 2. Active high. When connected low, it disables the channel and consumes less than 1μA of current. Feedback input pin for Channel 2. This pin is connected to the converter output. It is used to see the output of the converter to regulate to the desired value via an external resistor divider. Power switching node for Channel 2. Output switching node that connects to the output inductor. Input supply voltage for Channel 2. Must be closely decoupled. Power switching node for Channel 2. Output switching node that connects to the output inductor. Input supply voltage for Channel 1. Must be closely decoupled. Pin Configuration TDFN33-12 (Top View) EN1 FB1 GND EN2 FB2 GND 1 2 3 4 5 6 12 11 10 9 8 7 VIN1 LX1 GND VIN2 LX2 GND 2 www.analogictech.com 2515.2007.12.1.0 PRODUCT DATASHEET AAT2515 AAT2515 SystemPowerTM Dual 600mA Fast Transient High Frequency Buck Converter Absolute Maximum Ratings1 Symbol VIN VLX VFB VEN TJ TLEAD Description Input Voltages to GND LX to GND FB1 and FB2 to GND EN1 and EN2 to GND Operating Junction Temperature Range Maximum Soldering Temperature (at leads, 10 sec) Value 6.0 -0.3 to VIN + 0.3 -0.3 to VIN + 0.3 -0.3 to 6.0 -40 to 150 300 Units V V V V °C °C Thermal Information Symbol PD θJA Description Maximum Power Dissipation Thermal Resistance2 Value 2.0 50 Units W °C/W 1. Stresses above those listed in Absolute Maximum Ratings may cause permanent damage to the device. Functional operation at conditions other than the operating conditions specified is not implied. Only one Absolute Maximum Rating should be applied at any one time. 2. Mounted on an FR4 board. 2515.2007.12.1.0 www.analogictech.com 3 PRODUCT DATASHEET AAT2515 AAT2515 SystemPowerTM Dual 600mA Fast Transient High Frequency Buck Converter Electrical Characteristics1 VIN = 3.6V; TA = -40°C to +85°C, unless otherwise noted. Typical values are TA = 25°C. Symbol VIN VOUT VOUT IQ ISHDN ILX_LEAK IFB ILIM RDS(ON)H RDS(ON)L ΔVLINE FOSC TS TSD THYS VEN(L) VEN(H) IEN Description Input Voltage Output Voltage Tolerance Output Voltage Range Quiescent Current Shutdown Current LX Leakage Current Feedback Leakage P-Channel Current Limit High Side Switch On Resistance Low Side Switch On Resistance Line Regulation Oscillator Frequency Start-Up Time Over-Temperature Shutdown Threshold Over-Temperature Shutdown Hysteresis Enable Threshold Low Enable Threshold High Input Low Current Conditions IOUT = 0 to 600mA; VIN = 2.7V to 5.5V Per Channel EN1 = EN2 = GND VIN = 5.5V, VLX = 0 to VIN VFB = 1.0V Both Channels Min 2.7 -3.0 0.6 Typ Max 5.5 3.0 VIN 70 1.0 1.0 0.2 Units V % V μA μA μA μA A Ω Ω % MHz μs °C °C V V μA 27 VIN = 2.7V to 5.5V From Enable to Output Regulation; Both Channels 1.2 0.45 0.40 0.2 1.4 150 140 15 0.6 1.4 -1.0 VIN = VFB = 5.5V 1.0 1. The AAT2515 is guaranteed to meet performance specifications over the -40°C to +85°C operating temperature range and is assured by design, characterization, and correlation with statistical process controls. 4 www.analogictech.com 2515.2007.12.1.0 PRODUCT DATASHEET AAT2515 AAT2515 SystemPowerTM Typical Characteristics EN1 = VIN; EN2 = GND. Dual 600mA Fast Transient High Frequency Buck Converter Efficiency vs. Load (VOUT = 1.8V; L = 4.7μH) 100 90 1.0 DC Regulation (VOUT = 1.8V) VIN = 2.7V Output Error (%) 0.5 Efficiency (%) 80 70 60 50 0.1 VIN = 3.6V VIN = 4.2V VIN = 4.2V 0.0 -0.5 VIN = 3.6V VIN = 2.7V 1 10 100 1000 1 10 100 1000 -1.0 0.1 Output Current (mA) Output Current (mA) Efficiency vs. Load (VOUT = 2.5V; L = 6.8μH) 100 90 DC Regulation (VOUT = 2.5V) 1.0 VIN = 2.7V Output Error (%) VIN = 5.0V VIN = 4.2V VIN = 3.6V VIN = 4.2V 0.5 Efficiency (%) VIN = 5.0V 80 70 60 50 0.1 0.0 -0.5 VIN = 3.6V VIN = 3.0V 1 10 100 1000 -1.0 0.1 1 10 100 1000 Output Current (mA) Output Current (mA) Efficiency vs. Load (VOUT = 3.3V; L = 6.8μH) 100 90 DC Regulation (VOUT = 3.3V; L = 6.8µH) 1.0 VIN = 3.6V Output Error (%) VIN = 4.2V VIN = 5.0V VIN = 5.0V 0.5 Efficiency (%) 80 70 60 50 0.1 VIN = 4.2V 0.0 -0.5 VIN = 3.6V 1 10 100 1000 -1.0 0.1 1 10 100 1000 Output Current (mA) Output Current (mA) 2515.2007.12.1.0 www.analogictech.com 5 PRODUCT DATASHEET AAT2515 AAT2515 SystemPowerTM Typical Characteristics EN1 = VIN; EN2 = GND. Dual 600mA Fast Transient High Frequency Buck Converter Soft Start (VIN = 3.6V; VOUT = 1.8V; IOUT = 400mA) Enable and Output Voltage (top) (V) 5.0 4.0 3.0 2.0 1.0 0.0 -1.0 -2.0 -3.0 -4.0 -5.0 1.6 1.4 1.0 0.8 0.6 0.4 0.2 0.0 -0.2 -0.4 1.2 0.40 0.30 Line Regulation (VOUT = 1.8V) VEN VO Accuracy (%) 0.20 0.10 0.00 -0.10 -0.20 -0.30 -0.40 2.5 3.0 3.5 IOUT = 10mA Inductor Current (bottom) (A) IOUT = 1mA IL IOUT = 400mA 4.0 4.5 5.0 5.5 6.0 Time (100μs/div) Input Voltage (V) Output Voltage Error vs. Temperature (VIN = 3.6V; VO = 1.8V; IOUT = 400mA) 2.0 15.0 12.0 9.0 Switching Frequency vs. Temperature (VIN = 3.6V; VOUT = 1.8V) Output Error (%) Variation (%) 1.0 6.0 3.0 0.0 -3.0 -6.0 -9.0 -12.0 -15.0 -40 0.0 -1.0 -2.0 -40 -20 0 20 40 60 80 100 -20 0 20 40 60 80 100 Temperature (°C) Temperature (°C) Frequency vs. Input Voltage 2.0 No Load Quiescent Current vs. Input Voltage 50 Frequency Variation (%) Supply Current (μA) 1.0 0.0 -1.0 -2.0 -3.0 -4.0 VOUT = 1.8V 45 40 35 30 25 20 15 10 85°C 25°C VOUT = 2.5V VOUT = 3.3V -40°C 2.7 3.1 3.5 3.9 4.3 4.7 5.1 5.5 2.7 3.1 3.5 3.9 4.3 4.7 5.1 5.5 Input Voltage (V) Input Voltage (V) 6 www.analogictech.com 2515.2007.12.1.0 PRODUCT DATASHEET AAT2515 AAT2515 SystemPowerTM Typical Characteristics EN1 = VIN; EN2 = GND. Dual 600mA Fast Transient High Frequency Buck Converter P-Channel RDS(ON) vs. Input Voltage 750 700 650 750 700 650 N-Channel RDS(ON) vs. Input Voltage RDS(ON) (mΩ) RDS(ON) (mΩ) 120°C 100°C 120°C 600 550 500 450 400 350 300 2.5 3.0 3.5 4.0 4.5 5.0 5.5 6.0 25°C 85°C 600 550 500 450 400 350 300 2.5 3.0 3.5 25°C 85°C 100°C 4.0 4.5 5.0 5.5 6.0 Input Voltage (V) Input Voltage (V) Load Transient Response (1mA to 300mA; VIN = 3.6V; VOUT = 1.8V; C1 = 10μF; CFF = 100pF) 2.0 1.9 1.90 1.85 1.80 1.75 Load Transient Response (300mA to 400mA; VIN = 3.6V; VOUT = 1.8V; C1 = 4.7μF) Load and Inductor Current (200mA/div) (bottom) Load and Inductor Current (200mA/div) (bottom) VO IO 400mA 300mA 0.4 VO IO IL Output Voltage (top) (V) 1.7 300mA 1mA Output Voltage (top) (V) 1.8 0 IL Time (50μs/div) 0.3 0.2 0.1 Time (50μs/div) Load Transient Response (300mA to 400mA; VIN = 3.6V; VOUT = 1.8V; C1 = 10μF) 1.90 1.85 1.80 1.75 Load Transient Response (300mA to 400mA; VIN = 3.6V; VOUT = 1.8V; C1 = 10μF; C4 = 100pF) 1.850 1.825 1.800 1.775 Load and Inductor Current (200mA/div) (bottom) Load and Inductor Current (200mA/div) (bottom) VO IO 400mA 300mA 0.4 VO IO Output Voltage (top) (V) Output Voltage (top) (V) 400mA 300mA 0.4 IL Time (50μs/div) 0.3 0.2 0.1 IL Time (50μs/div) 0.3 0.2 0.1 2515.2007.12.1.0 www.analogictech.com 7 PRODUCT DATASHEET AAT2515 AAT2515 SystemPowerTM Typical Characteristics EN1 = VIN; EN2 = GND. Dual 600mA Fast Transient High Frequency Buck Converter Line Response (VOUT = 1.8V @ 400mA) Output Voltage (AC coupled) (top) (mV) 1.82 1.81 6.0 5.5 40 20 0 -20 -40 -60 -80 -100 -120 Output Ripple (VIN = 3.6V; VOUT = 1.8V; IOUT = 1mA) 0.30 VO 0.25 Inductor Current (bottom) (A) Output Voltage (top) (V) 0.20 0.15 0.10 Input Voltage (bottom) (V) 1.80 1.79 1.78 1.77 1.76 5.0 4.5 4.0 3.5 3.0 IL 0.05 0.00 -0.05 -0.10 Time (25μs/div) Time (10µs/div) Output Ripple (VIN = 3.6V; VOUT = 1.8V; IOUT = 400mA) Output Voltage (AC coupled) (top) (mV) 40 20 0 -20 -40 -60 -80 -100 -120 0.9 VO 0.8 Inductor Current (bottom) (A) 0.7 0.6 0.5 0.4 0.3 IL Time (500ns/div) 0.2 0.1 8 www.analogictech.com 2515.2007.12.1.0 PRODUCT DATASHEET AAT2515 SystemPowerTM Dual 600mA Fast Transient High Frequency Buck Converter Functional Block Diagram FB1 VIN1 Err. Amp. Comp. DH Logic Voltage Reference LX1 DL EN1 Control Logic GND GND See Note VIN2 FB2 Err. Amp. Comp. DH LX2 Logic DL Voltage Reference EN2 See Note Control Logic GND GND Note: Internal resistor divider included for fixed output voltage versions. For low voltage versions, the feedback pin is tied directly to the error amplifier input. Functional Description The AAT2515 is a high performance power management IC comprised of two buck converters. Each channel has independent input voltages and enable pins. Designed to operate at 1.4MHz of switching frequency, the converters require only three external components (CIN, COUT, and LX), minimizing cost and size of external components. Both converters are designed to operate with an input voltage range of 2.7V to 5.5V. Typical values of the output filter are 4.7μH and 10μF ceramic capacitor. The output voltage operates to as low as 0.6V and is offered as both fixed and adjustable. Power devices are sized for 600mA current capability while maintaining over 90% efficiency at full load. Light load efficiency is maintained at greater than 80% down to 500μA of load current. Both channels have excellent transient response, load, and line regulation. Transient response time is typically less than 20μs. The AAT2515 also features soft-start control to limit inrush current. Soft start increases the inductor current limit point in discrete steps when power is applied to the input or when the enable pins are pulled high. It limits the current surge seen at the input and eliminates output voltage overshoot. The enable input, when pulled low, forces the converter into a low power, non-switching state consuming less than 1μA of current. For overload conditions, the peak input current is limited. As load impedance decreases and the output voltage falls closer to zero, more power is dissipated internally, raising the device temperature. Thermal protection completely disables switching when internal dissipation becomes excessive, protecting the device from damage. The junction over-temperature threshold is 140°C with 15°C of hysteresis. The under-voltage lockout guarantees sufficient VIN bias and proper operation of all internal circuits prior to activation. 2515.2007.12.1.0 www.analogictech.com 9 PRODUCT DATASHEET AAT2515 SystemPowerTM Dual 600mA Fast Transient High Frequency Buck Converter Input Capacitor Select a 4.7μF to 10μF X7R or X5R ceramic capacitor for the input. To estimate the required input capacitor size, determine the acceptable input ripple level (VPP) and solve for C. The calculated value varies with input voltage and is a maximum when VIN is double the output voltage. Applications Information Inductor Selection The step-down converter uses peak current mode control with slope compensation to maintain stability for duty cycles greater than 50%. The output inductor value must be selected so the inductor current down slope meets the internal slope compensation requirements. The internal slope compensation for the adjustable and low-voltage fixed versions of the AAT2515 is 0.24A/μs. This equates to a slope compensation that is 75% of the inductor current down slope for a 1.5V output and 4.7μH inductor. CIN = V⎞ VO ⎛ ⋅ 1- O VIN ⎝ VIN ⎠ ⎛ VPP ⎞ - ESR ⋅ FS ⎝ IO ⎠ m= 0.75 ⋅ VO 0.75 ⋅ 1.5V A = = 0.24 L 4.7µH µs This equation provides an estimate for the input capacitor required for a single channel. Configuration 0.6V Adjustable With External Feedback Fixed Output Output Voltage 1V, 1.2V 1.5V, 1.8V 2.5V, 3.3V 0.6V to 3.3V Inductor 2.2μH 4.7μH 6.8μH 4.7μH This is the internal slope compensation for the adjustable (0.6V) version or low-voltage fixed version. When externally programming the 0.6V version to a 2.5V output, the calculated inductance would be 7.5μH. Table 1: Inductor Values. 0.75V 0.75 ⋅ VO µs ≈ 3 A ⋅ VO L= = m 0.24A /µs =3 µs ⋅ 2.5V = 7.5µH A The equation below solves for input capacitor size for both channels. It makes the worst-case assumptions that both converters are operating at 50% duty cycle and are synchronized. In this case, a standard 6.8μH value is selected. For highvoltage fixed versions (2.5V and above), m = 0.48A/μs. Table 1 displays inductor values for the AAT2515 fixed and adjustable options. Manufacturer’s specifications list both the inductor DC current rating, which is a thermal limitation, and the peak current rating, which is determined by the saturation characteristics. The inductor should not show any appreciable saturation under normal load conditions. Some inductors may meet the peak and average current ratings yet result in excessive losses due to a high DCR. Always consider the losses associated with the DCR and its effect on the total converter efficiency when selecting an inductor. The 4.7μH CDRH3D16 series inductor selected from Sumida has a 105mΩ DCR and a 900mA DC current rating. At full load, the inductor DC loss is 37.8mW which gives a 4.2% loss in efficiency for a 600mA 1.5V output. CIN = 1 ⎛ VPP ⎞ - ESR · 4 · FS ⎝ IO1 + IO2 ⎠ Because the AAT2515 channels will generally operate at different duty cycles and are not synchronized, the actual ripple will vary and be less than the ripple (VPP) used to solve for the input capacitor in the equation above. Always examine the ceramic capacitor DC voltage coefficient characteristics when selecting the proper value. For example, the capacitance of a 10μF 6.3V X5R ceramic capacitor with 5V DC applied is actually about 6μF. The maximum input capacitor RMS current is: IRMS = IO1 · ⎛ ⎝ VO1 ⎛ V⎞ · 1 - O1 ⎞ + IO2 · ⎛ VIN ⎝ VIN ⎠ ⎠ ⎝ VO2 ⎛ V⎞ · 1 - O2 ⎞ VIN ⎝ VIN ⎠ ⎠ 10 www.analogictech.com 2515.2007.12.1.0 PRODUCT DATASHEET AAT2515 SystemPowerTM Dual 600mA Fast Transient High Frequency Buck Converter the power leads from the bench power supply, most applications do not exhibit this problem. In applications where the input power source lead inductance cannot be reduced to a level that does not affect converter performance, a high ESR tantalum or aluminum electrolytic capacitor should be placed in parallel with the low ESR, ESL bypass ceramic capacitor. This dampens the high Q network and stabilizes the system. The input capacitor RMS ripple current varies with the input and output voltage and will always be less than or equal to half of the total DC load current of both converters combined. IRMS(MAX) = IO1(MAX) + IO2(MAX) 2 This equation also makes the worst-case assumption that both converters are operating at 50% duty cycle and are synchronized. Since the converters are not synchronized and are not both operating at 50% duty cycle, the actual RMS current will always be less than this. Losses associated with the input ceramic capacitor are typically minimal. The term V ⎝ V ⎠ appears in both the input voltage ripple and input capacitor RMS current equations. It is a maximum when VO is twice VIN. This is why the input voltage ripple and the input capacitor RMS current ripple are a maximum at 50% duty cycle. IN IN Output Capacitor The output capacitor limits the output ripple and provides holdup during large load transitions. A 10μF X5R or X7R ceramic capacitor typically provides sufficient bulk capacitance to stabilize the output during large load transitions and has the ESR and ESL characteristics necessary for low output ripple. The output voltage droop due to a load transient is dominated by the capacitance of the ceramic output capacitor. During a step increase in load current the ceramic output capacitor alone supplies the load current until the loop responds. As the loop responds, the inductor current increases to match the load current demand. This typically takes several switching cycles and can be estimated by: VO ⎛ V⎞ · 1- O The input capacitor provides a low impedance loop for the edges of pulsed current drawn by the AAT2515. Low ESR/ ESL X7R and X5R ceramic capacitors are ideal for this function. To minimize the stray inductance, the capacitor should be placed as closely as possible to the IC. This keeps the high frequency content of the input current localized, minimizing EMI and input voltage ripple. The proper placement of the input capacitor (C3 and C8) can be seen in the evaluation board layout in Figure 2. Since decoupling must be as close to the input pins as possible, it is necessary to use two decoupling capacitors. C3 provides the bulk capacitance required for both converters, while C8 is a high frequency bypass capacitor for the second channel (see C3 and C8 placement in Figure 2). A laboratory test set-up typically consists of two long wires running from the bench power supply to the evaluation board input voltage pins. The inductance of these wires, along with the low ESR ceramic input capacitor, can create a high Q network that may affect converter performance. This problem often becomes apparent in the form of excessive ringing in the output voltage during load transients. Errors in the loop phase and gain measurements can also result. Since the inductance of a short printed circuit board trace feeding the input voltage is significantly lower than COUT = 3 · ΔILOAD VDROOP · FS Once the average inductor current increases to the DC load level, the output voltage recovers. The above equation establishes a limit on the minimum value for the output capacitor with respect to load transients. The internal voltage loop compensation also limits the minimum output capacitor value to 10μF. This is due to its effect on the loop crossover frequency (bandwidth), phase margin, and gain margin. Increased output capacitance will reduce the crossover frequency with greater phase margin. The maximum output capacitor RMS ripple current is given by: IRMS(MAX) = VOUT · (VIN(MAX) - VOUT) L · F · VIN(MAX) 2· 3 · 1 Dissipation due to the RMS current in the ceramic output capacitor ESR is typically minimal, resulting in less than a few degrees rise in hot spot temperature. 2515.2007.12.1.0 www.analogictech.com 11 PRODUCT DATASHEET AAT2515 SystemPowerTM Dual 600mA Fast Transient High Frequency Buck Converter Thermal Calculations There are three types of losses associated with the AAT2515 converter: switching losses, conduction losses, and quiescent current losses. Conduction losses are associated with the RDS(ON) characteristics of the power output switching devices. Switching losses are dominated by the gate charge of the power output switching devices. At full load, assuming continuous conduction mode (CCM), a simplified form of the dual converter losses is given by: Adjustable Output Resistor Selection For applications requiring an adjustable output voltage, the 0.6V version can be programmed externally. Resistors R1 through R4 of Table 2 program the output to regulate at a voltage higher than 0.6V. To limit the bias current required for the external feedback resistor string, the minimum suggested value for R2 and R4 is 59kΩ. Although a larger value will reduce the quiescent current, it will also increase the impedance of the feedback node, making it more sensitive to external noise and interference. Table 2 summarizes the resistor values for various output voltages with R2 and R4 set to either 59kΩ for good noise immunity or 221kΩ for reduced no load input current. PTOTAL = IO12 · (RDSON(HS) · VO1 + RDSON(LS) · [VIN -VO1]) VIN IO22 · (RDSON(HS) · VO2 + RDSON(LS) · [VIN -VO2]) VIN ⎛ VOUT ⎞ ⎛ 1.5V ⎞ R1 = V -1 · R2 = 0.6V - 1 · 59kΩ = 88.5kΩ ⎝ REF ⎠ ⎝ ⎠ The adjustable version of the AAT2515 in combination with an external feedforward capacitor (C4 and C5 of Figure 1) delivers enhanced transient response for extreme pulsed load applications. The addition of the feedforward capacitor typically requires a larger output capacitor (C1 and C2) for stability. R2, R4 = 59kΩ VOUT (V) 0.8 0.9 1.0 1.1 1.2 1.3 1.4 1.5 1.8 1.85 2.0 2.5 3.3 + + (tsw · F · [IO1 + IO2] + 2 · IQ) · VIN IQ is the AAT2515 quiescent current for one channel and tsw is used to estimate the full load switching losses. For the condition where channel one is in dropout at 100% duty cycle, the total device dissipation reduces to: R2, R4 = 221kΩ R1, R3 75K 113K 150K 187K 221K 261K 301K 332K 442K 464K 523K 715K 1.00M R1, R3 (kΩ) 19.6 29.4 39.2 49.9 59.0 68.1 78.7 88.7 118 124 137 187 267 PTOTAL = IO12 · RDSON(HS) IO22 · (RDSON(HS) · VO2 + RDSON(LS) · [VIN -VO2]) VIN + + (tsw · F · IO2 + 2 · IQ) · VIN Since RDS(ON), quiescent current, and switching losses all vary with input voltage, the total losses should be investigated over the complete input voltage range. Given the total losses, the maximum junction temperature can be derived from the θJA for the TDFN33-12 package which is 50°C/W. Table 2: Adjustable Resistor Values For Use With 0.6V Version. TJ(MAX) = PTOTAL · ΘJA + TAMB 12 www.analogictech.com 2515.2007.12.1.0 PRODUCT DATASHEET AAT2515 SystemPowerTM PCB Layout The following guidelines should be used to insure a proper layout. 1. Due to the pin placement of VIN for both converters, proper decoupling is not possible with just one input capacitor. The large input capacitor C3 should connect as closely as possible to VIN and GND, as shown in Figure 2. The additional input bypass capacitor C8 is necessary for proper high frequency decoupling of the second converter. 2. The output capacitor and inductor should be connected as closely as possible. The connection of the inductor to the LX pin should also be as short as possible. Dual 600mA Fast Transient High Frequency Buck Converter 3. The feedback trace should be separate from any power trace and connect as closely as possible to the load point. Sensing along a high-current load trace will degrade DC load regulation. If external feedback resistors are used, they should be placed as closely as possible to the FB pin. This prevents noise from being coupled into the high impedance feedback node. The resistance of the trace from the load return to GND should be kept to a minimum. This will help to minimize any error in DC regulation due to differences in the potential of the internal signal ground and the power ground. For good thermal coupling, PCB vias are required from the pad for the TDFN paddle to the ground plane. The via diameter should be 0.3mm to 0.33mm and positioned on a 1.2 mm grid. 4. 5. 2515.2007.12.1.0 www.analogictech.com 13 PRODUCT DATASHEET AAT2515 AAT2515 SystemPowerTM Design Example Specifications VO1 VO2 VIN FS TAMB = = = = = 2.5V @ 600mA (adjustable using 0.6V version), pulsed load ΔILOAD = 300mA 1.8V @ 600mA (adjustable using 0.6V version), pulsed load ΔILOAD = 300mA 2.7V to 4.2V (3.6V nominal) 1.4 MHz 85°C Dual 600mA Fast Transient High Frequency Buck Converter 2.5V VO1 Output Inductor µs µs L1 = 3 A ⋅ VO1 = 3 A ⋅ 2.5V = 7.5µH (see Table 1) For Sumida inductor CDRH3D16, 10μH, DCR = 210mΩ. ΔI1 = ⎛ 2.5V⎞ VO1 ⎛ V⎞ 2.5V ⋅ 1 - O1 = ⋅ 1= 72.3mA L1 ⋅ F ⎝ VIN ⎠ 10μH ⋅ 1.4MHz ⎝ 4.2V⎠ IPK1 = IO1 + ΔI1 = 0.6A + 0.036A = 0.64A 2 PL1 = IO12 ⋅ DCR = 0.6A2 ⋅ 210mΩ = 75.6mW 1.8V VO2 Output Inductor µs µs L2 = 3 A ⋅ VO2 = 3 A ⋅ 1.8V = 5.4µH (see Table 1) For Sumida inductor CDRH3D16, 4.7μH, DCR = 105mΩ. ΔI2 = ⎛ 1.8V ⎞ VO2 ⎛ V⎞ 1.8V ⋅ 1 - O2 = ⋅ 1= 156mA L⋅F ⎝ VIN ⎠ 4.7μH ⋅ 1.4MHz ⎝ 4.2V⎠ IPK2 = IO2 + ΔI2 = 0.6A + 0.078A = 0.68A 2 PL2 = IO22 ⋅ DCR = 0.6A2 ⋅ 105mΩ = 37.8mW 14 www.analogictech.com 2515.2007.12.1.0 PRODUCT DATASHEET AAT2515 AAT2515 SystemPowerTM 2.5V Output Capacitor COUT = 3 · ΔILOAD 3 · 0.3A = = 6.4µF; use 10µF VDROOP · FS 0.1V · 1.4MHz 1 2· 3 · (VOUT) · (VIN(MAX) - VOUT) 1 2.5V · (4.2V - 2.5V) · = 21mArms = L · F · VIN(MAX) 2 · 3 10µH · 1.4MHz · 4.2V Dual 600mA Fast Transient High Frequency Buck Converter IRMS(MAX) = Pesr = esr · IRMS2 = 5mΩ · (21mA)2 = 2.2µW 1.8V Output Capacitor COUT = 3 · ΔILOAD 3 · 0.3A = = 6.4µF; use 10µF VDROOP · FS 0.1V · 1.4MHz (VOUT) · (VIN(MAX) - VOUT) 1 1.8V · (4.2V - 1.8V) · = 45mArms = L · F · VIN(MAX) 2 · 3 4.7µH · 1.4MHz · 4.2V 2· 3 1 · IRMS(MAX) = Pesr = esr · IRMS2 = 5mΩ · (45mA)2 = 10µW Input Capacitor Input Ripple VPP = 25mV. CIN = 1 ⎛ VPP ⎞ - ESR · 4 · FS ⎝ IO1 + IO2 ⎠ = 1 = 11.3µF; use 10µF ⎛ 25mV ⎞ - 5mΩ · 4 · 1.4MHz ⎝ 1.2A ⎠ IRMS(MAX) = IO1 + IO2 = 0.6Arms 2 P = esr · IRMS2 = 5mΩ · (0.6A)2 = 1.8mW 2515.2007.12.1.0 www.analogictech.com 15 PRODUCT DATASHEET AAT2515 AAT2515 SystemPowerTM AAT2515 Losses The maximum dissipation occurs at dropout where VIN = 2.7V. All values assume an ambient temperature of 85°C and a junction temperature of 120°C. Dual 600mA Fast Transient High Frequency Buck Converter PTOTAL = IO12 · (RDSON(HS) · VO1 + RDSON(LS) · (VIN -VO1)) + IO22 · (RDSON(HS) · VO2 + RDSON(LS) · (VIN -VO2)) VIN + (tsw · F · IO2 + 2 · IQ) · VIN = 0.62 · (0.725Ω · 2.5V + 0.7Ω · (2.7V - 2.5V)) + 0.62 · (0.725Ω · 1.8V + 0.7Ω · (2.7V - 1.8V)) 2.7V + 5ns · 1.4MHz · 0.6A + 60μA) · 2.7V = 530mW TJ(MAX) = TAMB + ΘJA · PLOSS = 85°C + (50°C/W) · 530mW = 111°C Output 1 Enable VIN 123 C41 R1 see Table 3 U1 AAT2515 1 2 3 LX1 12 11 EN1 FB1 GND EN2 FB2 GND VIN1 LX1 GND VIN2 LX2 GND L1 see Table 3 C3 VO1 LX2 L2 see Table 3 C11 10μF C7 0.01μF C21 10μF GND C6 0.01μF VO2 10 9 8 7 C51 R3 see Table 3 4 5 6 10μF R4 59.0k GND R2 59.0k C8 0.1μF 321 Output 2 Enable Figure 1: AAT2515 Evaluation Board Schematic. 1. For enhanced transient configuration C5, C4 = 100pF. 16 www.analogictech.com 2515.2007.12.1.0 PRODUCT DATASHEET AAT2515 AAT2515 SystemPowerTM Adjustable Version (0.6V device) VOUT (V) 0.8 0.9 1.0 1.1 1.2 1.3 1.4 1.5 1.8 1.85 2.0 2.5 3.3 Dual 600mA Fast Transient High Frequency Buck Converter R2, R4 = 59kΩ R1, R3 (kΩ) 19.6 29.4 39.2 49.9 59.0 68.1 78.7 88.7 118 124 137 187 267 R2, R4 = 221kΩ1 R1, R3 (kΩ) 75.0 113 150 187 221 261 301 332 442 464 523 715 1000 L1, L2 (μH) 2.2 2.2 2.2 2.2 2.2 2.2 4.7 4.7 4.7 4.7 6.8 6.8 6.8 Fixed Version VOUT (V) 0.6-3.3V R2, R4 Not Used R1, R3 (kΩ) 0 L1, L2 (μH) 4.7 Table 3: Evaluation Board Component Values. Figure 2: AAT2515 Evaluation Board Top Side. Figure 3: AAT2515 Evaluation Board Bottom Side. 1. For reduced quiescent current, R2 and R4 = 221kΩ. 2515.2007.12.1.0 www.analogictech.com 17 PRODUCT DATASHEET AAT2515 AAT2515 SystemPowerTM Manufacturer Sumida Sumida Sumida Murata Murata Coilcraft Coiltronics Coiltronics Coiltronics Dual 600mA Fast Transient High Frequency Buck Converter Part Number Inductance (μH) 2.2 4.7 6.8 4.7 4.7 4.7 4.7 6.8 4.7 Max DC Current (A) 1.20 0.90 0.73 0.40 0.45 0.80 0.98 0.82 1.30 DCR (Ω) 0.072 0.105 0.170 0.80 0.20 0.27 0.122 0.175 0.122 Size (mm) LxWxH 3.8x3.8x1.8 3.8x3.8x1.8 3.8x3.8x1.8 2.0x1.6x0.95 2.5x3.2x2.0 3.2x3.2x1.0 3.1x3.1x1.85 3.1x3.1x1.85 5.7x4.4x1.0 Type Shielded Shielded Shielded Non-Shielded Non-Shielded 1mm Shielded Shielded 1mm Shielded CDRH3D16-2R2 CDRH3D16-4R7 CDRH3D16-6R8 LQH2MCN4R7M02 LQH32CN4R7M23 LPO3310-472 SD3118-4R7 SD3118-6R8 SDRC10-4R7 Table 4: Typical Surface Mount Inductors. Manufacturer Murata Murata Murata Part Number GRM219R61A475KE19 GRM21BR60J106KE19 GRM21BR60J226ME39 Value 4.7μF 10uF 22uF Temp. Co. X5R X5R X5R Case 0805 0805 0805 Table 5: Surface Mount Capacitors. 18 www.analogictech.com 2515.2007.12.1.0 PRODUCT DATASHEET AAT2515 AAT2515 SystemPowerTM Ordering Information Voltage Package TDFN33-12 Channel 1 0.6V Channel 2 0.6V Dual 600mA Fast Transient High Frequency Buck Converter Marking1 2XXYY Part Number (Tape and Reel)2 AAT2515IWP-AA-T1 All AnalogicTech products are offered in Pb-free packaging. The term “Pb-free” means semiconductor products that are in compliance with current RoHS standards, including the requirement that lead not exceed 0.1% by weight in homogeneous materials. For more information, please visit our website at http://www.analogictech.com/pbfree. Legend Voltage Adjustable (0.6V) 0.9 1.2 1.5 1.8 1.9 2.5 2.6 2.7 2.8 2.85 2.9 3.0 3.3 4.2 Code A B E G I Y N O P Q R S T W C 1. XYY = assembly and date code. 2. Sample stock is generally held on part numbers listed in BOLD. 2515.2007.12.1.0 www.analogictech.com 19 PRODUCT DATASHEET AAT2515 AAT2515 SystemPowerTM Package Information TDFN33-12 Index Area Detail "A" 0.43 ± 0.05 Dual 600mA Fast Transient High Frequency Buck Converter 3.00 ± 0.05 2.40 ± 0.05 0.1 REF C0.3 0.45 ± 0.05 Pin 1 Indicator (optional) 3.00 ± 0.05 1.70 ± 0.05 Top View Bottom View Detail "A" 0.75 ± 0.05 0.05 ± 0.05 Side View All dimensions in millimeters. 1. The leadless package family, which includes QFN, TQFN, DFN, TDFN and STDFN, has exposed copper (unplated) at the end of the lead terminals due to the manufacturing process. A solder fillet at the exposed copper edge cannot be guaranteed and is not required to ensure a proper bottom solder connection. Advanced Analogic Technologies, Inc. 3230 Scott Boulevard, Santa Clara, CA 95054 Phone (408) 737-4600 Fax (408) 737-4611 © Advanced Analogic Technologies, Inc. AnalogicTech cannot assume responsibility for use of any circuitry other than circuitry entirely embodied in an AnalogicTech product. No circuit patent licenses, copyrights, mask work rights, or other intellectual property rights are implied. AnalogicTech reserves the right to make changes to their products or specifications or to discontinue any product or service without notice. Except as provided in AnalogicTech’s terms and conditions of sale, AnalogicTech assumes no liability whatsoever, and AnalogicTech disclaims any express or implied warranty relating to the sale and/or use of AnalogicTech products including liability or warranties relating to fitness for a particular purpose, merchantability, or infringement of any patent, copyright or other intellectual property right. In order to minimize risks associated with the customer’s applications, adequate design and operating safeguards must be provided by the customer to minimize inherent or procedural hazards. Testing and other quality control techniques are utilized to the extent AnalogicTech deems necessary to support this warranty. Specific testing of all parameters of each device is not necessarily performed. AnalogicTech and the AnalogicTech logo are trademarks of Advanced Analogic Technologies Incorporated. All other brand and product names appearing in this document are registered trademarks or trademarks of their respective holders. 20 www.analogictech.com 0.23 ± 0.05 0.23 ± 0.05 2515.2007.12.1.0