AAT2550ISK-CAA-T1

PRODUCT DATASHEET AAT2550178 SystemPowerTM General Description Total Power Solution for Portable Applications Features • Two Step-Down Converters: ▪ 600mA Output Current per Converter ▪ VIN Range: 2.7V to 5.5V ▪ 1.4MHz Switching Frequency ▪ Low RDS(ON) 0.4Ω Integrated Power Switches ▪ Internal Soft Start ▪ 27μA Quiescent Current per Converter • Highly Integrated Battery Charger: ▪ Programmable Charging Current from 100mA to 1A ▪ Pass Device ▪ Reverse Blocking Diodes ▪ Current Sensing Resistor ▪ Digital Thermal Regulation • Short-Circuit, Over-Temperature, and Current Limit Protection • QFN44-24 Package • -40°C to +85°C Temperature Range The AAT2550 is a fully integrated total power solution with two step-down converters plus a single-cell lithiumion / polymer battery charger. The step-down converter input voltage range spans 2.7V to 5.5V, making the AAT2550 ideal for systems powered by single-cell lithium-ion/polymer batteries. The battery charger is a complete constant current/ constant voltage linear charger. It offers an integrated pass device, reverse blocking protection, high current accuracy and voltage regulation, charge status, and charge termination. The charging current is programmable via external resistor from 100mA to 1A. In addition to these standard features, the device offers over-voltage, overcurrent, and thermal protection. The two step-down converters are highly integrated, operating at a switching frequency of 1.4MHz, minimizing the size of external components while keeping switching losses low. Each converter has independent input, enable, and feedback pins. The output voltage ranges from 0.6V to VIN. Each converter is capable of delivering up to 600mA of load current. The AAT2550 is available in a Pb-free, space-saving, thermally-enhanced QFN44-24 package and is rated over the -40°C to +85°C temperature range. Applications • • • • • Cellular Telephones Digital Cameras Handheld Instruments MP3, Portable Music, and Portable Media Players PDAs and Handheld Computers Typical Application Battery Pack Adapter ADP BAT Batt+ AAT2550 STAT1 STAT2 Serial Interface RSET TS Batt- DATA ADPSET CT Temp LXA ENBAT INA Li-Ion Battery or Adapter V OUTA COUTA FBA LXB FBB GND VOUTB COUTB INB ENA ENB 2550.2008.02.1.3 www.analogictech.com 1 PRODUCT DATASHEET AAT2550178 AAT2550178 SystemPowerTM Pin Descriptions Pin # 1 2 3, 17 4 5, 7 6 8 9 10, 11, 22 12 13 14 15 16 18 19 20 21 23 24 EP Total Power Solution for Portable Applications Symbol ENA LXA PGND DATA N/C ADPSET BAT ADP AGND ENBAT TS STAT2 STAT1 CT LXB ENB INB FBB FBA INA Function Enable pin for Converter A. When connected to logic low, it disables the step-down converter and consumes less than 1μA of current. When connected to logic high, the converter operates normally. Power switching node for Converter A. Connect the inductor to this pin. Internally, it is connected to the drain of both high- and low-side MOSFETs. Power ground. Connect the PGND pins together as close to the IC as possible. Connect AGND to PGND at a single point as close to the IC as possible. Status report to the microcontroller via serial interface (open drain). Not connected. Charge current set point. Connect a resistor from this pin to ground. Refer to Typical Characteristics curves for resistor selection. Battery charging and sensing. Connect the positive terminal of the battery to BAT. Input for adapter charger. Analog signal ground. Connect AGND to PGND at a single point as close to the IC as possible. Enable pin for the battery charger. When connected to logic low, the battery charger is disabled and consumes less than 1μA of current. When connected to logic high, the charger operates normally. Temperature sense input. Connect to a 10kΩ NTC thermistor. Battery charge status indicator pin to drive an LED. It is an open drain input. Battery charge status indicator pin to drive an LED. It is an open drain input. Timing capacitor to adjust internal watchdog timer. Sets maximum charge time for adapter powered trickle, constant current, and constant voltage charge modes. Power switching node for Converter B. Connect the inductor to this pin. Internally, it is connected to the drain of both high- and low-side MOSFETs. Enable pin for Converter B. When connected to logic low, it disables the step-down converter and consumes less than 1μA of current. When connected to logic high, the converter operates normally. Input voltage for Converter B. Output voltage feedback input for Converter B. FBB senses the output voltage B for regulation control. The FBB regulation threshold is 0.6V. A resistive voltage divider is connected to the output B, FBB, and AGND. Output voltage feedback input for Converter A. FBA senses the output voltage A for regulation control. The FBA regulation threshold is 0.6V. A resistive voltage divider is connected to the output A, FBA, and AGND. Input voltage for Converter A. Exposed paddle; connect to ground directly beneath the package. Pin Configuration QFN44-24 (Top View) ENB INB FBB AGND FBA INA 24 23 22 21 20 19 ENA LXA PGND DATA N/C ADPSET 1 2 3 4 5 6 10 11 12 7 8 9 18 17 16 15 14 13 LXB PGND CT STAT1 STAT2 TS 2 www.analogictech.com ENBAT AGND AGND ADP BAT N/C 2550.2008.02.1.3 PRODUCT DATASHEET AAT2550178 AAT2550178 Units V V V °C °C SystemPowerTM Absolute Maximum Ratings1 Symbol VINA/B, VADP VLXA/B, VFBA/B VX TJ TLEAD Total Power Solution for Portable Applications Description INA, INB, and ADP Voltages to GND VLXA, VLXB, VFBA, and VFBB to GND Voltage on All Other Pins to GND Operating Junction Temperature Range Maximum Soldering Temperature (at leads, 10 sec) Value -0.3 to 6.0 -0.3 to VINA/B, VADP + 0.3 -0.3 to 6.0 -40 to 150 300 Thermal Information Symbol PD θJA Description Maximum Power Dissipation Thermal Resistance2 Value 2.0 50 Units W °C/W 1. Stresses above those listed in Absolute Maximum Ratings may cause permanent damage to the device. Functional operation at conditions other than the operating conditions specified is not implied. Only one Absolute Maximum Rating should be applied at any one time. 2. Mounted on an FR4 printed circuit board. 2550.2008.02.1.3 www.analogictech.com 3 PRODUCT DATASHEET AAT2550178 AAT2550178 SystemPowerTM Electrical Characteristics1 Total Power Solution for Portable Applications VIN = 3.6V; TA = -40°C to +85°C, unless otherwise noted. Typical values are at TA = 25°C. Symbol Description Conditions Min 2.7 VIN Rising Hysteresis VIN Falling IOUT = 0 to 600mA, VIN = 2.7V to 5.5V Per Converter Each Converter VENA = VENB = GND Each Converter VIN = 5.5V, VLX = 0 to VIN, VENA = VENB = GND VFB = 0.6V VOUT > 0.6V No Load, TA = 25°C 100 1.8 -3.0 0.6 27 0.8 1.0 1.0 0.2 250 0.591 0.6 0.45 0.40 0.1 1.4 140 15 0.6 VIN = VFB = 5.5V 1.4 -1.0 1.0 0.609 3.0 VIN 600 70 1.0 Typ Max 5.5 2.7 Units V V mV V % V mA μA μA A μA μA kΩ V Ω Ω %/V MHz °C °C V V μA Step-Down Converters A and B Input Voltage VIN VUVLO VOUT VOUT IOUT IQ ISHDN ILIM ILX_LEAK IFB_LEAK RFB VFB RDS(ON)H RDS(ON)L ΔVLineReg FOSC TSD THYS VEN(L) VEN(H) IEN Under-Voltage Lockout Threshold Output Voltage Tolerance Output Voltage Range Output Current Quiescent Current Shutdown Current P-Channel Current Limit LX Leakage Current Feedback Leakage FB Impedance Feedback Threshold Voltage Accuracy (0.6V Adjustable Version) High-Side Switch On Resistance Low-Side Switch On Resistance Line Regulation Switching Frequency Over-Temperature Shutdown Threshold Over-Temperature Shutdown Hysteresis Enable Threshold Low Enable Threshold High Input Low Current VIN = 2.7V to 5.5V 1. The AAT2550 is guaranteed to meet performance specifications over the -40°C to +85°C operating temperature range and is assured by design, characterization, and correlation with statistical process controls. 4 www.analogictech.com 2550.2008.02.1.3 PRODUCT DATASHEET AAT2550178 AAT2550178 SystemPowerTM Total Power Solution for Portable Applications Electrical Characteristics1 (continued) VADP = 5V; TA = -40°C to +85°C, unless otherwise noted. Typical values are at TA = 25°C. Symbol Description Conditions Min 4.0 Rising Edge ICHARGE = 100mA VBAT = 4.25V VBAT = 4V, ADP Pin Open VEN = GND 4.158 2.80 100 Constant Current Mode VIN = 5.5V CT = 100nF, VADP = 5.5V CT = 100nF, VADP = 5.5V CT = 100nF, VADP = 5.5V ISINK = 4mA 0.20 10 2.0 4000 0.25 3.0 25 3.0 8.0 4.4 10 7.5 80 330 15 2.3 10 3.0 150 0.75 0.3 1.0 4.2 0.5 3.0 VBAT_EOC - 0.1 Typ Max 5.5 Units V V mV mA μA μA μA V % V V mA % V Ω Hour Minute Hour V mA V % % μA mV V mV mA V V ns μs kHz °C °C °C °C Battery Charger VADP Adapter Voltage Range Under-Voltage Lockout VUVLO UVLO Hysteresis IQ Quiescent Current ISLEEP Sleep Mode Current ILEAKAGE Reverse Leakage Current ISHDN Shutdown Current VBAT_EOC2 End of Charge Voltage Accuracy ΔVCH/VCH Output Charge Voltage Tolerance VMIN Preconditioning Voltage Threshold VRCH Battery Recharge Voltage Threshold ICH Charge Current ΔICH/ICH Charge Current Regulation Tolerance VADPSET ADPSET Pin Voltage KIA Current Set Factor: ICH/IADPSET Charger Pass Device RDS(ON) TC Constant Current Mode Time-Out TP Preconditioning Time-Out TV Constant Voltage Mode Time-Out VSTAT Output Low Voltage ISTAT STAT Sink Current VOVP Over-Voltage Protection ITK/ICH Preconditioning (Trickle Charge) Current ITERM/ICH Charge Termination Threshold Current ITS Current Source from TS Pin TS1 TS2 IDATA VDATA(H) VDATA(L) SQPULSE TPeriod FDATA TREG TLOOP_IN TLOOP_OUT TSD TS Hot Temperature Fault TS Cold Temperature Fault DATA Pin Sink Current Input High Threshold Input Low Threshold Status Request Pulse Width System Clock Period Data Output Frequency Thermal Loop Regulation Thermal Loop Entering Threshold Thermal Loop Exiting Threshold Over-Temperature Shutdown Threshold 3.0 1.0 1.0 4.242 3.15 1000 0.35 0.4 Threshold Hysteresis Threshold Hysteresis DATA Pin is Active Low 70 310 2.2 3.0 1.6 90 350 2.4 0.4 200 50 20 90 110 85 145 1. The AAT2550 is guaranteed to meet performance specifications over the -40°C to +85°C operating temperature range and is assured by design, characterization, and correlation with statistical process controls. 2. End of Charge Voltage Accuracy is specified over the 0° to 70°C ambient temperature range. 2550.2008.02.1.3 www.analogictech.com 5 PRODUCT DATASHEET AAT2550178 AAT2550178 SystemPowerTM Total Power Solution for Portable Applications Typical Characteristics — Step-Down Converter Efficiency vs. Load (VOUT = 1.8V; L = 4.7μH) 100 90 1.0 DC Regulation (VOUT = 1.8V) VIN = 2.7V Output Error (%) 0.5 Efficiency (%) 80 70 60 50 0.1 VIN = 3.6V VIN = 4.2V VIN = 4.2V 0.0 -0.5 VIN = 3.6V VIN = 2.7V 1 10 100 1000 -1.0 0.1 1 10 100 1000 Output Current (mA) Output Current (mA) Efficiency vs. Load (VOUT = 2.5V; L = 6.8μH) 100 1.0 DC Regulation (VOUT = 2.5V) VIN = 2.7V Output Error (%) 90 VIN = 4.2V 0.5 Efficiency (%) 80 70 60 50 0.1 VIN = 5.0V VIN = 4.2V VIN = 3.6V VIN = 5.0V 0.0 -0.5 VIN = 3.6V VIN = 3.0V -1.0 1 10 100 1000 0.1 1 10 100 1000 Output Current (mA) Output Current (mA) Efficiency vs. Load (VOUT = 3.3V; L = 6.8μH) 100 DC Regulation (VOUT = 3.3V; L = 6.8µH) 1.0 VIN = 3.6V Output Error (%) 90 VIN = 5.0V 0.5 Efficiency (%) 80 70 60 50 0.1 VIN = 4.2V VIN = 5.0V VIN = 4.2V 0.0 -0.5 VIN = 3.6V -1.0 1 10 100 1000 0.1 1 10 100 1000 Output Current (mA) Output Current (mA) 6 www.analogictech.com 2550.2008.02.1.3 PRODUCT DATASHEET AAT2550178 AAT2550178 SystemPowerTM Total Power Solution for Portable Applications Typical Characteristics — Step-Down Converter (continued) Soft Start (VIN = 3.6V; VOUT = 1.8V; IOUT = 400mA) Enable and Output Voltage (top) (V) 5.0 4.0 3.0 2.0 1.0 0.0 0.6 0.4 0.2 0.40 0.30 Line Regulation (VOUT = 1.8V) VEN VO Inductor Current (bottom) (A) Accuracy (%) 0.20 0.10 0.00 -0.10 -0.20 -0.30 -0.40 2.5 3.0 3.5 IOUT = 10mA IOUT = 1mA IOUT = 400mA IL 0.0 -0.2 -0.4 4.0 4.5 5.0 5.5 6.0 Time (100μs/div) Input Voltage (V) Output Voltage Error vs. Temperature (VIN = 3.6V; VO = 1.8V; IOUT = 400mA) 2.0 15.0 12.0 9.0 Switching Frequency vs. Temperature (VIN = 3.6V; VOUT = 1.8V) Output Error (%) Variation (%) 1.0 6.0 3.0 0.0 -3.0 -6.0 -9.0 -12.0 -15.0 -40 0.0 -1.0 -2.0 -40 -20 0 20 40 60 80 100 -20 0 20 40 60 80 100 Temperature (°C) Temperature (°C) Frequency vs. Input Voltage 2.0 No Load Quiescent Current vs. Input Voltage 50 Frequency Variation (%) 1.0 0.0 -1.0 VOUT = 1.8V Supply Current (μA) 45 40 35 30 25 20 15 10 85°C 25°C VOUT = 2.5V -2.0 -3.0 -4.0 2.7 3.1 3.5 3.9 VOUT = 3.3V -40°C 2.7 3.1 3.5 3.9 4.3 4.7 5.1 5.5 4.3 4.7 5.1 5.5 Input Voltage (V) Input Voltage (V) 2550.2008.02.1.3 www.analogictech.com 7 PRODUCT DATASHEET AAT2550178 AAT2550178 SystemPowerTM Total Power Solution for Portable Applications Typical Characteristics — Step-Down Converter (continued) P-Channel RDS(ON) vs. Input Voltage 750 700 650 750 700 N-Channel RDS(ON) vs. Input Voltage RDS(ON)H (mΩ) RDS(ON)L (mΩ) 120°C 100°C 650 600 550 500 450 400 350 300 25°C 120°C 100°C 600 550 500 450 400 350 300 2.5 3.0 3.5 4.0 4.5 5.0 5.5 6.0 25°C 85°C 85°C 2.5 3.0 3.5 4.0 4.5 5.0 5.5 6.0 Input Voltage (V) Input Voltage (V) Load Transient Response (1mA to 300mA; VIN = 3.6V; VOUT = 1.8V; COUT = 10µF; CFF = 100pF) 2.0 1.9 1.90 1.85 Load Transient Response (300mA to 400mA; VIN = 3.6V; VOUT = 1.8V; COUT = 4.7µF) Load and Inductor Current (200mA/div) (bottom) Load and Inductor Current (100mA/div) (bottom) VO IO VO IO IL Output Voltage (top) (V) 1.7 300mA 1mA Output Voltage (top) (V) 1.8 1.80 1.75 400mA 300mA 0.4 0 IL Time (50µs/div) 0.3 0.2 0.1 Time (50µs/div) Load Transient Response (300mA to 400mA; VIN = 3.6V; VOUT = 1.8V; COUT = 10µF) 1.90 1.85 Load Transient Response (300mA to 400mA; VIN = 3.6V; VOUT = 1.8V; COUT = 10µF; CFF = 100pF) 1.850 1.825 Load and Inductor Current (100mA/div) (bottom) Load and Inductor Current (100mA/div) (bottom) VO IO VO IO 400mA 300mA 0.4 Output Voltage (top) (V) 1.75 Output Voltage (top) (V) 1.80 1.800 1.775 400mA 300mA 0.4 IL 0.3 0.2 0.1 IL 0.3 0.2 0.1 Time (50µs/div) Time (50µs/div) 8 www.analogictech.com 2550.2008.02.1.3 PRODUCT DATASHEET AAT2550178 AAT2550178 SystemPowerTM Total Power Solution for Portable Applications Typical Characteristics — Step-Down Converter (continued) Line Response (VOUT = 1.8V @ 400mA) Output Voltage (AC coupled) (top) (mV) 1.82 1.81 40 20 0 -20 0.15 0.10 Output Ripple (VIN = 3.6V; VOUT = 1.8V; IOUT = 1mA) VO Inductor Current (bottom) (A) Output Voltage (top) (V) Input Voltage (bottom) (V) 1.80 4.5 4.0 3.5 3.0 IL 0.05 0.00 -0.05 -0.10 Time (25µs/div) Time (10µs/div) Output Ripple (VIN = 3.6V; VOUT = 1.8V; IOUT = 400mA) Output Voltage (AC coupled) (top) (mV) 40 20 0 -20 0.6 0.5 0.4 0.3 VO Inductor Current (bottom) (A) IL 0.2 0.1 Time (500ns/div) 2550.2008.02.1.3 www.analogictech.com 9 PRODUCT DATASHEET AAT2550178 AAT2550178 SystemPowerTM Total Power Solution for Portable Applications Typical Characteristics — Battery Charger Constant Charging Current vs. RSET 10000 4.242 Battery Voltage vs. Supply Voltage 4.221 ICH (mA) 1000 VBAT (V) 100 10 1 10 100 4.200 4.179 4.158 4.5 4.75 5.0 5.25 5.5 RSET (kΩ) Supply Voltage (V) End of Charge Voltage Regulation vs. Temperature 4.242 Preconditioning Threshold Voltage vs. Temperature 3.05 3.04 4.221 3.03 3.02 VBAT_EOC (V) VMIN (V) 3.01 3.00 2.99 2.98 2.97 2.96 4.200 4.179 4.158 -50 2.95 -25 0 25 50 75 100 -50 -25 0 25 50 75 100 Temperature (°C) Temperature (°C) Preconditioning Current vs. Temperature (ADPSET = 8.06kΩ) 120 Constant Charging Current vs. Temperature (ADPSET = 8.06kΩ) 1100 1080 110 1060 1040 ICH (mA) -25 0 25 50 75 100 ITK (mA) 1020 1000 980 960 940 920 100 90 80 -50 900 -50 -25 0 25 50 75 100 Temperature (°C) Temperature (°C) 10 www.analogictech.com 2550.2008.02.1.3 PRODUCT DATASHEET AAT2550178 AAT2550178 SystemPowerTM Total Power Solution for Portable Applications Typical Characteristics — Battery Charger (continued) Charging Current vs. Battery Voltage (ADPSET = 8.06kΩ; VIN = 5.0V) 1.2 1.0 0.8 Constant Charging Current vs. Input Voltage (ADPSET = 8.06kΩ) 1200 VBAT = 3.3V 1000 800 ICH (mA) ICH (A) VBAT = 3.9V 600 400 200 0 0.6 0.4 0.2 0.0 2.5 2.9 3.3 3.7 4.1 4.5 VBAT = 3.5V 4.5 4.75 5.0 5.25 5.5 5.75 6.0 Battery Voltage (V) Input Voltage (V) VIH vs. Input Voltage EN Pin (Rising) 1.4 1.3 1.2 1.1 1.4 1.3 1.2 VIL vs. Input Voltage EN Pin (Falling) VIH (V) 0.9 0.8 0.7 0.6 0.5 0.4 4.2 4.4 4.6 4.8 5.0 5.2 5.4 5.6 5.8 6.0 VIH (V) 1.0 -40°C +25°C 1.1 1.0 0.9 0.8 0.7 -40°C +25°C +85°C 0.6 0.5 0.4 4.2 4.4 4.6 4.8 +85°C 5.0 5.2 5.4 5.6 5.8 6.0 Input Voltage (V) Input Voltage (V) Adapter Mode Supply Current vs. ADPSET Resistor 0.80 10 Counter Timeout vs. Temperature (CT = 0.1μF) Counter Timeout (%) 1000 0.70 0.60 8 6 4 2 0 -2 -4 -6 -8 IQ (mA) 0.50 0.40 0.30 0.20 0.10 0.00 1 10 Constant Current Pre-Conditioning 100 -10 -50 -25 0 25 50 75 100 ADPSET Resistor (kΩ) Temperature (°C) 2550.2008.02.1.3 www.analogictech.com 11 PRODUCT DATASHEET AAT2550178 AAT2550178 SystemPowerTM Total Power Solution for Portable Applications Typical Characteristics — Battery Charger (continued) CT Pin Capacitance vs. Counter Timeout 2.0 1.8 Temperature Sense Output Current vs. Temperature 88 Capacitance (μF) 1.6 1.4 1.2 1.0 0.8 0.6 0.4 0.2 0.0 0 2 4 6 8 10 TS Pin Current (μA) 86 84 82 80 78 76 74 72 -50 -25 0 25 50 75 100 Precondition Timeout Precondition + Constant Current Timeout or Constant Voltage Timeout Time (hours) Temperature (°C) 12 www.analogictech.com 2550.2008.02.1.3 PRODUCT DATASHEET AAT2550178 AAT2550178 SystemPowerTM Functional Block Diagram Total Power Solution for Portable Applications Reverse Blocking ADP ADPSET 4.2V Current Compare OTP UVLO BAT ENBAT STAT2 STAT1 CT FBA Err. Amp. Constant Current Charge Status Watchdog Timer Charge Control CV/PreCharge 80μA Window Comparator TS INA DH Voltage Reference Logic Control Logic LXA DL ENA PGND INB FBB Err. Amp. DH Voltage Reference Logic Control Logic LXB DL ENB PGND Functional Description The AAT2550 is a highly integrated power management IC comprised of a battery charger and two step-down voltage converters. The battery charger is designed for charging single-cell lithium-ion / polymer batteries. Featuring an integrated pass device and reverse blocking, it offers a constant current / constant voltage charge algorithm with a user-programmable charge current level. The two step-down converters have been designed to minimize external component size and maximize efficiency over the entire load range. Each converter has independent enable and input voltage pins and can provide 600mA of load current. Battery Charger The battery charger is designed to operate with standard AC adapter input sources, while requiring a minimum number of external components. It precisely regulates charge voltage and current for single-cell lithium-ion / polymer batteries. The adapter charge input constant current level may be programmed up to 1A for rapid charging applications. The battery charger features thermal loop charge reduction. In the event of operating ambient temperatures exceeding the power dissipation abilities of the device package for a given constant current charge level, the 2550.2008.02.1.3 www.analogictech.com 13 PRODUCT DATASHEET AAT2550178 SystemPowerTM Total Power Solution for Portable Applications Charging Operation As shown in Figure 1, there are three basic phases for the battery charge cycle: 1. Pre-conditioning / trickle charge 2. Constant current / fast charge 3. Constant voltage charge charge control will enter into thermal regulation. When the system thermal regulation becomes active, the programmed constant current charge amplitude will automatically decrease to a safe level for the present operating conditions. If the ambient temperature drops to a level sufficient to allow the device to come out of thermal regulation, then the system will automatically resume charging at the full programmed constant current level. This intelligent thermal management system permits the battery charger to operate and charge a battery cell safely over a wide range of ambient conditions, while maximizing the greatest possible charge current and minimizing the battery charge time for a given set of conditions. Status monitor output pins are provided to indicate the battery charge state by directly driving two external LEDs. A serial interface output is also available to report any one of 12 distinct charge states to the host system microcontroller / microprocessor. Battery temperature and charge state are fully monitored for fault conditions. In the event of an over-voltage or over-temperature condition, the device will automatically shut down, protecting the charging device, control system, and the battery under charge. In addition to internal charge controller thermal protection, the charger also offers a temperature sense feedback function (TS pin) from the battery to shut down the device in the event the battery exceeds its own thermal limit during charging. All fault events are reported to the user either by simple status LEDs or via the DATA pin function. Battery Preconditioning Before the start of charging, the charger checks several conditions in order to assure a safe charging environment. The input supply must be above the minimum operating voltage, or under-voltage lockout threshold (VUVLO), for the charging sequence to begin. Also, the battery temperature, as reported by a thermistor connected to the TS pin from the battery, must be within the proper window for safe charging. When these conditions have been met and a battery is connected to the BAT pin, the charger checks the state of the battery. If the battery voltage is below the preconditioning voltage threshold (VMIN), then the charge control begins preconditioning the battery. The preconditioning trickle charge current is equal to the fast charge constant current divided by 10. For example, if the programmed fast charge current is 1A, then the preconditioning mode (trickle charge) current will be 100mA. Battery preconditioning is a safety precaution for deeply discharged batteries and also helps to limit power dissipation in the pass transistor when the voltage across the device is at the greatest potential. Preconditioning Trickle Charge Phase Charge Complete Voltage Regulated Current Constant Current Charge Phase I = Max CC Constant Voltage Charge Phase Constant Current Mode Voltage Threshold Trickle Charge and Termination Threshold I = CC / 10 Figure 1: Typical Charge Profile. 14 www.analogictech.com 2550.2008.02.1.3 PRODUCT DATASHEET AAT2550178 SystemPowerTM Fast Charge/Constant Current Charging Total Power Solution for Portable Applications Input voltage range is 2.7V to 5.5V and each converter’s efficiency has been optimized for all load conditions, ranging from no load to 600mA. The internal error amplifier and compensation provides excellent transient response, load regulation, and line regulation. Soft start eliminates output voltage overshoot when the enable or the input voltage is applied. Battery preconditioning continues until the voltage on the BAT pin exceeds the preconditioning voltage threshold (VMIN). At this point, the charger begins the constant current fast charging phase. The fast charge constant current (ICH) amplitude is programmed by the user via the RSET resistor. The charger remains in the constant current charge mode until the battery reaches the voltage regulation threshold, VBAT_EOC. Soft Start / Enable The internal soft start limits the inrush current during start-up. This prevents possible sagging of the input voltage and eliminates output voltage overshoot. Typical start-up time for a 4.7μF output capacitor and load current of 600mA is 100μs. The AAT2550 offers independent enable pins for each converter. When connected to logic low, the enable input forces the respective step-down converter into a low-power, non-switching, shutdown state. The total input current during shutdown is less than 1μA for each channel. Constant Voltage Charging The system transitions to a constant voltage charging mode when the battery voltage reaches the output charge regulation threshold (VBAT_EOC) during the constant current fast charge phase. The regulation voltage level is factory programmed to 4.2V (±1%). The charge current in the constant voltage mode drops as the battery under charge reaches its maximum capacity. End of Charge Cycle Termination and Recharge Sequence When the charge current drops to 7.5% of the programmed fast charge current level in the constant voltage mode, the device terminates charging and goes into a sleep state. The charger will remain in a sleep state until the battery voltage decreases to a level below the battery recharge voltage threshold (VRCH). When the input supply is disconnected, the charger will automatically transition into a power-saving sleep mode. Consuming only an ultra-low 0.3μA in sleep mode, the charger minimizes battery drain when it is not charging. This feature is particularly useful in applications where the input supply level may fall below the battery charge or under-voltage lockout level. In such cases where the input voltage drops, the device will enter sleep mode and resume charging automatically once the input supply has recovered from the fault condition. Current Limit and Over-Temperature Protection For overload conditions, the peak input current is limited. To minimize power dissipation and stresses under current limit and short-circuit conditions, switching is terminated after entering current limit for a series of pulses. Switching is terminated for seven consecutive clock cycles after a current limit has been sensed for a series of four consecutive clock cycles. Thermal protection completely disables switching when internal dissipation becomes excessive. The junction over-temperature threshold is 140°C with 15°C of hysteresis. Once an over-temperature or over-current fault conditions is removed, the output voltage automatically recovers. Step-Down Converters The AAT2550 offers two high-performance, 600mA, 1.4MHz step-down converters. Both converters minimize external component size and optimize efficiency over the entire load range. Both converters can be programmed with external feedback resistors to any voltage ranging from 0.6V to the input voltage. At dropout, the converter duty cycle increases to 100% and the output voltage tracks the input voltage minus the RDS(ON) drop of the P-channel MOSFET. Under-Voltage Lockout The under-voltage lockout circuit prevents the device from improper operation at low input voltages. Internal bias of all circuits is controlled via the VIN input. Under-voltage lockout (UVLO) guarantees sufficient VIN bias and proper operation of all internal circuitry prior to activation. 2550.2008.02.1.3 www.analogictech.com 15 PRODUCT DATASHEET AAT2550178 AAT2550178 SystemPowerTM System Operation Flow Chart Total Power Solution for Portable Applications Yes No No Enable No Timing Yes Yes No No Expire Yes Yes No Set No Yes BAT_EOC No Yes TERM No 16 www.analogictech.com 2550.2008.02.1.3 PRODUCT DATASHEET AAT2550178 SystemPowerTM Application Information AC Adapter Power Charging Total Power Solution for Portable Applications drops below the UVLO threshold. When power is reapplied to the adapter pin or the UVLO condition recovers and ADP > VBAT, the system charge control will assess the state of charge on the battery cell and will automatically resume charging in the appropriate mode for the condition of the battery. ICH 100 200 300 400 500 600 700 800 900 1000 The adapter constant current charge levels can be programmed up to 1A. The AAT2550 will operate from the adapter input over a 4.0V to 5.5V range. The constant current fast charge current for the adapter input mode is set by the RSET resistor connected between the ADPSET and ground. Refer to Table 1 for recommended RSET values for a desired constant current charge level. The precise charging function in the adapter mode may be read from the DATA pin and/or status LEDs. Please refer to the Battery Charge Status Indication discussion in this datasheet for further details on data reporting. ADP RSET (kΩ) 84.5 43.2 28.0 21.0 16.9 13.3 11.5 10.2 9.09 8.06 Thermal Loop Control Due to the integrated nature of the linear charging control pass device, a special thermal loop control system has been employed to maximize charging current under all operation conditions. The thermal management system measures the internal circuit die temperature and reduces the fast charge current when the device exceeds a preset internal temperature control threshold. Once the thermal loop control becomes active, the fast charge current is initially reduced by a factor of 0.44. The initial thermal loop current can be estimated by the following equation: Table 1: Resistor Values. Enable / Disable The AAT2550 provides an enable function to control the charger IC on and off. The enable (ENBAT) pin is active high. When pulled to a logic low level, the AAT2550 will be shut down and forced into the sleep state. Charging will be halted regardless of the battery voltage or charging state. When the device is re-enabled, the charge control circuit will automatically reset and resume charging functions with the appropriate charging mode based on the battery charge state and measured cell voltage. ITLOOP = ICH · 0.44 The thermal loop control re-evaluates the circuit die temperature every three seconds and adjusts the fast charge current back up in small steps to the full fast charge current level or until an equilibrium current is discovered and maximized for the given ambient temperature condition. The thermal loop controls the system charge level; therefore, the AAT2550 will always provide the highest level of constant current possible in the fast charge mode for any given ambient temperature condition. Programming Charge Current The fast charge constant current charge level is programmed with a resistor placed between the ADPSET pin and ground. The accuracy of the fast charge, as well as the preconditioning trickle charge current, is dominated by the tolerance of the set resistor used. For this reason, 1% tolerance metal film resistors are recommended for the set resistor function. Fast charge constant current levels from 100mA to 1A can be set by selecting the appropriate resistor value from Table 1. The RSET resistor should be connected between the ADPSET pin and ground. Adapter Input Charge Inhibit and Resume The AAT2550 has an under-voltage lockout and power on reset feature so that the charger will suspend charging and shut down if the input supply to the adapter pin 2550.2008.02.1.3 www.analogictech.com 17 PRODUCT DATASHEET AAT2550178 SystemPowerTM 10000 Total Power Solution for Portable Applications timing capacitor should be physically located on the printed circuit board layout as closely as possible to the CT pin. Since the accuracy of the internal timer is dominated by the capacitance value, 10% tolerance or better ceramic capacitors are recommended. Ceramic capacitor materials, such as X7R and X5R type, are a good choice for this application. ICH (mA) 1000 ADP 100 Over-Voltage Protection 10 1 10 100 RSET (kΩ) Figure 2: Constant Charging Current vs. RSET. Protection Circuitry Programmable Watchdog Timer The AAT2550 contains a watchdog timing circuit for the adapter input charging mode. Typically, a 0.1μF ceramic capacitor is connected between the CT pin and ground. When a 0.1μF ceramic capacitor is used, the device will time a shutdown condition if the trickle charge mode exceeds 25 minutes and a combined trickle charge plus fast charge mode of three hours. When the device transitions to the constant voltage mode, the timing counter is reset and will time out after three hours and shut down the charger (see Table 2). Mode Trickle Charge (TC) Time Out Trickle Charge (TC) + Constant Current (CC) Mode Time Out Constant Voltage (VC) Mode Time Out An over-voltage event is defined as a condition where the voltage on the BAT pin exceeds the maximum battery charge voltage and is set by the over-voltage protection threshold (VOVP). If an over-voltage condition occurs, the AAT2550 charge control will shut down the device until voltage on the BAT pin drops below the overvoltage protection threshold (VOVP). The AAT2550 will resume normal charging operation after the over-voltage condition is removed. During an over-voltage event, the STAT LEDs will report a system fault, and the actual fault condition may be read via the DATA pin signal. Over-Temperature Shutdown The AAT2550 has a thermal protection control circuit which will shut down charging functions should the internal die temperature exceed the preset thermal limit threshold. Battery Temperature Fault Monitoring In the event of a battery over-temperature condition, the charge control will turn off the internal pass device and report a battery temperature fault on the DATA pin function. The STAT LEDs will also display a system fault. After the system recovers from a temperature fault, the device will resume charging operation. The AAT2550 checks battery temperature before starting the charge cycle, as well as during all stages of charging. This is accomplished by monitoring the voltage at the TS pin. This system is intended to use negative temperature coefficient thermistors (NTC), which are typically integrated into the battery package. Most of the commonly used NTC thermistors in battery packs are approximately 10kΩ at room temperature (25°C). The TS pin has been specifically designed to source 80μA of current to the thermistor. The voltage on the TS pin that results from the resistive load should stay within a window from 330mV to 2.3V. If the battery becomes too hot during charging due to an internal fault, the thermistor will heat up and reduce in value, pulling the TS pin voltage lower than the TS1 threshold, and the AAT2550 will signal the fault condition. Time 25 minutes 3 hours 3 hours Table 2: Summary for a 0.1μF Used for the Timing Capacitor. The CT pin is driven by a constant current source and will provide a linear response to increases in the timing capacitor value. Thus, if the timing capacitor were to be doubled from the nominal 0.1μF value, the time-out durations would be doubled. If the programmable watchdog timer function is not needed, it can be disabled by connecting the CT pin to ground. The CT pin should not be left floating or un-terminated, as this will cause errors in the internal timing control circuit. The constant current provided to charge the timing capacitor is very small, and this pin is susceptible to noise and changes in capacitance value. Therefore, the 18 www.analogictech.com 2550.2008.02.1.3 PRODUCT DATASHEET AAT2550178 SystemPowerTM Total Power Solution for Portable Applications Note: Red LED forward voltage (VF) is typically 2.0V @ 2mA. Green LED forward voltage (VF) is typically 3.2V @ 2mA. The four status LED display conditions are described in Table 3. Event Description Charge Disabled or Low Supply Charge Enabled Without Battery Battery Charging Charge Completed Fault If the use of the TS pin function is not required by the system, it should be terminated to ground with a 10kΩ resistor. Battery Charge Status Indication The AAT2550 indicates the status of the battery under charge with two different systems. First, the device has two status LED driver outputs. These two LEDs can indicate simple functions such as no battery charge activity, battery charging, charge complete, and charge fault. The AAT2550 also provides a bi-directional data reporting function so that a system microcontroller can interrogate the DATA pin and read any one of 13 system states. STAT1 Off Flash1 On Off On STAT2 Off Flash1 Off On On Table 3: Status LED Display Conditions. Status Indicator Display Simple system charging status states can be displayed using one or two LEDs in conjunction with the STAT1 and STAT2 pins on the AAT2550. These two pins are simple switches to connect the LED cathodes to ground. It is not necessary to use both display LEDs if a user simply wants to have a single lamp to show “charging” or “not charging.” This can be accomplished by using the STAT1 pin and a single LED. Using two LEDs and both STAT pins simply gives the user more information to the charging states. Refer to Table 3 for LED display definitions. The LED anodes should be connected to ADP. The LEDs should be biased with as little current as necessary to create reasonable illumination; therefore, a ballast resistor should be placed between the LED cathodes and the STAT1/2 pins. LED current consumption will add to the overall thermal power budget for the device package, so it is wise to keep the LED drive current to a minimum. 2mA should be sufficient to drive most low-cost green or red LEDs. It is not recommended to exceed 8mA for driving an individual status LED. The required ballast resistor value can be estimated using the following formulas: For connection to the adapter supply: Digital Charge Status Reporting The AAT2550 has a comprehensive digital data reporting system by use of the DATA pin feature. This function can provide detailed information regarding the status of the charging system. The DATA pin is a bi-directional port which will read back a series of data pulses when the system microcontroller asserts a request pulse. This single strobe request protocol will invoke one of 13 possible return pulse counts which the microcontroller can look up based on the serial report table shown in Table 4. Number 1 2 3 4 5 6 7 8 9 10 11 12 23 DATA Report Status Chip Over-Temperature Shutdown Battery Temperature Fault Over-Voltage Turn Off Not Used ADP Watchdog Time-Out in Battery Condition Mode ADP Battery Condition Mode ADP Watchdog Time-Out in Constant Current Mode ADP Thermal Loop Regulation in Constant Current Mode ADP Constant Current Mode ADP Watchdog Time-Out in Constant Voltage Mode ADP Constant Voltage Mode ADP End of Charging Data Report Error RB(STAT1/2) = Example: VADP - VF(LED) ILED(STAT1/2) Table 4: Serial Data Report Table. RB(STAT1) = 5.5V - 2.0V = 1.75kΩ 2mA 1. Flashing rate depends on output capacitance. 2550.2008.02.1.3 www.analogictech.com 19 PRODUCT DATASHEET AAT2550178 SystemPowerTM Total Power Solution for Portable Applications be calculated based on a recommended minimum pull-up current of 3mA. Use the following formula: The DATA pin function is active low and should normally be pulled high to VADP. This data line may also be pulled high to the same level as the high state for the logic I/O port on the system microcontroller. In order for the DATA pin control circuit to generate clean, sharp edges for the data output and to maintain the integrity of the data timing for the system, the pull-up resistor on the data line should be low enough in value so that the DATA signal returns to the high state without delay. If too small a pull-up resistor is used, the strobe pulse from the system microcontroller could exceed the maximum pulse time and the DATA output control could issue false status reports. A 1.5kΩ resistor is recommended when pulling the DATA pin high to 5.0V. If the data line is pulled high to a voltage level less than 5.0V, the pull-up resistor can RPULL-UP ≤ Data Timing VPULL-UP 3mA The system microcontroller should assert an active low data request pulse for minimum duration of 200ns; this is specified by the SQPULSE. Upon sensing the rising edge of the end of the data request pulse, the AAT2550 status data control will reply the data word back to the system microcontroller after a delay defined by the data report time specification TDATA(RPT). The period of the following group of data pulses will be defined by the TDATA specification. 1.8V to 5.0V IN RPULL_UP DATA Pin GPIO AAT2550 Status Control OUT IN OUT μP GPIO Port Figure 3: Data Pin Application Circuit. Timing Diagram SQ SQPULSE System Reset System Start PDATA CK TSYNC TLAT TOFF Data TDATA(RPT) = TSYNC + TLAT < 2.5 PDATA TOFF > 2 PDATA N=1 N=2 N=3 20 www.analogictech.com 2550.2008.02.1.3 PRODUCT DATASHEET AAT2550178 SystemPowerTM Capacitor Selection Input Capacitor Total Power Solution for Portable Applications can also be added to the external feedback with a 10μF output capacitor for improved transient response (see C10 and C11 in Figure 4). At dropout, the converter duty cycle increases to 100% and the output voltage tracks the input voltage minus the RDS(ON) drop of the P-channel high-side MOSFET. The input voltage range is 2.7V to 5.5V. The converter efficiency has been optimized for all load conditions, ranging from no load to 600mA. The internal error amplifier and compensation provides excellent transient response, load, and line regulation. Soft start eliminates any output voltage overshoot when the enable or the input voltage is applied. In general, it is good design practice to place a decoupling capacitor between the ADP pin and ground. An input capacitor in the range of 1μF to 22μF is recommended. If the source supply is unregulated, it may be necessary to increase the capacitance to keep the input voltage above the under-voltage lockout threshold during device enable and when battery charging is initiated. If the AAT2550 adapter input is to be used in a system with an external power supply source, such as a typical AC-to-DC wall adapter, then a CIN capacitor in the range of 10μF should be used. A larger input capacitor in this application will minimize switching or power bounce effects when the power supply is “hot plugged.” Control Loop Both step-down converters are peak current mode control converters. The current through the P-channel MOSFET (high side) is sensed for current loop control, as well as short-circuit and overload protection. A fixed slope compensation signal is added to the sensed current to maintain stability for duty cycles greater than 50%. The peak current mode loop appears as a voltage-programmed current source in parallel with the output capacitor. The output of the voltage error amplifier programs the current mode loop for the necessary peak switch current to force a constant output voltage for all load and line conditions. Internal loop compensation terminates the transconductance voltage error amplifier output. The error amplifier reference is fixed at 0.6V. Output Capacitor The AAT2550 only requires a 1μF ceramic capacitor on the BAT pin to maintain circuit stability. This value should be increased to 10μF or more if the battery connection is made any distance from the charger output. If the AAT2550 is to be used in applications where the battery can be removed from the charger, such as in the case of desktop charging cradles, an output capacitor greater than 10μF may be required to prevent the device from cycling on and off when no battery is present. Step-Down Converter Functional Description The AAT2550 has two step-down converters and both are designed with the goal of minimizing external component size and optimizing efficiency over the complete load range (600mA). Apart from the small bypass input capacitor, only a small L-C filter is required at the output. Typically, a 4.7μH inductor and a 4.7μF ceramic capacitor are recommended (see Table 5). Configuration 0.6V Adjustable With External Feedback Soft Start / Enable Soft start limits the current surge seen at the input and eliminates output voltage overshoot. When pulled low, the enable input forces the AAT2550 into a low-power, non-switching state. The total input current during shutdown is less than 1μA. Output Voltage 1V, 1.2V 1.5V, 1.8V 2.5V, 3.3V Inductor 2.2μH 4.7μH 6.8μH Current Limit and Over-Temperature Protection For overload conditions, the peak input current is limited. To minimize power dissipation and stresses under current limit and short-circuit conditions, switching is terminated after entering current limit for a series of pulses. Switching is terminated for seven consecutive clock cycles after a current limit has been sensed for a series of four consecutive clock cycles. Table 5: Inductor Values. The two step-down converters can be programmed with external feedback to any voltage, ranging from 0.6V to the input voltage. An additional feed-forward capacitor 2550.2008.02.1.3 www.analogictech.com 21 PRODUCT DATASHEET AAT2550178 SystemPowerTM Total Power Solution for Portable Applications tion characteristics. The inductor should not show any appreciable saturation under normal load conditions. Some inductors may meet the peak and average current ratings yet result in excessive losses due to a high DCR. Always consider the losses associated with the DCR and its effect on the total converter efficiency when selecting an inductor. The Sumida 4.7μH CDRH2D14 series inductor has a 135mΩ DCR and a 1A DC current rating. At full load, the inductor DC loss is 48.6mW, which gives a 4% loss in efficiency for a 600mA, 1.5V output. Thermal protection completely disables switching when internal dissipation becomes excessive. The junction over-temperature threshold is 140°C with 15°C of hysteresis. Once an over-temperature or over-current fault conditions is removed, the output voltage automatically recovers. Under-Voltage Lockout Internal bias of all circuits is controlled via the VIN input. Under-voltage lockout (UVLO) guarantees sufficient VIN bias and proper operation of all internal circuitry prior to activation. Input Capacitor Select a 4.7μF to 10μF X7R or X5R ceramic capacitor for the input. To estimate the required input capacitor size, determine the acceptable input ripple level (VPP) and solve for C. The calculated value varies with input voltage and is a maximum when VIN is double the output voltage. Step-Down Converter Applications Information Inductor Selection The step-down converter uses peak current mode control with slope compensation to maintain stability for duty cycles greater than 50%. The output inductor value must be selected so the inductor current down slope meets the internal slope compensation requirements. The internal slope compensation for the AAT2550 is 0.24A/μs. This equates to a slope compensation that is 75% of the inductor current down slope for a 1.5V output and 4.7μH inductor. CIN = V⎞ VO ⎛ · 1- O VIN ⎝ VIN ⎠ ⎛ VPP ⎞ - ESR · FS ⎝ IO ⎠ VO ⎛ V⎞ 1 · 1 - O = for VIN = 2 · VO VIN ⎝ VIN ⎠ 4 CIN(MIN) = 1 ⎛ VPP ⎞ - ESR · 4 · FS ⎝ IO ⎠ m= 0.75 ⋅ VO 0.75 ⋅ 1.5V A = = 0.24 L 4.7μH μsec This is the internal slope compensation for the stepdown converter. When externally programming the 0.6V version to 2.5V, the calculated inductance is 7.5μH. L= 0.75 ⋅ VO = m μsec 0.75 ⋅ VO ≈ 3 A ⋅ VO A 0.24A μsec Always examine the ceramic capacitor DC voltage coefficient characteristics when selecting the proper value. For example, the capacitance of a 10μF, 6.3V, X5R ceramic capacitor with 5.0V DC applied is actually about 6μF. The maximum input capacitor RMS current is: =3 μsec ⋅ 2.5V = 7.5μH A IRMS = IO · VO ⎛ V⎞ · 1- O VIN ⎝ VIN ⎠ In this case, a standard 6.8μH value is selected. For high-voltage output (≥2.5V), m = 0.48A/μs. Table 5 displays inductor values for the AAT2550 step-down converters. Manufacturer's specifications list both the inductor DC current rating, which is a thermal limitation, and the peak current rating, which is determined by the saturaThe input capacitor RMS ripple current varies with the input and output voltage and will always be less than or equal to half of the total DC load current. VO ⎛ V⎞ · 1- O = VIN ⎝ VIN ⎠ D · (1 - D) = 0.52 = 1 2 22 www.analogictech.com 2550.2008.02.1.3 PRODUCT DATASHEET AAT2550178 SystemPowerTM for VIN = 2 · VO Total Power Solution for Portable Applications The output voltage droop due to a load transient is dominated by the capacitance of the ceramic output capacitor. During a step increase in load current, the ceramic output capacitor alone supplies the load current until the loop responds. Within two or three switching cycles, the loop responds and the inductor current increases to match the load current demand. The relationship of the output voltage droop during the three switching cycles to the output capacitance can be estimated by: IRMS(MAX) = VO ⎛ V⎞ · 1- O IO 2 The term VIN ⎝ VIN ⎠ appears in both the input voltage ripple and input capacitor RMS current equations and is a maximum when VO is twice VIN. This is why the input voltage ripple and the input capacitor RMS current ripple are a maximum at 50% duty cycle. The input capacitor provides a low impedance loop for the edges of pulsed current drawn by the AAT2550. Low ESR/ESL X7R and X5R ceramic capacitors are ideal for this function. To minimize stray inductance, the capacitor should be placed as closely as possible to the IC. This keeps the high frequency content of the input current localized, minimizing EMI and input voltage ripple. Proper placement of the input capacitors (C4 and C5) can be seen in the evaluation board schematic in Figure 4. A laboratory test set-up typically consists of two long wires running from the bench power supply to the evaluation board input voltage pins. The inductance of these wires, along with the low-ESR ceramic input capacitor, can create a high Q network that may affect converter performance. This problem often becomes apparent in the form of excessive ringing in the output voltage during load transients. Errors in the loop phase and gain measurements can also result. Since the inductance of a short PCB trace feeding the input voltage is significantly lower than the power leads from the bench power supply, most applications do not exhibit this problem. In applications where the input power source lead inductance cannot be reduced to a level that does not affect the converter performance, a high ESR tantalum or aluminum electrolytic input capacitor should be placed in parallel with the low ESR bypass ceramic input capacitor (C6 of Figure 4). This dampens the high Q network and stabilizes the system. COUT = 3 · ΔILOAD VDROOP · FS Once the average inductor current increases to the DC load level, the output voltage recovers. The above equation establishes a limit on the minimum value for the output capacitor with respect to load transients. The internal voltage loop compensation also limits the minimum output capacitor value to 4.7μF. This is due to its effect on the loop crossover frequency (bandwidth), phase margin, and gain margin. Increased output capacitance will reduce the crossover frequency with greater phase margin. The maximum output capacitor RMS ripple current is given by: IRMS(MAX) = VOUT · (VIN(MAX) - VOUT) L · FS · VIN(MAX) 2· 3 · 1 Dissipation due to the RMS current in the ceramic output capacitor ESR is typically minimal, resulting in less than a few degrees rise in hot-spot temperature. Feedback Resistor Selection Table 6 shows all output voltages, which can be externally programmed. Resistors R7 through R10 of Figure 4 program the output to regulate at a voltage higher than 0.6V. To limit the bias current required for the external feedback resistor string while maintaining good noise immunity, the minimum suggested value for R7 and R9 is 59kΩ. Although a larger value will further reduce quiescent current, it will also increase the impedance of the feedback node, making it more sensitive to external noise and interference. Table 6 summarizes the resistor values for various output voltages with R7 and R9 set to either 59kΩ for good noise immunity or 221kΩ for reduced no load input current. Output Capacitor The output capacitor limits the output ripple and provides holdup during large load transitions. A 4.7μF to 10μF X5R or X7R ceramic capacitor typically provides sufficient bulk capacitance to stabilize the output during large load transitions and has the ESR and ESL characteristics necessary for low output ripple. 2550.2008.02.1.3 www.analogictech.com 23 PRODUCT DATASHEET AAT2550178 SystemPowerTM VOUT (V) 0.8 0.9 1.0 1.1 1.2 1.3 1.4 1.5 1.8 1.85 2.0 2.5 3.3 Total Power Solution for Portable Applications R7, R9 = 221kΩ R8, R10 (kΩ) 75 113 150 187 221 261 301 332 442 464 523 715 1000 R7, R9 = 59kΩ R8, R10 (kΩ) 19.6 29.4 39.2 49.9 59.0 68.1 78.7 88.7 118 124 137 187 267 PSD is the total loss associated with both step-down converters and PC is the loss associated with the charger. The total losses will vary considerably depending on input voltage, load, and charging current. While charging a battery, the current capability of the step-down converters is limited. Step-Down Converter Losses There are three types of losses are associated with the AAT2550 step-down converter: switching losses (tSW · FS), conduction losses (I2 · RDS(ON)), and quiescent current losses (IQ · VIN). At full load, assuming continuous conduction mode, a simplified form of the step-down converter losses is: IOA2 · (RDS(ON)H · VOA + RDS(ON)L · (VIN - VOA)) + IOB2 · (RDS(ON)H · VOB + RDS(ON)L · (VIN - VOB)) VIN Table 6: Adjustable Resistor Values for Use With 0.6V Step-Down Converter. The AAT2550, combined with an external feedforward capacitor (C10 and C11 in Figure 4), delivers enhanced transient response for extreme pulsed load applications. The addition of the feedforward capacitor (100pF) typically requires a larger output capacitor for stability. PSD = + (tSW · FS · (IOA + IOB) + 2 · IQ ) · VIN For the condition where one channel is in dropout at 100% duty cycle (IOA), the step-down converter dissipation is: ⎛ VOUT ⎞ ⎛ 1.5V ⎞ R8 = V -1 · R7 = 0.6V - 1 · 59kΩ = 88.5kΩ ⎝ REF ⎠ ⎝ ⎠ PSD = IOA2 · RDS(ON)H + Thermal Considerations The AAT2550 is available in a 4x4mm QFN package, which has a typical thermal resistance of 50°C/W when the exposed paddle is soldered to a printed circuit board (PCB) in the manner discussed in the Printed Circuit Board Layout section of this datasheet. Thermal resistance will vary with the PCB area, ground plane area, size and number of other adjacent components, and the heat they generate. The maximum ambient operating temperature is limited by either the design derating criteria, the over-temperature shutdown temperature, or the thermal loop charge current reduction control. To calculate the junction temperature, sum the step-down converter losses with the battery charger losses. Multiply the total losses by the package thermal resistance and add to the ambient temperature to determine the junction temperature rise. IOB2 · (RDS(ON)H · VOB + RDS(ON)L · (VIN - VOB)) VIN + (tSW · FS · IOB + 2 · IQ ) · VIN PSD VIN RDS(ON)H RDS(ON)L VOA VOB IOA IOB IQ tSW FS = Step-Down Converter Dissipation = Converter Input Voltage = High Side MOSFET On Resistance = Low Side MOSFET On Resistance = Converter A Output Voltage = Converter B Output Voltage = Converter A Load Current = Converter B Load Current = Converter Quiescent Current = Switching Time Estimate = Converter Switching Frequency Always use the RDS(ON) and quiescent current value that corresponds to the applied input voltage. TJ(MAX) = (PSD + PC) · θJA + TAMB 24 www.analogictech.com 2550.2008.02.1.3 PRODUCT DATASHEET AAT2550178 SystemPowerTM Battery Charger Losses The maximum battery charger loss is: Total Power Solution for Portable Applications junction temperature to 110°C and avoids the thermal loop charge reduction at a 70°C ambient temperature. Conditions: PC = (VADP - VMIN) · ICH + VADP · IQC PC VADP VMIN ICH IQC = = = = = Total Charger Dissipation Adapter Voltage Preconditioning Voltage Threshold Programmed Charge Current Charger Quiescent Current Consumed by the Charger VOA VOB IQ VIN = VADP VMIN ICH IOP 2.5V @ 400mA 1.8V @ 400mA 70μA 5.0V 3.0V 0.6A 0.75mA Step-Down Converter A Step-Down Converter B Converter Quiescent Current Charger and Step-Down Battery Preconditioning Threshold Voltage Battery Charge Current Charger Operating Current For an application where no load is applied to the stepdown converters and the charger current is set to 1A with VADP = 5.0V, the maximum charger dissipation occurs at the preconditioning voltage threshold VMIN. PC = (VADP - VMIN) · ICH + VADP · IQC = (5.0V - 3.0V) · 1A + 5.0V · 0.75mA = 2W The charger thermal loop begins reducing the charge current at a 110°C junction temperature (TLOOP_IN). The ambient temperature at which the charger thermal loop begins reducing the charge current is: The step-down converter load current capability is greatest when the battery charger is disabled. The following example demonstrates the junction temperature rise for conditions where the battery charger is disabled and full load is applied to both converter outputs at the nominal battery input voltage. IOA2 · (RDS(ON)H · VOA + RDS(ON)L · (VIN - VOA)) + IOB2 · (RDS(ON)H · VOB + RDS(ON)L · (VIN - VOB)) VIN PTOTAL = + (tSW · FS · (IOA + IOB) + 2 · IQ) · VIN + (VADP - VMIN) · ICH + VADP · IOP = 0.4A2 · (0.475Ω · 2.5V + 0.45Ω · (5.0V - 2.5V)) + 0.4A2 · (0.475Ω · 1.8V + 0.45Ω · (5.0V - 1.8V)) 5.0V + 2 · (5ns · 1.4MHz · 0.4A + 70µA) · 5.0V + (5.0V - 3.0V) · 0.6A + 5.0V · 0.75mA = 1.38W TJ(MAX) = TAMB + (θJA · PLOSS) = 70°C + (50°C/W · 1.38W) TA = TLOOP_IN - θJA · PC = 110°C - (50°C/W · 2W) = 10°C Therefore, under the given conditions, the AAT2550 battery charger will enter the thermal loop charge current reduction at an ambient temperature greater than 10°C. = 139°C Conditions: VOA VOB IQ VIN ICH = IOP 2.5V @ 600mA 1.8V @ 600mA 70μA 3.6V 0A Step-Down Converter A Step-Down Converter B Converter Quiescent Current Charger and Step-Down Converter Input Voltage Charger Disabled Total Power Loss Examples The most likely high power scenario is when the charger and step-down converter are both operational and powered from the adapter. To examine the step-down converter maximum current capability for this condition, it is necessary to determine the step-down converter MOSFET RDS(ON), quiescent current, and switching losses at the adapter voltage level (5V). This example shows that with a 600mA battery charge current, the buck converter output current capability is limited 400mA. This limits the PTOTAL = IOA2 · (RDS(ON)H · VOA + RDS(ON)L · (VIN - VOA)) + IOB2 · (RDS(ON)H · VOB + RDS(ON)L · (VIN - VOB)) VIN + (tSW · FS · (IOA + IOB) + 2 · IQ) · VIN + (VADP - VMIN) · ICH + VADP · IOP = 0.6A2 · (0.58Ω · 2.5V + 0.56Ω · (3.6V - 2.5V)) + 0.2A2 · (0.58Ω · 1.8V + 0.56Ω · (3.6V - 1.8V)) 3.6V + 2 · (5ns · 1.4MHz · 0.4A + 70µA) · 3.6V = 0.443W TJ(MAX) = TAMB + (θJA · PLOSS) = 85°C + (50°C/W · 0.443W) = 107.15°C 2550.2008.02.1.3 www.analogictech.com 25 PRODUCT DATASHEET AAT2550178 SystemPowerTM Printed Circuit Board Layout Total Power Solution for Portable Applications 4. The resistance of the trace from the load return to GND should be kept to a minimum. This minimizes any error in DC regulation due to differences in the potential of the internal signal ground and the power ground. For good thermal coupling, vias are required from the pad for the QFN paddle to the ground plane. Via diameters should be 0.3mm to 0.33mm and positioned on a 1.2mm grid. Avoid close placement to other heat generating devices. Minimize the trace impedance from the battery to the BAT pin. The charger output is not remotely sensed, so any drop in the output across the BAT output trace feeding the battery will add to the error in the EOC battery voltage. To minimize voltage drops on the PCB, maintain an adequate high current carrying trace width. Use the following guidelines to ensure a proper printed circuit board layout. 1. Step-down converter bypass capacitors (C4 and C5 in Figure 4) must be placed as close as possible to the step-down converter inputs. The connections from the LXA and LXB pins of the step-down converters to the output inductors should be kept as short as possible. This is a switching node, so minimizing the length will reduce the potential of this noisy trace interfering with other high impedance noise sensitive nodes. The feedback trace should be separate from any power trace and connected as closely as possible to the load point. Sensing along a high current load trace will degrade the DC load regulation. If external feedback resistors are used, they should be placed as closely as possible to the FB pins and AGND. This prevents noise from being coupled into the high impedance feedback node. 5. 2. 6. 3. 26 www.analogictech.com 2550.2008.02.1.3 PRODUCT DATASHEET AAT2550178 AAT2550178 SystemPowerTM VIN C6 120μF (opt) GND C4 10μF EnVoA 1 2 3 Total Power Solution for Portable Applications GND GND EnVoB C5 10μF 3 2 1 R9 59k R7 59k AGND FBA VINA FBB VINB ENB R10 118k C10 100pF (opt.) 24 23 22 21 20 19 LX B C11 100pF (opt) 18 17 16 15 14 13 R8 187k VoB C9 4.7μF CT C12 0.1μF R1 1.5k LX A VoA C8 4.7μF L2 4.7μH 1 2 3 4 5 6 L1 6.8μH ENA LXA PGND DATA N/C ADPSET AGND AGND N/C AD BA U1 AAT2550 LXB PGND CT STAT1 STAT2 TS ENBA Data SW1 Data Strobe C14 (open) R6 8.06k 7 R4 10k R2 1.5k D1 STAT1 Red 8 9 10 11 12 R3 1k D2 STAT2 Green 1 ADP GND C13 10μF C3 10μF 1 2 3 2 Adapter BAT GND TS 1 2 3 Charger Enable Battery VoA, VoB (V) 1.0 1.2 1.5 1.8 2.5 3.0 3.3 R8, R10 (Ω) 9.2k 59k 88.7k 118k 187k 237k 267k L1, L2 2.2μH 2.2μH 4.7μH 4.7μH 6.8μH 6.8μH 6.8μH (CDRH2D14; (CDRH2D14; (CDRH2D14; (CDRH2D14; (CDRH2D14; (CDRH2D14; (CDRH2D14; DCR DCR DCR DCR DCR DCR DCR 75mΩ; 1200mA @ 20°C) 75mΩ; 1200mA @ 20°C) 135mΩ; 1000mA @ 20°C) 135mΩ; 1000mA @ 20°C) 170mΩ; 850mA @ 20°C) 170mΩ; 850mA @ 20°C) 170mΩ; 850mA @ 20°C) VoA VoB Figure 4: AAT2550 Evaluation Board Schematic. 2550.2008.02.1.3 www.analogictech.com 27 PRODUCT DATASHEET AAT2550178 AAT2550178 SystemPowerTM Total Power Solution for Portable Applications Figure 5: AAT2550 Evaluation Board Top Side Layout. Figure 6: AAT2550 Evaluation Board Layer 2 Layout. Figure 7: AAT2550 Evaluation Board Layer 3 Layout. Figure 8: AAT2550 Evaluation Board Bottom Side Layout. 28 www.analogictech.com 2550.2008.02.1.3 PRODUCT DATASHEET AAT2550178 AAT2550178 Part Number SystemPowerTM Qty. 1 1 3 2 1 1 2 2 2 1 1 2 1 1 1 1 1 1 1 Total Power Solution for Portable Applications Description Reference Designator Adapter Input Battery Output C3, C4, C5, C13 C8,C9 C12 C6 C10, C11 L1, L2 R1,R2 R3 R6 R7,R9 R10 R8 R4 D1 D2 SW1 U1 Manufacturer Phoenix Contact Phoenix Contact Murata Murata Vishay Vishay Vishay Sumida Vishay Vishay Vishay Vishay Vishay Vishay Vishay Chicago Miniature Lamp Chicago Miniature Lamp ITT Industries/C&K Div Advanced Analogic Technologies Conn. Term Block 2.54mm 2 POS Conn. Term Block 2.54mm 3 POS Ceramic Capacitor 10μF 10%, 10V, X5R, 0805 Ceramic Capacitor 4.7μF 10%, 6.3V, X5R, 0805 Ceramic Capacitor 0.1μF 25V 10% X5R 0603 Tantalum Capacitor 100μF, 6.3V, Case C Optional Ceramic Capacitor 100pF, 0402, COG Ferrite Shielded Inductor CDRH2D14 1.5k, 5%, 1/16W, 0402 1.0k, 5%, 1/16W, 0402 8.06k, 1%, 1/16W, 0402 59.0k, 1%, 1/16W, 0402 118k, 1%, 1/16W, 0402 187k, 1%, 1/16W, 0402 10k, 5%, 1/16W, 0402 Red LED, 1206 Green LED, 1206 Switch Tact 6mm SPST H = 5.0mm AAT2550 Total Power Solution for Portable Applications CMD15-21SRC/TR8 CMD15-21SRC/TR8 CKN9012-ND AAT2550ISK-CAA-T1 Table 7: AAT2550 Evaluation Board Bill of Materials. Inductance (μH) 2.2 4.7 6.8 4.7 4.7 6.8 4.7 Manufacturer Sumida Sumida Sumida Coilcraft Coiltronics Coiltronics Coiltronics Part Number CDRH2D14-2R2 CDRH2D14-4R7 CDRH2D14-6R8 LPO3310-472 SD3118-4R7 SD3118-6R8 SDRC10-4R7 Max DC Current (A) 1.20 1.00 0.85 0.80 0.98 0.82 1.30 DCR (Ω) 0.075 0.135 0.170 0.27 0.122 0.175 0.122 Size (mm) LxWxH 3.2x3.2x1.55 3.2x3.2x1.55 3.2x3.2x1.55 3.2x3.2x1.0 3.1x3.1x1.85 3.1x3.1x1.85 5.7x4.4x1.0 Type Shielded Shielded Shielded 1mm Shielded Shielded 1mm Shielded Table 8: Typical Surface Mount Inductors. Manufacturer Murata Murata Murata Part Number GRM219R61A475KE19 GRM21BR60J106KE19 GRM21BR60J226ME39 Value 4.7μF 10μF 22μF Voltage 10V 6.3V 6.3V Temp. Co. X5R X5R X5R Case 0805 0805 0805 Table 9: Surface Mount Capacitors. 2550.2008.02.1.3 www.analogictech.com 29 PRODUCT DATASHEET AAT2550178 AAT2550178 L1, L2 (μH) 2.2 2.2 2.2 2.2 2.2 2.2 4.7 4.7 4.7 4.7 6.8 6.8 6.8 SystemPowerTM Adjustable Version (0.6V device) VOUT (V) 0.8 0.9 1.0 1.1 1.2 1.3 1.4 1.5 1.8 1.85 2.0 2.5 3.3 Total Power Solution for Portable Applications R7, R9 = 59kΩ R8, R10 (kΩ) 19.6 29.4 39.2 49.9 59.0 68.1 78.7 88.7 118 124 137 187 267 R7, R9 = 221kΩ1 R8, R10 (kΩ) 75.0 113 150 187 221 261 301 332 442 464 523 715 1000 Table 10: Evaluation Board Component Values. 1. For reduced quiescent current, R7 and R9 = 221kΩ. 30 www.analogictech.com 2550.2008.02.1.3 PRODUCT DATASHEET AAT2550178 AAT2550178 SystemPowerTM Total Power Solution for Portable Applications Step-Down Converter Design Example Specifications VOA = 2.5V @ 400mA (VFBA = 0.6V), pulsed load ΔILOAD = 300mA VOB = 1.8V @ 400mA (VFBB = 0.6V), pulsed load ΔILOAD = 300mA VIN = 2.7V to 4.2V (3.6V nominal) FS = 1.4MHz TAMB = 85°C 2.5V VOA Output Inductor L1 = 3 μsec μsec ⋅ VO1 = 3 ⋅ 2.5V = 7.5μH (see Table 5) A A For Sumida inductor CDRH2D14, 6.8μH, DCR = 170mΩ. ΔIA = ⎛ ⎞ VO V⎞ 2.5V 2.5V ⎛ ⋅ 1 - OA = ⋅ 1⎠ = 106mA L1 ⋅ FS ⎝ VIN ⎠ 6.8μH ⋅ 1.4MHz ⎝ 4.2V IPKA = IOA + ΔIA = 0.4A + 0.053A = 0.453A 2 PLA = IOA2 ⋅ DCR = 0.452 ⋅ 170mΩ = 34mW 1.8V VOB Output Inductor L2 = 3 μsec μsec ⋅ VO2 = 3 ⋅ 1.8V = 5.4μH (see Table 5) A A For Sumida inductor CDRH2D14, 4.7μH, DCR = 135mΩ. ΔIB = ⎛ 1.8V ⎞ VOB ⎛ VOB ⎞ 1.8V ⋅ 1= ⋅ 1= 156mA L ⋅ FS ⎝ VIN ⎠ 4.7μH ⋅ 1.4MHz ⎝ 4.2V⎠ IPKB = IOB + ΔIB = 0.4A + 0.078A = 0.48A 2 PLB = IOB2 ⋅ DCR = 0.4A2 ⋅ 135mΩ = 21.6mW 2550.2008.02.1.3 www.analogictech.com 31 PRODUCT DATASHEET AAT2550178 AAT2550178 SystemPowerTM 2.5V Output Capacitor COUT = 3 · ΔILOAD 3 · 0.3A = = 3.2μF 0.2V · 1.4MHz VDROOP · FS Total Power Solution for Portable Applications IRMS(MAX) = (VOUT) · (VIN(MAX) - VOUT) 1 2.5V · (4.2V - 2.5V) · = 21mArms = L · FS · VIN(MAX) 2 · 3 10μH · 1.4MHz · 4.2V 2· 3 1 · Pesr = esr · IRMS2 = 5mΩ · (21mA)2 = 2.2μW 1.8V Output Capacitor COUT = 3 · ΔILOAD 3 · 0.3A = = 3.2μF VDROOP · FS 0.2V · 1.4MHz (VOUT) · (VIN(MAX) - VOUT) 1 1.8V · (4.2V - 1.8V) · = 45mArms = L · FS · VIN(MAX) 2 · 3 4.7μH · 1.4MHz · 4.2V 2· 3 1 · IRMS(MAX) = Pesr = esr · IRMS2 = 5mΩ · (45mA)2 = 10μW Input Capacitor Input Ripple VPP = 25mV. CIN = 1 ⎛ VPP ⎞ - ESR · 4 · FS ⎝ IO1 + IO2 ⎠ = 1 = 6.8μF ⎛ 25mV ⎞ - 5mΩ · 4 · 1.4MHz ⎝ 0.8A ⎠ IRMS(MAX) = IO1 + IO2 = 0.4Arms 2 P = esr · IRMS2 = 5mΩ · (0.4A)2 = 0.8mW 32 www.analogictech.com 2550.2008.02.1.3 PRODUCT DATASHEET AAT2550178 AAT2550178 SystemPowerTM Ordering Information Voltage Package QFN44-24 Converter 1 0.6V Converter 2 0.6V Total Power Solution for Portable Applications Marking1 RJXYY Part Number (Tape and Reel)2 AAT2550ISK-CAA-T1 All AnalogicTech products are offered in Pb-free packaging. The term “Pb-free” means semiconductor products that are in compliance with current RoHS standards, including the requirement that lead not exceed 0.1% by weight in homogeneous materials. For more information, please visit our website at http://www.analogictech.com/about/quality.aspx. Legend Voltage Adjustable (0.6V) 0.9 1.2 1.5 1.8 1.9 2.5 2.6 2.7 2.8 2.85 2.9 3.0 3.3 4.2 Code A B E G I Y N O P Q R S T W C 1. XYY = assembly and date code. 2. Sample stock is generally held on part numbers listed in BOLD. 2550.2008.02.1.3 www.analogictech.com 33 PRODUCT DATASHEET AAT2550178 AAT2550178 SystemPowerTM Package Information Total Power Solution for Portable Applications QFN44-24 0.305 ± 0.075 0.4 ± 0.05 19 18 24 1 Pin 1 Identification Pin 1 Dot By Marking 4.000 ± 0.050 0.5 BSC R0.030Max 13 12 7 6 4.000 ± 0.050 2.7 ± 0.05 Top View Bottom View 2.7 ± 0.05 0.214 ± 0.036 0.025 ± 0.025 Side View All dimensions in millimeters. 1. The leadless package family, which includes QFN, TQFN, DFN, TDFN and STDFN, has exposed copper (unplated) at the end of the lead terminals due to the manufacturing process. A solder fillet at the exposed copper edge cannot be guaranteed and is not required to ensure a proper bottom solder connection. Advanced Analogic Technologies, Inc. 3230 Scott Boulevard, Santa Clara, CA 95054 Phone (408) 737-4600 Fax (408) 737-4611 © Advanced Analogic Technologies, Inc. AnalogicTech cannot assume responsibility for use of any circuitry other than circuitry entirely embodied in an AnalogicTech product. No circuit patent licenses, copyrights, mask work rights, or other intellectual property rights are implied. AnalogicTech reserves the right to make changes to their products or specifications or to discontinue any product or service without notice. Except as provided in AnalogicTech’s terms and conditions of sale, AnalogicTech assumes no liability whatsoever, and AnalogicTech disclaims any express or implied warranty relating to the sale and/or use of AnalogicTech products including liability or warranties relating to fitness for a particular purpose, merchantability, or infringement of any patent, copyright or other intellectual property right. In order to minimize risks associated with the customer’s applications, adequate design and operating safeguards must be provided by the customer to minimize inherent or procedural hazards. Testing and other quality control techniques are utilized to the extent AnalogicTech deems necessary to support this warranty. Specific testing of all parameters of each device is not necessarily performed. AnalogicTech and the AnalogicTech logo are trademarks of Advanced Analogic Technologies Incorporated. All other brand and product names appearing in this document are registered trademarks or trademarks of their respective holders. 34 www.analogictech.com 0.900 ± 0.050 0.300 × 45° 2550.2008.02.1.3