AOZ1905DI

EZBoost 2A General Purpose Regulator AOZ1905 General Description The AOZ1905 EZBoost is a high-performance, currentmode, constant frequency step-up regulator with internal MOSFET. 600kHz/1.2MHz switching frequency allows the use of low-profile inductor and capacitors. The current-mode control ensures easy loop compensation and fast transient response. The AOZ1905 works from a 2.7V to 5.5V input voltage range and generates an output voltage as high as 24V. Other features include input under-voltage lockout, cycle-by-cycle current limit, thermal shutdown and soft-start. The AOZ1905 is available in a tiny 3mm x 3mm 10-pin DFN package and MSOP8 package and is rated over a -40°C to +85°C operating temperature range. Features ● ● ● ● ● ● ● ● 2.7V to 5.5V input voltage range Adjustable output up to 24V 600kHz/1.2MHz constant switching frequency Cycle-by-cycle current limit Thermal overload protection Programmable Soft-start Small 3mm x 3mm DFN 10L package MSOP-8L package Applications ● ● ● ● ● ● ● LCD TV LCD Monitors Notebook Displays PCMCIA Cards Hand-Held Devices GPS Power TV Tuner Typical Application L1 4.7µH D1 VOUT VIN C1 10µF IN FSEL SS C4 GND LX R2 FB R1 AOZ1905 C2 10µF OFF ON EN COMP R3 C3 Figure 1. Typical Application Circuit Rev. 1.5 December 2008 www.aosmd.com Page 1 of 16 AOZ1905 Ordering Information Part Number AOZ1905DI AOZ1905FI AOZ1905FIL Operating Temperature Range -40°C to +85°C -40°C to +85°C -40°C to +85°C Package 3x3 DFN-10 MSOP-8 MSOP-8 Environmental Green Product RoHS Compliant Green Product All AOS products are offered in packages with Pb-free plating and compliant to RoHS standards. Parts marked as Green Products (with “L” suffix) use reduced levels of Halogens, and are also RoHS compliant. Please visit www.aosmd.com/web/quality/rohs_compliant.jsp for additional information. Pin Configuration COMP COMP FB EN GND 1 2 3 4 8 7 6 5 1 2 3 4 5 10 9 8 7 6 SS FSEL IN LX LX SS FSEL IN LX FB EN GND GND MSOP-8 (Top View) DFN-10 (Top View) Pin Description Pin Number Pin Name COMP FB EN GND LX IN FSEL SS DFN-10 1 2 3 4, 5 6, 7 8 9 10 MSOP-8 1 2 3 4 5 6 7 8 Pin Function Compensation Pin. COMP is the output of the internal transconductance error amplifier. Connect a RC network from COMP to GND to compensate the loop. Feedback Input. Connect a resistive divider between the boost regulator output and ground with the center tap connected to FB to set output voltage. Enable Input. Pull EN high to enable the boost regulator and pull EN low to disable the regulator. System Ground. Boost Regulator Switching Node. Input Supply Pin. Frequency Select Pin. The switching frequency is 1.2MHz when FSEL is connected to IN, and 600kHz when FSEL is connected to ground. Soft-Start Pin. Connect a capacitor from SS to GND to set the soft-start period. Rev. 1.5 December 2008 www.aosmd.com Page 2 of 16 AOZ1905 Absolute Maximum Ratings Exceeding the Absolute Maximum ratings may damage the device. Recommend Operating Ratings Rating -0.3V to +6V -0.3V to +30V -0.3V to +6V -65°C to +150°C 2kV The device is not guaranteed to operate beyond the Maximum Operating Ratings. Parameter IN to GND LX to GND COMP, EN, FB, FSEL, SS to GND ESD Rating(1) Note: Parameter Supply Voltage (VIN) Output Voltage (VOUT) Ambient Temperature (TA) Package Thermal Resistance MSOP-8 (ΘJA) DFN-10 Rating 2.7V to 5.5V VIN to 24V -40°C to +85°C 150°C/W 48°C/W Storage Temperature (TS) 1. Devices are inherently ESD sensitive, handling precautions are required. Human body model rating: 1.5kΩ in series with 100pF. Functional Block Diagram 4.7µH VIN VOUT 10µF 10μF IN Bias Generator EN R Q S LX UVLO Comp OSC UVLO Threshold Thermal Shutdown FSEL OFF ON EN SS Soft-Start PWM Comp Error Amp Gm ILIM FB REF COMP Rev. 1.5 December 2008 www.aosmd.com Page 3 of 16 AOZ1905 Electrical Characteristics TA = 25°C, VIN = 3.3V, unless otherwise specified. Specifications in BOLD indicate an ambient temperature range of -40°C to +85°C. Symbol VIN VIN_UVLO IIN_ON IIN_OFF VFB Parameter IN Supply Voltage Range IN UVLO Threshold IN UVLO Hysteresis IN Quiescent Current IN Shutdowns Current FB Voltage FB Input Bias Current FB Line Regulation FB Load Regulation Conditions IN rising Min. 2.7 Typ. Max. 5.5 2.6 Units V V mV mA µA V µA %/V % 200 EN = IN, FB = 1.4V EN = GND 1.143 VIN = 2.7V 2.7V < VIN < 5.5V 0.2A < Iswitch < 1.8A, VOUT = 16V 7 0.15 1.5 10 200 340 FSEL = VIN FSEL = GND VIN = 2.7V FSEL = VIN FSEL = GND 960 480 1200 600 89 24 12 0.20 LX = 24V, EN = GND 2 2.7 145 35 1.5 0.4 0.85 x VIN 0.15 x VIN 0.1 1 0.25 2 3.5 1440 720 13 1.17 1 1 1.197 1 ISS gm AV OSCILLATOR fSW DMAX(2) DMIN (2) Soft-Start Charge Current Error Amplifier Transconductance Error Amplifier Voltage Gain Switching Frequency Maximum Duty Cycle Minimum Duty Cycle µA µS V/V kHz % % ERROR AMPLIFIER POWER SWITCH RON_LX PROTECTIONS ILIM TSD LOGIC INPUTS EN Logic High Threshold EN Logic Low Threshold FSEL High FSEL Low EN, FSEL Input Current Note: 2. Guaranteed by design. LX On Resistance LX Leakage Current Current Limit Thermal Shutdown Threshold Thermal Shutdown Hysteresis Ω µA A °C °C V V V V µA Rev. 1.5 December 2008 www.aosmd.com Page 4 of 16 AOZ1905 Typical Performance Characteristics Switching Waveform (IOUT = 400mA, fLX = 1.2MHz, L = 4.7μH) Switching Waveform (IOUT = 400mA, fLX = 600kHz, L = 10μH) LVX 5V/div LVX 5V/div IL 0.5A/div IL 0.5A/div 400ns/div 1μs/div Load Transient Response (IOUT = 40mA–400mA, fLX = 1.2MHz, L = 4.7μH) Load Transient Response (IOUT = 40mA–400mA, fLX = 600kHz, L = 10μH) Vo Ripple 200mV/div Vo Ripple 200mV/div Io 0.2A/div Io 0.2A/div 200μs/div 200μs/div Startup Waveform (ROUT = 200Ω, fLX = 1.2MHz, L = 4.7μH) Startup Waveform (ROUT = 200Ω, fLX = 600kHz, L = 4.7μH) VEN 2V/div Vo 5V/div Vo 5V/div IL 0.5A/div VEN 2V/div IL 0.5A/div 200μs/div 200μs/div Rev. 1.5 December 2008 www.aosmd.com Page 5 of 16 AOZ1905 Efficiency AOZ1905 Efficiency (VIN = 3.3V, VOUT = 12V) 100 95 90 85 Efficiency (%) Efficiency (%) AOZ1905 Efficiency (VIN = 5V, VOUT = 12V) 100 95 90 85 80 75 70 65 60 55 50 1 10 fSW=600kHz, L=10μH fSW=1.2MHz, L=4.7μH 80 75 70 65 60 55 fSW=600kHz, L=10μH fSW=1.2MHz, L=4.7μH 100 1,000 50 1 10 100 1,000 Load Current (mA) Load Current (mA) AOZ1905 Efficiency (VIN = 3.3V, VOUT = 8V) 100 95 90 85 Efficiency (%) 80 75 70 65 60 55 50 1 10 fSW=600kHz, L=10μH fSW=1.2MHz, L=4.7μH 100 1,000 Load Current (mA) Rev. 1.5 December 2008 www.aosmd.com Page 6 of 16 AOZ1905 Applications Information The AOZ1905 is a current-mode step up regulator (Boost Converter) with integrated NMOS switch. It operates from a 2.7V to 5.5V input voltage range and supplies up to 24V output voltage. The duty cycle can be adjusted to obtain a wide range of output voltage up to 24V. Features include enable control, cycle by cycle current limit, input under voltage lockout, adjustable soft-start and thermal shut down. The AOZ1905 is available in MSOP-8 and DFN-10 3x3 packages. Enable and Soft Start The AOZ1905 has the adjustable soft start feature to limit in-rush current and ensure the output voltage ramps up smoothly to regulation voltage. A soft start process begins when the input voltage rises to 2.6V and voltage on EN pin is HIGH. In soft start process, a 10µA internal current source charges the external capacitor at SS. As the SS capacitor is charged, the voltage at SS rises. The SS voltage clamps the reference voltage of the error amplifier, therefore output voltage rising time follows the SS pin voltage. With the slow ramping up output voltage, the inrush current can be prevented. The EN pin of the AOZ1905 is active high. Connect the EN pin to VIN if enable function is not used. Pulling EN to ground will disable the AOZ1905. Do not leave it open. The voltage on EN pin must be above 1.5 V to enable the AOZ1905. When voltage on EN pin falls below 0.4V, the AOZ1905 is disabled. If an application circuit requires the AOZ1905 to be disabled, an open drain or open collector circuit should be used to interface to EN pin. Steady-State Operation Under steady-state conditions, the converter operates in fixed frequency. The AOZ1905 integrates an internal N-MOSFET as the control switch. Inductor current is sensed by amplifying the voltage drop across the drain to source of the control power MOSFET. Output voltage is divided down by the external voltage divider at the FB pin. The difference of the FB pin voltage and reference is amplified by the internal transconductance error amplifier. The error voltage, which shows on the COMP pin, is compared against the current signal, which is sum of inductor current signal and ramp compensation signal, at PWM comparator input. If the current signal is less than the error voltage, the internal NMOS switch is on. The inductor current ramps up. When the current signal exceeds the error voltage, the switch is off. The inductor current is freewheeling through the Schottky diode to output. Switching Frequency The AOZ1905 switching frequency is fixed and set by an internal oscillator and FSEL. When the voltage of FSEL is high (connected to VIN) The switching frequency is 1.2MHz; when the voltage of FSEL is low (connected to GND), the switching frequency is 600kHz. Output Voltage Programming Output voltage can be set by feeding back the output to the FB pin with a resistor divider network. In the application circuit shown in Figure 1. The resistor divider network includes R1 and R2. Usually, a design is started by picking a fixed R1 value and calculating the required R2 with equation below. R 2⎞ ⎛ V O = 1.2 × ⎜ 1 + ------ ⎟ R 1⎠ ⎝ Some standard value of R1, R2 for most commonly used output voltage values are listed in Table 1. Table 1. VO (V) 8 12 16 18 25 R2 (kΩ) 170 270 370 420 595 R1 (kΩ) 30 30 30 30 30 The combination of R1 and R2 should be large enough to avoid drawing excessive current from the output, which will cause power loss. Protection Features The AOZ1905 has multiple protection features to prevent system circuit damage under abnormal conditions. Over Current Protection (OCP) The sensed inductor current signal is also used for over current protection. Since the AOZ1905 employs peak current mode control, the COMP pin voltage is proportional to the peak inductor current. The peak inductor current is automatically limited cycle by cycle. The cycle by cycle current limit threshold is set between 2A and 3A. When the current of control NMOS reaches the current limit threshold, the cycle by cycle current limit circuit turns off the NMOS immediately to terminate the current duty cycle. The inductor current stop rising. Rev. 1.5 December 2008 www.aosmd.com Page 7 of 16 AOZ1905 The cycle-by-cycle current limit protection directly limits inductor peak current. The average inductor current is also limited due to the limitation on peak inductor current. When cycle by cycle current limit circuit is triggered, the output voltage drops as the duty cycle decreasing. Power-On Reset (POR) A power-on reset circuit monitors the input voltage. When the input voltage exceeds 2.6V, the converter starts operation. When input voltage falls below 2.2V, the converter will stop switching. Thermal Protection An internal temperature sensor monitors the junction temperature. It shuts down the internal control circuit and NMOS switch if the junction temperature exceeds 145°C. High inductance gives low inductor ripple current but requires larger size inductor to avoid saturation. Low ripple current reduces inductor core losses. It also reduces RMS current through inductor, switch and freewheeling diode, which results in less conduction loss. Usually, peak to peak ripple current on the inductor is designed to be 30% to 50% of input current. When selecting the inductor, make sure it is able to handle the peak current without saturation even at the highest operating temperature. The inductor takes the highest current in a boost circuit. The conduction loss on inductor needs to be checked for thermal and efficiency requirements. Surface mount inductors in different shape and styles are available from Coilcraft, Elytone and Murata. Shielded inductors are small and radiate less EMI noise. But they cost more than unshielded inductors. The choice depends on EMI requirement, price and size. Output Capacitor The output capacitor is selected based on the DC output voltage rating, output ripple voltage specification and ripple current rating. The selected output capacitor must have a higher rated voltage specification than the maximum desired output voltage including ripple. De-rating needs to be considered for long term reliability. Output ripple voltage specification is another important factor for selecting the output capacitor. In a boost converter circuit, output ripple voltage is determined by load current, input voltage, output voltage, switching frequency, output capacitor value and ESR. It can be calculated by the equation below: Application Information The basic AOZ1905 application circuit is shown in Figure 1. Component selection is explained below. Input capacitor The input capacitor (C1 in Figure 1) must be connected to the VIN pin and GND pin of the AOZ1905 to maintain steady input voltage. The voltage rating of input capacitor must be greater than maximum input voltage + ripple voltage. The RMS current rating should be greater than the inductor ripple current: V IN⎞ V IN ⎛ Δ I L = ---------- × ⎜ 1 – -------- ⎟ f×L ⎝ VO ⎠ The input capacitor value should be greater than 4.7µF for normal operation. The capacitor can be electrolytic, tantalum or ceramic. The input capacitor should be placed as close as possible to the IC; if not possible, put a 0.1µF decoupling ceramics capacitor between IN pin and GND. Inductor The inductor is used to supply higher output voltage when the NMOS switch is off. For given input and output voltage, inductance and switching frequency together decide the inductor ripple current, which is, V IN ⎞ ⎞ ⎛ ⎛ ⎜ ⎜ 1 – --------------⎟ ⎟ V OUT⎠ ⎟ ⎜ VO ⎝ Δ V O = I LOAD × ⎜ -------- × ESR CO + ----------------------------- ⎟ f × CO ⎟ ⎜ V IN ⎜ ⎟ ⎝ ⎠ where; ILOAD is the load current, CO is the output capacitor value, and ESRCO is the Equivalent Series Resistor of output capacitor. V IN⎞ V IN ⎛ Δ I L = ---------- × ⎜ 1 – -------- ⎟ f×L ⎝ VO ⎠ The peak inductor current is: Δ IL I Lpeak = I IN + ------2 When low ESR ceramic capacitor is used as output capacitor, the impedance of the capacitor at the switching frequency dominates. Output ripple is mainly caused by capacitor value and load current with the fixed fre- Rev. 1.5 December 2008 www.aosmd.com Page 8 of 16 AOZ1905 quency, input and output voltage. The output ripple voltage calculation can be simplified to: The RHP zero can be calculated by: V IN ⎞ ⎛ ⎜ 1 – --------------⎟ V OUT⎠ ⎝ Δ V O = I L × ----------------------------f × CO Output capacitor with the range of 4.7µF to 22µF ceramic capacitor usually can meet most applications. Diode The output rectifier diode freewheels the inductor current to output when the internal MOSFET is off. To reduce losses due to diode forward voltage and reverse recovery, Schottky diode is preferred in AOZ1905. The reverse voltage of selected diode should be higher than output voltage, the average current rating should be higher than the maximum load current and the peak current rating should be greater than the peak current of inductor: V IN 2 f Z 2 = -----------------------------------------2 π × L × IO × VO The RHP zero obviously can cause the instable issue if the bandwidth is higher. It is recommended to design the bandwidth to lower than the one half frequency of RHP zero. The compensation design is actually to shape the converter close loop transfer function to get desired gain and phase. Several different types of compensation network can be used for AOZ1905. For most cases, a series capacitor and resistor network connected to the COMP pin sets the pole-zero and is adequate for a stable high-bandwidth control loop. In the AOZ1905, FB pin and COMP pin are the inverting input and the output of internal transconductance error amplifier. A series R and C compensation network connected to COMP provides one pole and one zero. The pole is: Δ IL I Lpeak = I IN + ------2 Loop Compensation The AOZ1905 employs peak current mode control for easy use and fast transient response. Peak current mode control eliminates the double pole effect of the output L&C filter. It greatly simplifies the compensation loop design. With peak current mode control, the boost power stage can be simplified to be a one-pole, one left plane zero and one right half plane (RHP) system in frequency domain. The pole is dominant pole and can be calculated by: G EA f P 2 = -----------------------------------------2 π × C C × G VEA where; GEA is the error amplifier transconductance, which is 200 x 10-6 A/V, GVEA is the error amplifier voltage gain, which is 340 V/V, and CC is compensation capacitor. The zero given by the external compensation network, capacitor CC (C3 in Figure 1) and resistor RC (R3 in Figure 1), is located at: 1 f P 1 = ---------------------------------2 π × CO × RL The zero is a ESR zero due to output capacitor and its ESR. It is can be calculated by: 1 f Z 2 = ----------------------------------2 π × CC × RC Choosing the suitable CC and RC by trading-off stability and bandwidth. 1 f Z 1 = -----------------------------------------------2 π × C O × ESR CO where; CO is the output filter capacitor, RL is load resistor value, and ESRCO is the equivalent series resistance of output capacitor. Thermal Management and Layout Consideration In the AOZ1905 boost regulator circuit, high pulsing current flows through two circuit loops. The first loop starts from the input capacitors, to the filter inductor, to the LX pin, to the internal NMOS switch, to the ground and back to the input capacitor, when the switch turns on. The second loop starts from input capacitor, to the filter inductor, to the LX pin to the external diode, to the ground and back to the input capacitor, when the switch is off. The RHP zero has the effect of a zero in the gain causing an imposed +20dB/decade on the roll off, but has the effect of a pole in the phase, subtracting 90° in the phase. Rev. 1.5 December 2008 www.aosmd.com Page 9 of 16 AOZ1905 In PCB layout, minimizing the two loops area reduces the noise of this circuit and improves efficiency. A ground plane is recommended to connect input capacitor, output capacitor, and GND pin of the AOZ1905. In the AOZ1905 boost regulator circuit, the three major power dissipating components are the AOZ1905 and output inductor. The total power dissipation of converter circuit can be measured by input power minus output power. The maximum junction temperature of AOZ1905 is 145°C, which limits the maximum load current capability. The thermal performance of the AOZ1905 is strongly affected by the PCB layout. Extra care should be taken by users during design process to ensure that the IC will operate under the recommended environmental conditions. Several layout tips are listed below for the best electric and thermal performance. Figure 2 below illustrates the PCB layout example as reference. 1. Do not use thermal relief connection to the VIN and the GND pin. Pour a maximized copper area to the GND pin and the VIN pin to help thermal dissipation. 2. A ground plane is preferred. 3. Make the current trace from LX pins to L to Co to the GND as short as possible. 4. Pour copper plane on all unused board area and connect it to stable DC nodes, like VIN, GND or VOUT. 5. Keep sensitive signal trace such as trace connected with FB pin and COMP pin far away from the LX pin. P total_loss = V IN × I IN – V O × I O The power dissipation of inductor can be approximately calculated by input current and DCR of inductor. P inductor_loss = I IN 2 × R inductor × 1.1 The power dissipation in the diode can be calculated as: P diode_loss = IO × ( 1 – D ) × V FW where; VFW is the forward voltage drop of the diode. The actual AOZ1905 junction temperature can be calculated with power dissipation in the AOZ1905 and thermal impedance from junction to ambient. T junction = ( P total_loss – P inductor_loss – P diode_loss ) × × Θ + T ambient R2 R2 L1 L1 (a) MSOP-8 Figure 3. AOZ1905 PCB Layout Example Rev. 1.5 December 2008 (a) DFN-10 3x3 www.aosmd.com Page 10 of 16 AOZ1905 Application Case for AOZ1905: Multiple-Output, Low-Profile TFT LCD Power Supply TFT-LCD (Thin Film Transistor Liquid Crystal Display) is a variant of liquid crystal display (LCD) which uses thin film transistor (TFT) technology to improve image quality. TFT LCD is one type of active matrix LCD, which is used in televisions, flat panel displays and projectors. For this application, it usually needs several output sources – Vo1 = 9V, Vo2 = -9V and Vo3 = 26V. Using one AOZ1905 can easily supply the whole power solution to obtain three outputs. The detailed schematic is shown in Figure 4. Figure 3. Multiple-Output, Low-Profile TFT LCD Power Solution Rev. 1.5 December 2008 www.aosmd.com Page 11 of 16 AOZ1905 Package Dimensions, MSOP-8, MSOP-8L Gauge Plane D L3 L1 L2 Seating Plane E E1 c A A2 A1 0.10mm e b Dimensions in millimeters RECOMMENDED LAND PATTERN Symbols A A1 A2 b c D E e E1 L1 L2 L3 θ 0.40 0.90 0° Min. — 0.05 0.81 0.25 0.13 2.95 2.95 Nom. — — 0.86 0.30 0.15 3.00 3.00 0.65 TYP. 4.90 TYP. 0.55 0.95 0.25 BSC — 0.70 1.00 6° Max. 1.10 0.15 0.91 0.40 0.25 3.05 3.05 Dimensions in inches Symbols A A1 A2 b c D E e E1 L1 L2 L3 θ Min. — 0.002 0.032 0.010 0.005 0.116 0.116 Nom. — — 0.034 0.012 0.006 0.118 0.118 Max. 0.043 0.006 0.036 0.016 0.010 0.120 0.120 0.75 4.35 0.65 0.026 TYP. 0.190 TYP. 0.016 0.035 0° 0.022 0.037 0.028 0.039 0.35 0.010 BSC — 6° Notes: 1. All dimensions are in millimeters. 2. Dimensions are inclusive of plating. 3. Package body sizes exclude mold flash and gate burrs. Mold flash at the non-lead sides should be less than 6 mils each. 4. Dimension L is measured in gauge plane. 5. Controlling dimension is millimeter, converted inch dimensions are not necessarily exact. Rev. 1.5 December 2008 www.aosmd.com Page 12 of 16 AOZ1905 Tape & Reel Dimensions, MSOP-8, MSOP-8L Carrier Tape Section B-B' K1 P1 P2 D0 D1 E1 E2 R0.3 Max B0 T K0 UNIT: mm K1 A0 4.2 3.4 P0 R0.3 Typ. E Feeding Direction Section B-B' Package MSOP-8 T 0.30 ±0.05 B0 3.30 ±0.10 A0 5.20 ±0.10 K1 1.20 ±0.10 K0 1.60 ±0.10 D1 D0 ø1.50 ø1.50 +0.1/-0.0 Min. E 12.0 ±0.3 E1 1.75 ±0.10 E2 5.50 ±0.05 P0 8.00 ±0.10 P1 4.00 ±0.05 P2 2.00 ±0.05 Reel W1 S G M V N K R H UNIT: mm Tape Size Reel Size M N W 12mm ø330 ø330.00 ø97.00 13.00 ±0.50 ±0.10 ±0.30 W1 17.40 ±1.00 W H K ø13.00 10.60 +0.50/-0.20 S 2.00 ±0.50 G — R — V — Leader/Trailer and Orientation Trailer Tape 300mm min. Components Tape Orientation in Pocket Leader Tape 500mm min. Notes: 1. 10 sprocket hole pich cumulative tolerance ±0.2. 2. Camber not to exceed 1mm in 100mm. 3. A0 and B0 measured on a plane 0.3mm above the bottom of the pocket. 4. K0 measured from a plane on the inside bottom of the pocket to the top surface of the carrier. 5. Pocket position relative to sprocket hole measured as tue position of pocket, not pocket hole. 6. All dimensions in mm. Rev. 1.5 December 2008 www.aosmd.com Page 13 of 16 AOZ1905 Package Dimensions, DFN 3x3 EP 10L 10x D 10 b R E 10 10 Pin #1 ID Option 1 E E1 L 1 D1 1 1 TOP VIEW BOTTOM VIEW R Pin #1 ID Option 2 A A1 Seating Plane c SIDE VIEW Dimensions in millimeters RECOMMENDED LAND PATTERN 0.50 0.25 Symbols A A1 b c D D1 E E1 e L R aaa bbb ccc ddd Min. 0.70 0.00 0.18 — Nom. 0.75 0.02 0.25 0.15 3.00 BSC 2.23 2.38 3.00 BSC 1.50 1.65 0.50 BSC 0.30 0.30 0.20 0.15 0.10 0.10 0.08 Max. 0.80 0.05 0.30 0.20 2.48 1.75 0.50 Dimensions in inches Symbols A A1 b c D D1 E E1 e L R aaa bbb ccc ddd Min. 0.028 0.000 0.007 — Nom. Max. 0.030 0.031 0.001 0.002 0.010 0.012 0.006 0.008 0.118 BSC 0.088 0.094 0.098 0.118 BSC 0.059 0.065 0.069 0.020 BSC 0.012 0.016 0.020 0.008 0.006 0.004 0.004 0.003 1.65 1.30 0.40 2.38 UNIT: mm 2.60 Notes: 1. Dimensions and tolerances conform to ASME Y14.5M-1994. 2. Controlling dimension is millimeter, converted inch dimensions are not necessarily exact. 3. Dimension b applied to metallized terminal and is measured between 0.15mm and 0.30mm from the terminal tip. If the terminal has the optional radius on the other end of the terminal, dimension b should not be measured in that radius area. 4. Coplanarity ddd applies to the terminals and all other bottom surface metallization. Rev. 1.5 December 2008 www.aosmd.com Page 14 of 16 AOZ1905 Tape and Reel Dimensions, DFN 3x3 EP 10L Tape P2 P1 D0 D1 E1 K0 E2 B0 E T P0 A0 Feeding Direction UNIT: mm Package DFN 3x3 EP A0 3.40 ±0.10 B0 3.35 ±0.10 K0 1.10 ±0.10 D0 D1 E E1 E2 3.50 ±0.05 P0 4.00 ±0.10 P1 4.00 ±0.10 P2 2.00 ±0.05 T 0.23 ±0.20 1.00 8.00 1.75 1.50 ±0.10 +0.25/-0.00 +0.30/-0.10 ±0.10 Reel W1 S R K M N H UNIT: mm Tape Size Reel Size M 8mm ø180 ø180.00 ±0.50 N 60.0 ±0.50 W1 8.4 +1.5/-0.0 H 13.0 ±0.20 S 1.5 Min. K 13.5 Min. R 3.0 ±0.50 Leader/Trailer and Orientation Trailer Tape 300mm min. Components Tape Orientation in Pocket Leader Tape 500mm min. Rev. 1.5 December 2008 www.aosmd.com Page 15 of 16 AOZ1905 Package Marking AOZ1905FI (MSOP-8) Part Number Code, Underscore Denotes Green Product No Option 1905I 0FA Y W LT Industrial Temperature Range Assembly Year & Week Assembly Lot Number Fab & Assembly Location AOZ1905DI (3x3 DFN-10) Industrial Temperature Range No Option 1905 I0AW LT Part Number Code, Underscore Denotes Green Product Week (Year code is embedded by using upper bar, upper dot, under bar, under dot on “W”) Assembly Location Assembly Lot Number Alpha & Omega Semiconductor reserves the right to make changes at any time without notice. LIFE SUPPORT POLICY ALPHA & OMEGA SEMICONDUCTOR PRODUCTS ARE NOT AUTHORIZED FOR USE AS CRITICAL COMPONENTS IN LIFE SUPPORT DEVICES OR SYSTEMS. As used herein: 1. Life support devices or systems are devices or systems which, (a) are intended for surgical implant into the body or (b) support or sustain life, and (c) whose failure to perform when properly used in accordance with instructions for use provided in the labeling, can be reasonably expected to result in a significant injury of the user. 2. A critical component in any component of a life support, device, or system whose failure to perform can be reasonably expected to cause the failure of the life support device or system, or to affect its safety or effectiveness. Rev. 1.5 December 2008 www.aosmd.com Page 16 of 16