AOZ6606PI

AOZ6606PI EZBuckTM 6A Synchronous Buck Regulator General Description Features The AOZ6606PI works from 4.5V to 18V input voltage range, and provides up to 6A of continuous output current with an output voltage adjustable down to 0.8V.  4.5V to 18V operating input voltage range The AOZ6606PI comes in EPAD-SO8 package and is rated over a -40°C to +85°C operating ambient temperature range.  External program soft start  Synchronous Buck with internal low RDS(ON) (52m/ 24m) high-side and low-side MOSFETs  U-PEM (pulse energy mode) enables 86% plus efficiency with Io=10mA (Vin=12V, Vo=5V)  Adjacent pin short protection  Output voltage adjustable to 0.8V  6A continuous output current  600kHz PWM operation  Cycle-by-cycle current limit  Pre-bias start-up  Extensive protection features  EPAD-SO8 package Applications  High reliable DC/DC converters  High performance LCD TV  High performance cable modems Typical Application VIN CVCC CIN VIN VCC BST RBST CBST EN AOZ6606PI LX COMP RC CC SS CSS L1 3.3H VOUT R1 COUT FB GND R2 Figure 1. 6A Synchronous Buck Regulator, Fs = 600kHz Rev. 1.1 November 2018 www.aosmd.com Page 1 of 15 AOZ6606PI Ordering Information Part Number Ambient Temperature Range Package Environmental AOZ6606PI -40°C to +85°C 8-Pin EPAD SO Green Product AOS Green Products use reduced levels of Halogens, and are also RoHS compliant. Please visit www.aosmd.com/media/AOSGreenPolicy.pdf for additional information. Pin Configuration SS 1 EN 2 LX 8 FB 7 COMP VIN 3 6 VCC GND 4 5 BST Pin Description Pin Number Pin Name 1 SS Soft Start Pin. 2 EN Enable pin. Logic high to enable the device. 3 VIN Supply voltage input. When VIN rises above the UVLO threshold and EN is logic high, the device starts up. 4 GND Power ground. 5 BST Bootstrap. Requires a capacitor connected between LX and BST to form a floating supply across the high-side switch driver. 6 VCC Internal LDO output. 7 COMP External loop compensation pin. Connect a RC network between COMP and GND to compensate the control loop. 8 FB Feedback input. The FB pin is used to set the output voltage via a resistive voltage divider between the output and GND. Exposed Pad LX Switching node. LX is the drain of the internal low-side power FETs. Rev. 1.1 November 2018 Pin Function www.aosmd.com Page 2 of 16 AOZ6606PI Absolute Maximum Ratings Maximum Operating Ratings Exceeding the Absolute Maximum Ratings may damage the device. The device is not guaranteed to operate beyond the Maximum Operating ratings. Parameter Rating Parameter Supply Voltage (VIN), EN (VEN) +20V -0.7V to VIN+0.3V LX to GND Rating Supply Voltage (VIN) 4.5V to 18V Output Voltage Range 0.8V to 0.85*VIN LX to GND (20ns) -5V to 22V Ambient Temperature (TA) VCC, FB, COMP to GND -0.3V to 6V Package Thermal Resistance EPAD SO8 (JA)(2) VBST to LX 6V Junction Temperature (TJ) +150°C Storage Temperature (TS) -65°C to +150°C ESD Rating(1) 2kV Note: -40°C to +85°C 40°C/W Note: 2. The value of JA is measured with the device mounted on a 1-in2 FR-4 four layer board with 2oz copper and Vias, in a still air environment with TA = 25°C. The value in any given application depends on the user’s specification board design. 1. Devices are inherently ESD sensitive, handling precautions are required. Human body model rating: 1.5k in series with 100pF. Electrical Characteristics TA = 25°C, VIN = VEN = 12V, VOUT = 3.3V unless otherwise specified. Specifications in BOLD indicate a temperature range of -40°C to +85°C. These specifications are guaranteed by design. Symbol VIN VUVLO VCC IIN IOFF Parameter Conditions Supply Voltage Min. Typ. 4.5 Input Under-Voltage Lockout Threshold VIN rising VIN falling 3.3 VCC Regulator 4.0 3.7 Max Units 18 V 4.47 V V 5 V VCC Load Regulator ICC = 5mA 3 % Supply Current (Quiescent) IOUT = 0A 250 A Shutdown Supply Current VEN = 0V -40°C < TJunction < 125°C 1 VEN = 0V Feedback Voltage TA = 25°C RO Load Regulation PWM mode 1A < ILoad < 6A 0.5 4.5V < VIN < 18V 1 SV Line Regulation Feedback Voltage Input Current VEN EN Input Threshold VHYS EN Input Hysteresis A 0.1 VFB IFB A 10 0.591 0.600 0.609 % % 200 Off threshold On threshold -40°C < TJunction < 125°C EN Input Current VEN = 5V tSS SS Time CSS = 22nF nA 0.6 V 2 300 IEN V mV 5 A 0.9 2 3.7 ms 500 600 650 kHz Modulator fO Frequency DMAX Maximum Duty Cycle DMIN Controllable Minimum Duty Cycle Gmcs Current Sense Transconductance Rev. 1.1 November 2018 85 % 6.5 8 www.aosmd.com % A/V Page 3 of 16 AOZ6606PI Electrical Characteristics TA = 25°C, VIN = VEN = 12V, VOUT = 3.3V unless otherwise specified. Specifications in BOLD indicate a temperature range of -40°C to +85°C. These specifications are guaranteed by design. Symbol Gma ICH Parameter Conditions Error Amplifier Transconductance Min. Typ. Max Units 300 400 500 A/V Charging Current of Error Amp 40 A 7 A Protection ILIM Current Limit 6.5 VOVP Over Voltage Protection Off threshold On threshold 720 620 mV TOTP Over-temperature Shutdown LImit TJ rising TJ falling 150 100 °C RH High-Side Switch On-Resistance VBST-LX = 5V 52 m RL Low-Side Switch On-Resistance VCC = 5V 24 m Output Stage Rev. 1.1 November 2018 www.aosmd.com Page 4 of 16 AOZ6606PI Functional Block Diagram BST VCC UVLO & POR EN 5V LDO REGULATOR + ISEN - REFERENCE & BIAS SOFTSTART + + EAMP - – PWM COMP + PWM CONTROL LOGIC LEVEL SHIFTER + FET DRIVER SS 0.6V COMP Q1 ILIMIT SS FB VIN LX Q2 600kHz OSCILLATOR GND Rev. 1.1 November 2018 www.aosmd.com Page 5 of 16 AOZ6606PI Efficiency Efficiency vs. Load Current (VIN=5V) 100 100 90 90 Efficiency (%) Efficiency (%) Efficiency vs. Load Current (VIN=12V) 80 70 5.0V OUTPUT L=4.7µH 80 70 3.3V OUTPUT L=3.3µH 3.3V OUTPUT L=3.3µH 2.5V OUTPUT L=3.3µH 60 50 0.01 0.1 60 2.5V OUTPUT L=3.3µH 1.8V OUTPUT L=2.2µH 1.8V OUTPUT L=2.2µH 1.2V OUTPUT L=2.2µH 1.2V OUTPUT L=2.2µH 1 50 0.01 10 0.1 1 10 IO (A) IO (A) Thermal Derating (VIN=12V) Thermal Derating (VIN=5V) 6.2 6.2 6.0 6.0 5.8 5.8 5.6 5.6 5.4 5.4 IO_max (A) IO_max (A) Thermal Derating 5.2 5.0 5.0 VO 4.8 3.3 VO 4.6 5.2 5.0 4.6 2.5 VO 4.4 1.8 VO 4.4 4.2 1.2 VO 4.2 4.0 25 30 35 40 Rev. 1.1 November 2018 45 50 55 60 65 Temperature (°C) 3.3 VO 2.5 VO 4.8 70 75 80 85 1.8 VO 1.2 VO 4.0 www.aosmd.com 25 30 35 40 45 50 55 60 65 Temperature (°C) 70 75 80 85 Page 6 of 16 AOZ6606PI Typical Characteristics Circuit of Typical Application. TA = 25°C, VIN = VEN = 12V, VOUT = 3.3V, unless otherwise specified. Light Load Operation Full Load Operation VLX (5V/div) VLX (5V/div) V O ripple (50mV/div) IL (2A/div) V O ripple (50mV/div) V IN ripple (0.5V/div) V IN ripple (0.2V/div) IL (1A/div) 1µs/div 1µs/div PEM to PWM Mode Change PWM to PEM Mode Change VLX (5V/div) VLX (5V/div) VO (0.2V/div) VO (0.2V/div) IL (2A/div) IL (2A/div) 50µs/div 50µs/div Short Protection Short Protection Recovery VLX (5V/div) VLX (5V/div) VO (1V/div) VO (1V/div) IL (2A/div) IL (2A/div) 50ms/div 50ms/div Rev. 1.1 November 2018 www.aosmd.com Page 7 of 16 AOZ6606PI Typical Characteristics (continued) Circuit of Typical Application. TA = 25°C, VIN = VEN = 12V, VOUT = 3.3V, unless otherwise specified. Start-up to Full Load 50% to 100% Load Transient V IN (5V/div) VO (0.2V/div) VO (1V/div) IO (2A/div) 100µs/div 2ms/div Rev. 1.1 November 2018 IO (2A/div) www.aosmd.com Page 8 of 16 AOZ6606PI Detailed Description The AOZ6606PI is a current-mode step down regulator with integrated high-side NMOS switch and low-side NMOS switch. It operates from a 4.5V to 18V input voltage range and supplies up to 6A of load current. Features include, enable control, Power-On Reset, input under voltage lockout, output over voltage protection, external soft-start and thermal shut down. The AOZ6606PI is available in EPAD-SO8 package. Enable and Soft Start The AOZ6606PI has external soft start feature to limit inrush current and ensure the output voltage ramps up smoothly to regulation voltage. A soft start process begins when the input voltage rises to 4.1V and voltage on EN pin is HIGH. The soft start time is programmed by external soft start capacitor, and can be calculated by below equation: Css  nF x0.6V T SS  ms  = ---------------------------------------5uA signal, at PWM comparator input. If the current signal is less than the error voltage, the internal high-side switch is on. The inductor current flows from the input through the inductor to the output. When the current signal exceeds the error voltage, the high-side switch is off. The inductor current is freewheeling through the internal low-side NMOSFET switch to output. The internal adaptive FET driver guarantees no turn on overlap of both high-side and low-side switch. Comparing with regulators using freewheeling Schottky diodes, the AOZ6606PI uses freewheeling NMOSFET to realize synchronous rectification. It greatly improves the converter efficiency and reduces power loss in the lowside switch. The AOZ6606PI uses a N-Channel MOSFET as the high-side switch. Since the NMOSFET requires a gate voltage higher than the input voltage, a boost capacitor is needed between LX pin and BST pin to drive the gate. The boost capacitor is charged while LX is low. Output Voltage Programming The EN pin of the AOZ6606PI is active high. Connect the EN pin to VIN if enable function is not used. Pull it to ground will disable the AOZ6606PI. Do not leave it open. The voltage on EN pin must be above 2 V to enable the AOZ6606PI. When voltage on EN pin falls below 0.6V, the AOZ6606PI is disabled. Light Load and PWM Operation Under low output current settings, the AOZ6606PI will operate with pulse energy mode to obtain high efficiency. In pulse energy mode, the PWM will not turn off until the inductor current reaches to 800mA and the current signal exceeds the error voltage. Output voltage can be set by feeding back the output to the FB pin by using a resistor divider network. In the application circuit shown in Figure 1. The T-type resistor divider network includes R1 R2. Usually, a design is started by picking a fixed R2 value and calculating the required R1 with equation below. R 1  V O = 0.6   1 + ------- R 2  Some standard value of R1, R2 and most used output voltage values are listed in Table 1. VO (V) R1 (k) R2 (k) Steady-State Operation 1.0 10 15 Under heavy load steady-state conditions, the converter operates in fixed frequency and Continuous-Conduction Mode (CCM). 1.2 10 10 The AOZ6606PI integrates an internal N-MOSFET as the high-side switch. Inductor current is sensed by amplifying the voltage drop across the drain to source of the high side power MOSFET. Output voltage is divided down by the external voltage divider at the FB pin. The difference of the FB pin voltage and reference is amplified by the internal transconductance error amplifier. The error voltage is compared against the current signal, which is sum of inductor current signal and ramp compensation Rev. 1.1 November 2018 1.5 15 10 1.8 20 10 2.5 31.6 10 3.3 68.1 15 5.0 110 15 Table 1. Combination of R1 and R2 should be large enough to avoid drawing excessive current from the output, which will cause power loss. www.aosmd.com Page 9 of 16 AOZ6606PI Protection Features If we let m equal the conversion ratio: The AOZ6606PI has multiple protection features to prevent system circuit damage under abnormal conditions. Over Current Protection (OCP) The sensed inductor current signal is also used for over current protection. Since the AOZ6606PI employs peak current mode control, during over current conditions, the peak inductor current is automatically limited to cycle-by cycle, and if output drop to some level after current limit, then the AOZ6606PI will shut down and auto restart with hiccup mode. VO -------- = m V IN The relation between the input capacitor RMS current and voltage conversion ratio is calculated and shown in Figure. 2 below. It can be seen that when VO is half of VIN, CIN is under the worst current stress. The worst current stress on CIN is 0.5·IO. 0.5 0.4 Power-On Reset (POR) A power-on reset circuit monitors the VIN voltage. When the VIN voltage exceeds 4V, the converter starts operation. When VIN voltage falls below 3.7V, the converter will be shut down. ICIN_RMS(m) 0.3 IO 0.2 0.1 Thermal Protection 0 An internal temperature sensor monitors the junction temperature. It shuts down the internal control circuit and high side NMOS if the junction temperature exceeds 150ºC. The regulator will restart automatically under the control of soft-start circuit when the junction temperature decreases to 100ºC. Application Information The basic AOZ6606PI application circuit is show in Figure 1. Component selection is explained below. Input Capacitor The input capacitor must be connected to the VIN pin and GND pin of AOZ6606PI to maintain steady input voltage and filter out the pulsing input current. The voltage rating of input capacitor must be greater than maximum input voltage plus ripple voltage. The input ripple voltage can be approximated by equation below: VO  VO IO  V IN = -----------------   1 – ---------  --------V IN V IN f  C IN  0 0.5 m 1 Figure 2. ICIN vs. Voltage Conversion Ratio For reliable operation and best performance, the input capacitors must have current rating higher than ICIN-RMS at worst operating conditions. Ceramic capacitors are preferred for input capacitors because of their low ESR and high current rating. Depending on the application circuits, other low ESR tantalum capacitor may also be used. When selecting ceramic capacitors, X5R or X7R type dielectric ceramic capacitors should be used for their better temperature and voltage characteristics. Note that the ripple current rating from capacitor manufactures are based on certain amount of life time. Further derating may be necessary in practical design. Inductor The inductor is used to supply constant current to output when it is driven by a switching voltage. For given input and output voltage inductance and switching frequency together decide the inductor ripple current, which is: Since the input current is discontinuous in a buck converter, the current stress on the input capacitor is another concern when selecting the capacitor. For a buck circuit the RMS value of input capacitor current can be calculated by: VO  VO  I L = -----------   1 – --------- V IN fL  VO  VO  I CIN_RMS = I O  ---------  1 – --------- V IN  V IN Rev. 1.1 November 2018 www.aosmd.com Page 10 of 16 AOZ6606PI The peak inductor current is: 1 V O = I L  ------------------------8fC I L I Lpeak = I O + -------2 O High inductance gives low inductor ripple current but requires larger size inductor to avoid saturation. Low ripple current reduces inductor core losses. It also reduces RMS current through inductor and switches, which results in less conduction loss. Usually, peak to peak ripple current on inductor is designed to be 20% to 40% of output current. When selecting the inductor, make sure it is able to handle the peak current without saturation even at the highest operating temperature. The inductor takes the highest current in a buck circuit. The conduction loss on inductor need to be checked for thermal and efficiency requirements. Surface mount inductors in different shape and styles are available from Coilcraft, Elytone and Murata. Shielded inductors are small and radiate less EMI noise. But they cost more than unshielded inductors. The choice depends on EMI requirement, price and size. Output Capacitor The output capacitor is selected based on the DC output voltage rating, output ripple voltage specification and ripple current rating. The selected output capacitor must have a higher rated voltage specification than the maximum desired output voltage including ripple. De-rating needs to be considered for long term reliability. Output ripple voltage specification is another important factor for selecting the output capacitor. In a buck converter circuit, output ripple voltage is determined by inductor value, switching frequency, output capacitor value and ESR. It can be calculated by the equation below: VO  IL  (ESRCO  1 ) 8  f  CO If the impedance of ESR at switching frequency dominates, the output ripple voltage is mainly decided by capacitor ESR and inductor ripple current. The output ripple voltage calculation can be further simplified to: V O = I L  ESR CO For lower output ripple voltage across the entire operating temperature range, X5R or X7R dielectric type of ceramic, or other low ESR tantalum are recommended to be used as output capacitors. In a buck converter, output capacitor current is continuous. The RMS current of output capacitor is decided by the peak to peak inductor ripple current. It can be calculated by: I L I CO_RMS = ---------12 Usually, the ripple current rating of the output capacitor is a smaller issue because of the low current stress. When the buck inductor is selected to be very small and inductor ripple current is high, output capacitor could be overstressed. Loop Compensation The AOZ6606PI employs peak current mode control for easy use and fast transient response. Peak current mode control eliminates the double pole effect of the output L&C filter. It greatly simplifies the compensation loop design. With peak current mode control, the buck power stage can be simplified to be a one-pole and one-zero system in frequency domain. The pole is dominant pole can be calculated by: f p1  where CO is output capacitor value and ESRCO is the Equivalent Series Resistor of output capacitor. When low ESR ceramic capacitor is used as output capacitor, the impedance of the capacitor at the switching frequency dominates. Output ripple is mainly caused by capacitor value and inductor ripple current. The output ripple voltage calculation can be simplified to: 1 2  CO  RL The zero is a ESR zero due to output capacitor and its ESR. It is can be calculated by: fZ 1  1 2  CO  ESRCO where CO is the output filter capacitor; Rev. 1.1 November 2018 www.aosmd.com Page 11 of 16 AOZ6606PI RL is load resistor value; ESRCO is the equivalent series resistance of output capacitor; The compensation design is actually to shape the converter control loop transfer function to get desired gain and phase. Several different types of compensation network can be used for the AOZ6606PI. For most cases a series capacitor and resistor network connected to the COMP pin sets the pole-zero and is adequate for a stable high-bandwidth control loop. In the AOZ6606PI, FB pin and COMP pin are the inverting input and the output of internal error amplifier. A series R and C compensation network connected to COMP provides one pole and one zero. The pole is: fp 2  with Cc. Using selected crossover frequency, fC, to calculate Rc: Rc  fC  where fC is desired crossover frequency. For best performance, fc is set to be about 1/10 of switching frequency: VFB is 0.6V; GEA is the error amplifier transconductance, which is 480 x 10-6 A/V; GCS is the current sense circuit transconductance, which is 8 A/V; The compensation capacitor Cc and resistor Rc together make a zero. This zero is put somewhere close to the dominate pole fp1 but lower than 1/5 of selected crossover frequency. Cc can is selected by: GEA 2  Cc  GVEA Where Cc  GEA is the error amplifier transconductance, which is 480 x 10-6 A/V; GVEA is the error amplifier voltage gain, which is 4800; CO  RL Rc An easy-to-use application software which helps to design and simulate the compensation loop can be found at www.aosmd.com. Cc is compensation capacitor in Figure 1; The zero given by the external compensation network, capacitor Cc and resistor Rc, is located at: fZ 2  2  Co VO  VFB GEA  GCS 1 2  Cc  Rc To design the compensation circuit, a target crossover frequency fC for close loop must be selected. The system crossover frequency is where control loop has unity gain. The crossover is the also called the converter bandwidth. Generally a higher bandwidth means faster response to load transient. However, the bandwidth should not be too high because of system stability concern. When designing the compensation loop, converter stability under all line and load condition must be considered. Usually, it is recommended to set the bandwidth to be equal or less than 1/10 of switching frequency. The strategy for choosing Rc and Cc is to set the cross over frequency with Rc and set the compensator zero Thermal Management and Layout Consideration In the AOZ6606PI buck regulator circuit, high pulsing current flows through two circuit loops. The first loop starts from the input capacitors, to the VIN pin to the LX pad to the filter inductor to the output capacitor and load and then return to the input capacitor through ground. Current flows in the first loop when the high side switch is on. The second loop starts from inductor, to the output capacitors and load, to the low side NMOSFET. Current flows in the second loop when the low side NMOSFET is on. In PCB layout minimizing the two loops area reduces the noise of this circuit and improves efficiency. A ground plane is strongly recommended to connect input capacitor, output capacitor and GND pin of the AOZ6606PI. In the AOZ6606PI buck regulator circuit, the major power dissipating components are the AOZ6606PI and the output inductor. The total power dissipation of converter circuit can be measured by input power minus output power. P total_loss = V IN  I IN – V O  I O Rev. 1.1 November 2018 www.aosmd.com Page 12 of 16 AOZ6606PI The power dissipation of inductor can be approximately calculated by output current and DCR of inductor. P inductor_loss = IO2  R inductor  1.1 The actual junction temperature can be calculated with power dissipation in the AOZ6606PI and thermal impedance from junction to ambient. T junction =  P total_loss – P inductor_loss    JA The maximum junction temperature of AOZ6606PI is 150ºC, which limits the maximum load current capability. The thermal performance of the AOZ6606PI is strongly affected by the PCB layout. Extra care should be taken by users during design process to ensure that the IC will operate under the recommended environmental conditions. Rev. 1.1 November 2018 1. The exposed pad (LX) is connected to internal Highside FET source and Lowside FET drains. Connect a large copper plane to LX pin to help thermal dissipation. 2. Do not use thermal relief connection to the VIN and the GND pin. Pour a maximized copper area to the GND pin and the VIN pin to help thermal dissipation. 3. Input capacitor should be connected to the VIN pin and the GND pin as close as possible. 4. Make the current trace from LX pins to L to Co to the GND as short as possible. 5. Pour copper plane on all unused board area and connect it to stable DC nodes, like VIN, GND or VOUT. 6. Keep sensitive signal trace away from the LX pad. www.aosmd.com Page 13 of 16 AOZ6606PI Package Dimensions, SO-8 EP1 Gauge plane 0.2500 D0 C L L1 E2 E1 E3 E L1' D1 Note 5 D θ 7 (4x) A2 e B A A1 Dimensions in millimeters RECOMMENDED LAND PATTERN 3.70 2.20 5.74 2.71 2.87 0.80 1.27 0.635 UNIT: mm Dimensions in inches Symbols A Min. 1.40 Nom. 1.55 Max. 1.70 Symbols A A1 A2 B 0.00 1.40 0.31 0.05 1.50 0.406 0.10 1.60 0.51 A1 A2 B C D 0.17 4.80 — 4.96 C D D0 D1 E e E1 E2 E3 L y θ | L1–L1' | L1 3.20 3.10 5.80 — 3.80 2.21 0.25 5.00 3.60 3.50 6.20 — 4.00 2.61 3.40 3.30 6.00 1.27 3.90 2.41 0.40 REF 0.40 0.95 1.27 — — 0.10 0° — 3° 0.04 1.04 REF 8° 0.12 D0 D1 E e E1 E2 E3 L y θ | L1–L1' | L1 Min. 0.055 0.000 0.055 0.012 0.007 0.189 Nom. 0.061 Max. 0.067 0.002 0.059 0.016 0.004 0.063 0.020 — 0.010 0.195 0.197 0.126 0.134 0.142 0.122 0.130 0.138 0.228 0.236 0.244 — 0.050 — 0.150 0.153 0.157 0.087 0.095 0.103 0.016 REF 0.016 0.037 0.050 — — 0.004 0° 3° 8° — 0.002 0.005 0.041 REF Notes: 1. Package body sizes exclude mold flash and gate burrs. 2. Dimension L is measured in gauge plane. 3. Tolerance 0.10mm unless otherwise specified. 4. Controlling dimension is millimeter, converted inch dimensions are not necessarily exact. 5. Die pad exposure size is according to lead frame design. 6. Followed from JEDEC MS-012 Rev. 1.1 November 2018 www.aosmd.com Page 14 of 16 AOZ6606PI Tape and Reel Dimensions, SO-8, EP1 Carrier Tape P1 D1 P2 T E1 E2 E B0 K0 A0 D0 P0 Feeding Direction UNIT: mm Package SO-8 (12mm) A0 6.40 ±0.10 B0 5.20 ±0.10 K0 2.10 ±0.10 D0 1.60 ±0.10 D1 1.50 ±0.10 E 12.00 ±0.10 Reel E1 1.75 ±0.10 E2 5.50 ±0.10 P0 8.00 ±0.10 P1 4.00 ±0.10 P2 2.00 ±0.10 T 0.25 ±0.10 W1 S G N M K V R H W UNIT: mm W N Tape Size Reel Size M 12mm ø330 ø330.00 ø97.00 13.00 ±0.10 ±0.30 ±0.50 W1 17.40 ±1.00 H K ø13.00 10.60 +0.50/-0.20 S 2.00 ±0.50 G — R — V — Leader/Trailer and Orientation Trailer Tape 300mm min. or 75 empty pockets Rev. 1.1 November 2018 Components Tape Orientation in Pocket www.aosmd.com Leader Tape 500mm min. or 125 empty pockets Page 15 of 16 AOZ6606PI Part Marking AD00 YWLT Part Number Code Assembly Lot Code Year & Week Code LEGAL DISCLAIMER Applications or uses as critical components in life support devices or systems are not authorized. AOS does not assume any liability arising out of such applications or uses of its products. AOS reserves the right to make changes to product specifications without notice. It is the responsibility of the customer to evaluate suitability of the product for their intended application. Customer shall comply with applicable legal requirements, including all applicable export control rules, regulations and limitations. AOS' products are provided subject to AOS' terms and conditions of sale which are set forth at: http://www.aosmd.com/terms_and_conditions_of_sale LIFE SUPPORT POLICY ALPHA AND OMEGA SEMICONDUCTOR PRODUCTS ARE NOT AUTHORIZED FOR USE AS CRITICAL COMPONENTS IN LIFE SUPPORT DEVICES OR SYSTEMS. As used herein: 1. Life support devices or systems are devices or systems which, (a) are intended for surgical implant into the body or (b) support or sustain life, and (c) whose failure to perform when properly used in accordance with instructions for use provided in the labeling, can be reasonably expected to result in a significant injury of the user. Rev. 1.1 November 2018 2. A critical component in any component of a life support, device, or system whose failure to perform can be reasonably expected to cause the failure of the life support device or system, or to affect its safety or effectiveness. www.aosmd.com Page 16 of 16