BL8039
2A 2MHz 5.5V Synchronous Buck Converter
DESCRIPTION
FEATURES
The BL8039 is a high-efficiency, DC-to-DC stepdown switching regulators, capable of delivering up
to 2A of output current. The device operates from
an input voltage range of 2.6V to 5.5V and provides
an output voltage from 0.6V to VIN. Working at a
fixed frequency of 2MHz allows the use of small
external components, such as ceramic input and
output caps, as well as small inductors, while still
providing low output ripples. This low noise output
along with its excellent efficiency achieved by the
internal synchronous rectifier, making BL8039 an
ideal replacement for large power consuming linear
regulators. Internal soft-start control circuitry
reduces inrush current. Short-circuit and thermal
shutdown protection improves design reliability.
The BL8039 is available in SOT23-5 package.
TYPICAL APPLICATION
VIN
2.6V to 5.5V
10uF
VOUT
1.8V
SW
LC2202
EN
240k
Cellular phones
Digital cameras
MP3 and MP4 players
Set top boxes
Wireless and DSL modems
USB supplied devices in notebooks
Portable devices
FB
VIN
5
4
option
NC
FB
GND
APPLICATIONS
PIN OUT & MARKING
1uH/2.2uH
VIN
High efficiency: up to 97%
Up to 2A Max output current
Output voltage range: VREF to VIN
2MHz switching frequency
Low dropout 100% duty operation
Internal compensation and soft-start
Current mode control
Reference 0.6V±2%
Logic control shutdown (IQ2000V
Note: Exceed these limits to damage to the device. Exposure to absolute maximum rating conditions may affect
device reliability.
ELECTRICAL CHARACTERISTICS
(VIN=5V, TA=25C, unless otherwise specified.)
Symbol
Parameter
VIN
Input voltage range
VOVP
Input overvoltage threshold
VREF
Feedback voltage
Conditions
0.588
IQ
Quiescent current
Active, VFB=0.65, No Switching
Shutdown input current
EN=0V
LNR
Line regulation
Vin=2.6V to 5.5V
LDR
Load regulation
Iout=0.01 to 1A
FSOC
Switching frequency
PMOS Rdson
RDSON_N
NMOS Rdson
VUVLO
VUVLO_HY
ILIMIT
V
0.1
1
uA
uA
0.1
0.2
%/V
0.1
0.2
%/A
2
2.4
MHz
180
Vin=5V, Vout=3.3V, Iout=0A
VH_EN
EN input high voltage
VL_EN
EN input low voltage
mohm
130
1.9
2.1
2.7
EN leakage current
uA
1
Peak current limit
IENLK
V
0.612
100
SW leakage current
V
0.6
UVLO hysteresis
ISWLK
Unit
5.5
80
1.6
Under voltage lockout
INOLOAD
Max
6.1
Vin=5V
Feedback leakage current
RDSON_P
Typ
2.6
IFB
ISHUTDOWN
Min
mohm
2.3
mV
3.3
80
Vin=6V, VSW=0 or 6V, EN=0V
V
A
uA
1
uA
1
uA
1.2
V
0.5
V
TSD
Thermal shutdown temp
160
°C
TSH
Thermal shutdown hysteresis
15
°C
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2
BL8039
ELECTRICAL PERFORMANCE
Tested under TA=25C, unless otherwise specified
Efficiency vs. Output Current
Efficiency vs. Output Current
(Vout=3.3V)
100%
100%
95%
95%
90%
90%
85%
85%
Efficiency
Efficiency
(Vout=1.8V)
80%
75%
80%
75%
70%
70%
65%
65%
60%
60%
55%
55%
Vin=5V
50%
0.001
0.01
0.1
Iout (A)
1
Vin=5V
50%
0.001
10
Load Regulation
0.01
1
10
Load Regulation
(Vout=1.8V)
(Vout=3.3V)
2.0
3.5
1.9
3.4
1.8
3.3
Vout(V)
Vout(V)
0.1
Iout (A)
1.7
1.6
3.2
3.1
Vin=5V
Vin=5V
1.5
3.0
0.0
0.5
1.0
Iout (A)
1.5
2.0
Output Ripple and SW at 1A load
0.0
1.0
Iout (A)
1.5
Output Ripple and SW at 1A load
Vin=5V / Vout=1.2V
Vin=5V / Vout=1.8V
Vout ripple, 5mV/div
Vout ripple, 5mV/div
Vsw, 2V/div
Vsw, 2V/div
Isw, 1A/div
Isw, 1A/div
Ch2—Vout ripple, Ch3—Vsw, Ch4—ISW
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0.5
Ch2—Vout ripple, Ch3—Vsw, Ch4—ISW
3
2.0
BL8039
Output Ripple and SW at 1A load
Output Ripple and SW at 1A load
Vin=5V / Vout=2.5V
Vin=5V / Vout=3.3V
Vout ripple, 5mV/div
Vout ripple, 5mV/div
Vsw, 2V/div
Vsw, 2V/div
Isw, 1A/div
Isw, 1A/div
Ch2—Vout ripple, Ch3—Vsw, Ch4—ISW
Ch2—Vout ripple, Ch3—Vsw, Ch4—ISW
Load Transient
Load Transient
Vin=5V / Vout=1.2V / Iout=0.01~1.8A
Vin=5V / Vout=1.8V / Iout=0.01~1.8A
Vout ripple, 100mV/div
Vout ripple, 100mV/div
Iout, 1A/div
Iout, 1A/div
Ch2—Vout ripple, Ch4—Iout
Ch2—Vout ripple, Ch4—Iout
Load Transient
Load Transient
Vin=5V / Vout=3.3V / Iout=0.01~1.8A
Vin=5V / Vout=2.5V / Iout=0.01~1.8A
Vout ripple, 200mV/div
Vout ripple, 200mV/div
Iout, 1A/div
Iout, 1A/div
Ch2—Vout ripple, Ch4—Iout
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Ch2—Vout ripple, Ch4—Iout
4
BL8039
PIN DESCRIPTION
Pin #
Name
Description
1
2
3
4
EN
GND
SW
VIN
5
FB
Enable pin for the IC. Drive the pin to high to enable the part, and low to disable.
Ground.
Inductor connection. Connect an inductor between SW and the regulator output.
Supply voltage.
Feedback input. Connect an external resistor divider from the output to FB and GND to set the
output to a voltage between 0.6V and Vin.
BLOCK DIAGRAM
DETAILED DESCRIPTION
The BL8039 high-efficiency switching regulator is a
small, simple, DC-to-DC step-down converter
capable of delivering up to 2A of output current.
The device operates in pulse-width modulation
(PWM) at 2MHz from a 2.6V to 5.5V input voltage
and provides an output voltage from 0.6V to VIN,
making the BL8039 ideal for on-board postregulation applications. An internal synchronous
rectifier improves efficiency and eliminates the
typical Schottky free-wheeling diode. Using the on
resistance of the internal high-side MOSFET to
sense switching currents eliminates current-sense
resistors, further improving efficiency and cost.
compensation ramp. At each rising edge of the
internal clock, the internal high-side MOSFET turns
on until the PWM comparator terminates the on
cycle. During this on-time, current ramps up
through the inductor, sourcing current to the
output and storing energy in the inductor. The
current mode feedback system regulates the peak
inductor current as a function of the output voltage
error signal. During the off cycle, the internal highside P-channel MOSFET turns off, and the internal
low-side N-channel MOSFET turns on. The inductor
releases the stored energy as its current ramps
down while still providing current to the output.
Loop operation
Current sense
BL8039 uses a PWM current-mode control scheme.
An open-loop comparator compares the integrated
voltage-feedback signal against the sum of the
amplified current-sense signal and the slope
An internal current-sense amplifier senses the
current through the high-side MOSFET during on
time and produces a proportional current signal,
which is used to sum with the slope compensation
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BL8039
signal. The summed signal then is compared with
the error amplifier output by the PWM comparator
to terminate the on cycle.
(UVLO), shutdown mode, or restarts following a
thermal shutdown event, the soft-start circuitry
slowly ramps up current available at SW.
Current limit
UVLO
There is a cycle-by-cycle current limit on the highside MOSFET of 2.7A (typ). When the current
flowing out of SW exceeds this limit, the high-side
MOSFET turns off and the synchronous rectifier
turns on. BL8039 utilizes a frequency fold-back
mode to prevent overheating during short-circuit
output conditions. The device enters frequency
fold-back mode when the FB voltage drops below
100mV, limiting the current to 2.7A (typ) and
reducing power dissipation. Normal operation
resumes upon removal of the short-circuit
condition.
If VIN drops below 2.1V, the UVLO circuit inhibits
switching. Once VIN rises above 2.2V, the UVLO
clears, and the soft-start sequence activates.
Soft-start
Thermal shutdown
Thermal shutdown protection limits total power
dissipation in the device. When the junction
temperature exceeds TJ= +160°C, a thermal sensor
forces the device into shutdown, allowing the die to
cool. The thermal sensor turns the device on again
after the junction temperature cools by 15°C,
resulting in a pulsed output during continuous
overload conditions. Following a thermal-shutdown
condition, the soft-start sequence begins.
BL8039 has an internal soft-start circuitry to reduce
supply inrush current during startup conditions.
When the device exits under-voltage lockout
DESIGN PROCEDURE
Setting output voltages
Output voltages are set by external resistors. The
FB threshold is 0.6V.
𝑉𝑂𝑈𝑇
𝑅𝑇𝑂𝑃 = 𝑅𝐵𝑂𝑇𝑇𝑂𝑀 × (
− 1)
0.6
Input capacitor selection
The input capacitor in a DC-to-DC converter reduces
current peaks drawn from the battery or other
input power source and reduces switching noise in
the controller. The impedance of the input
capacitor at the switching frequency should be less
than that of the input source so high-frequency
switching currents do not pass through the input
source. The output capacitor keeps output ripple
small and ensures control-loop stability. The output
capacitor must also have low impedance at the
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switching frequency. Ceramic, polymer, and
tantalum capacitors are suitable, with ceramic
exhibiting the lowest ESR and high-frequency
impedance. Output ripple with a ceramic output
capacitor is approximately as follows:
𝑉𝑂𝑈𝑇
𝑉𝑂𝑈𝑇
∆𝐼𝐿 =
× (1 −
)
𝐿 × 𝑓𝑆
𝑉𝐼𝑁
∆𝑉𝑂𝑈𝑇 =
8
× 𝑓𝑆2
𝑉𝑂𝑈𝑇
𝑉𝑂𝑈𝑇
× (1 −
)
𝑉𝐼𝑁
× 𝐿 × 𝐶𝑂𝑈𝑇
If the capacitor has significant ESR, the output
ripple component due to capacitor ESR is as follows:
𝑉𝑂𝑈𝑇
𝑉𝑂𝑈𝑇
∆𝑉𝑂𝑈𝑇 =
× (1 −
) × 𝑅𝐸𝑆𝑅
𝑓𝑆 × 𝐿
𝑉𝐼𝑁
BL8039
LAYOUT GUIDE
The blue line is placed
on the back side.
Cout as close as
possible to Vout
Cout
Vout
Keep the path short
and wide for low
resistance
L
Make GND loop
Resistance as
small as possible
Jumper
Off
EN
SW
SW
GND
On
GND
Keep the path short
and wide for low
resistance
FB
VIN
FB&GND connected
to R1 directly as
short as possible
VIN
Cin
R1
R2
Cin as close as
possible to VIN
PACKAGE OUTLINE
Package
SOT23-5
Devices per reel
Package specification:
Unit: mm
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7
3000pcs