ADCS9888CVH-170/NOPB

OBSOLETE ADCS9888 www.ti.com SNAS203C – JAN 2000 – REVISED APRIL 2013 ADCS9888 205/170/140 MSPS Video Analog Front End Check for Samples: ADCS9888 FEATURES APPLICATIONS • • • • • • • 1 2 • • 205 million pixels/s conversion rate Digitally programmed gain and offset for red, green and blue color balancing Compatible with RGB and YUV/YPbPr video signals Output format supports 4:2:2 video pulldown DESCRIPTION KEY SPECIFICATIONS • • • • • • • LCD flat panel monitors Video projectors Plasma display panels Video capture hardware RGB and YUV video processing Output data resolution 8 bits x 3 channels Maximum pixel conversion rate 205 MHz Analog input bandwidth (typical) 500 MHz PLL clock jitter (typical) 570 ps p-p Analog supply voltage 3.0 V to 3.6 V I/O supply voltage 2.2 V to 3.6 V Power dissipation (typical) 1.3W The ADCS9888 is a high performance Analog Front End (AFE) for digital video applications at resolutions up to UXGA. It performs all the analog and mixed signal functions necessary to digitize a variety of computer and component video sources. The ADCS9888 has a 3 channel, 8 bit 205 MHz ADC with full DC restoration and gain/offset compensation. Full processing of synchronization signals is included with on-chip PLL locked to the pixel rate. Digital sync and analog sync-on-green signals are supported. Flexible data output modes support a variety of downstream data capture and processing applications. These devices have limited built-in ESD protection. The leads should be shorted together or the device placed in conductive foam during storage or handling to prevent electrostatic damage to the MOS gates. Typical Application VIDEO SCALER OSD ADCS9888 VIDEO PROJECTOR uC DISPLAY DRIVE 1 2 Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet. All trademarks are the property of their respective owners. PRODUCTION DATA information is current as of publication date. Products conform to specifications per the terms of the Texas Instruments standard warranty. Production processing does not necessarily include testing of all parameters. Copyright © 2000–2013, Texas Instruments Incorporated OBSOLETE ADCS9888 SNAS203C – JAN 2000 – REVISED APRIL 2013 www.ti.com Simplified Block Diagram VD VDD PVD 8 CLAMP RED 0 GREEN 0 BLUE 0 8 A/D ROUTA 8 6:3 MUX ROUTB 8 A/D CLAMP RED 1 GREEN 1 BLUE 1 8 GOUTA 8 8 GOUTB A/D CLAMP RMIDSCV 8 BMIDSCV 8 BOUTA DATA OUT VREF BOUTB DATACK DATACK_B SOGIN 0 SOGIN 1 HSYNC 0 HSYNC 1 VSYNC 0 VSYNC 1 HSOUT 2:1 MUX VSOUT SOGOUT 2:1 MUX SYNC. PROCESSING 2:1 MUX CLOCK GENERATION CIRCUITRY PVD COAST CLAMP FILT CKINV CKEXT A0 SCL CONFIGURATION REGISTERS SDA GND 2 Submit Documentation Feedback Copyright © 2000–2013, Texas Instruments Incorporated Product Folder Links: ADCS9888 OBSOLETE ADCS9888 www.ti.com SNAS203C – JAN 2000 – REVISED APRIL 2013 DRB4 DRB5 DRB6 DRB7 106 105 104 103 DRB2 DRB3 108 107 DRB0 DRB1 110 109 VDD GND DRA6 DRA7 113 112 111 DRA4 116 115 114 DRA5 DRA2 DRA3 118 DRA0 DRA1 120 119 117 DATACK VDD GND 123 HSOUT DATACK_B 122 121 SOGOUT 125 124 GND VD VSOUT 128 127 126 Connection Diagram 1 102 2 101 VDD GND 3 100 GND 4 99 GND RAIN0 VD VD 5 98 VDD 6 97 DGA0 7 96 DGA1 RAIN1 NC VD 8 95 DGA2 9 94 DGA3 DGA4 REFBYPASS GND GND 10 93 GND SOGIN0 11 92 DGA5 12 91 DGA6 GAIN0 VD 13 90 DGA7 14 89 GND SOGIN1 15 88 VDD GND 16 87 DGB0 GAIN1 VD 17 86 DGB1 GND 19 BAIN0 VD 20 83 DGB4 21 82 DGB5 18 ADCS9888 128 pin QFP Top View 85 DGB2 84 DGB3 GND 22 81 DGB6 BAIN1 NC VD 23 80 DGB7 24 79 25 78 VDD GND 63 64 D B B0 D B B4 62 D B B5 D B B2 DBB1 59 60 61 D B B6 D B B3 57 58 VDD D B B7 55 GND 56 65 GND 38 53 GND NC 54 GND 66 CKEXT 67 37 COAST 36 51 VDD GND 52 68 PVD 35 GND GND GND VD 49 69 50 DBA7 34 FILT 70 GND 33 48 DBA6 A0 VD PVD 71 46 32 47 DBA5 SCL PVD 72 GND DBA4 31 44 73 45 30 VSYNC0 DBA3 CLAMP SDA HSYNC0 74 41 29 42 43 DBA2 CKINV GND 75 VSYNC1 HSYNC1 DBA1 28 39 DBA0 76 40 77 27 NC 26 GND VD GND GND Submit Documentation Feedback Copyright © 2000–2013, Texas Instruments Incorporated Product Folder Links: ADCS9888 3 OBSOLETE ADCS9888 SNAS203C – JAN 2000 – REVISED APRIL 2013 www.ti.com Pin Descriptions Pin Label Type Description Analog Video Inputs 5 RAIN0 Analog Input Channel 0 Red (V) Video Input. Input for Red component video channel or V chrominance channel in YUV/YPbPr/YCbCr applications. A high impedance analog input. Input signal should be capacitively coupled to the input using a 0.1 μF capacitor to support clamping and DC restoration. Signal range of 0.5 VPP to 1.0 VPP depending on gain setting. 13 GAIN0 Analog Input Channel 0 Green (Y) Video Input. Input for Green component video channel or Y luminance channel in YUV/YPbPr/YCbCr applications. A high impedance analog input. Input signal should be capacitively coupled to the input using a 0.1 μF capacitor to support clamping and DC restoration. Signal range of 0.5 VPP to 1.0 VPP depending on gain setting. 20 BAIN0 Analog Input Channel 0 Blue (U) Video Input. Input for Blue component video channel or U chrominance channel in YUV/YPbPr/YCbCr applications. A high impedance analog input. Input signal should be capacitively coupled to the input using a 0.1 μF capacitor to support clamping and DC restoration. Signal range of 0.5 VPP to 1.0 VPP depending on gain setting. 8 RAIN1 Analog Input Channel 1 Red (V) Video Input. See RAIN0 for more information. 17 GAIN1 Analog Input Channel 1 Green (Y) Video Input. See GAIN0 for more information. 23 BAIN1 Analog Input Channel 1 Blue (U) Video Input. See BAIN0 for more information. 12 SOGIN0 Analog Input Channel 0 Sync-On-Green-Input. A high impedance analog input. The video channel containing synchronization information should be capacitively coupled to this input using a 1.0 nF capacitor to support negative peak clamping of the signal. When unused, this input should be left unconnected. 16 SOGIN1 Analog Input Channel 1 Sync-On-Green-Input. See SOGIN0 for more information. 45 HSYNC0 Digital Input Channel 0 Horizontal Sync Input. A logic level synchronization signal at the horizontal line rate is applied to this input. In applications where a composite, logic level sync signal is present, that signal should be connected to the HSYNC input. A Schmitt trigger input is used for improved noise rejection. See the Application Information section for more information. 44 VSYNC0 Digital Input Channel 0 Vertical Sync Input. A logic level synchronization signal at the vertical frame rate is applied to this input. A Schmitt trigger input is used for improved noise rejection. See the Application Information section for more information. 43 HSYNC1 Digital Input Channel 1 Horizontal Sync Input. See HSYNC0 for more information. 42 VSYNC1 Digital Input Channel 1 Vertical Sync Input. See VSYNC0 for more information. 30 CLAMP Digital Input External CLAMP Timing Input. When enabled via Register OFh, Bit 7, this input will turn on the clamp circuits in the analog video inputs. This signal should be asserted during the black reference portion of the video waveform. Please refer to the Application Information section for more information. 53 COAST Digital Input PLL Clock Generator Coast Input. When enabled via Register 0Fh, Bit 5, this input will cause the clock generator circuit to run open loop and ignore the input reference clock. This is useful when operating with sync signals that contain extra equalization pulses that must be ignored by the PLL. In many cases, the internal VSOUT signal is used to provide the coast control signal, but in some cases it is useful to provide an external COAST control. Please refer to the Application Information section for more information. 54 CKEXT Digital Input External Clock Input (Optional). This input can be used to provide an external clock source instead of the internally generated clock. It is enabled via Register 15h, Bit 0. When an external clock is used, most other internal functions operate normally. When unused, this pin can be connected to ground directly, or through a 10 kΩ resistor. The sampling phase adjustment feature is operational when CKEXT is used. 29 CKINV Digital Input Sampling clock Inverting Input. This input can be used to invert the pixel sampling clock, with respect to the normal phase of operation. This causes the pixel sampling point to be shifted by 180 degrees in phase. Alternate pixel sampling mode makes use of this feature by sampling at 1/2 the incoming pixel rate, and switching the sampling phase by 180 degree between alternate frames of video. When unused, this input should be grounded. See the Application Information section for more information. Analog Video Sync Sync/Clock Inputs Serial Interface 4 Submit Documentation Feedback Copyright © 2000–2013, Texas Instruments Incorporated Product Folder Links: ADCS9888 OBSOLETE ADCS9888 www.ti.com SNAS203C – JAN 2000 – REVISED APRIL 2013 Pin Descriptions (continued) Pin Label Type Description 31 SDA Digital I/O Serial Control Interface Data Input/Output. The serial interface is used to access the configuration and status registers in the ADCS9888. Mode and Data information are transferred through the SDA pin from the host or master device. Please refer to the Application Information section of the datasheet under Serial Communications for more information. 32 SCL Digital Input Serial Control Interface Clock Input. The clock input is controlled by the host or master device, and is used to load in the data sent by the host, and to clock data out of the ADCS9888. Please refer to the Application Information section of the datasheet under Serial Communications for more information. 33 A0 Digital Input The least significant bit of the device serial address is selectable as 0 or 1 to allow up to 2 ADCS9888 devices to be connected on the same serial interface. Please refer to the Application Information section of the datasheet under Serial Communications for more information. 125 HSOUT Digital Output Horizontal Sync Output. Internally generated and phase aligned horizontal sync signal. This signal is used as a timing reference for the digital output data stream. Please refer to the section on sync processing for more information. 127 VSOUT Digital Output Vertical Sync Output. A delayed version of the input vertical synchronization signal. Please refer to the section on sync processing for more information. 126 SOGOUT Digital Output Sync-On-Green Output. A logic level signal that is the output of the Sync-On-Green slicer circuit. Please refer to the section on sync processing for more information. 123 DATACK Digital Output Data Output Clock. Complementary data clocks are provided so that output data and HSOUT can be synchronously captured by external logic or memory devices. The clock outputs are synchronous with the internal pixel sample clock. As the sampling phase is adjusted, the DATACK, data, and HSOUT signals all shift together with the sampling interval. When the chip is in power down or seek mode, the DATACK outputs enter a high impedance state. 124 DATACK_B Digital Output Data Output Clock Invert. See DATACK description. 113-120 DR_A(7:0) Digital Output Red Port A (V or U/V) Output Data. Converted pixel data is presented at the data output port synchronous with the DATACK and HSOUT signals. As the pixel sample phase is adjusted, the HSOUT, DATACK and data outputs all shift together. In single channel mode, all data is presented at the A output ports. In dual channel mode, output data is presented at A and B outputs, either in alternating (interleaved mode) or simultaneous (parallel mode ) timing. When 4:2:2 pulldown mode is enabled, only the A ports are used, with U/V data output on Red Port A, and Y data output on Green Port A. When the chip is in seek mode, or low power mode, all data outputs are placed in a high impedance state. See the Application Information section and Configuration Register Descriptions section for more information. 103-110 DR_B(7:0) Digital Output Red Port B (V) Output Data. See DR_A(7:0). 90-97 DG_A(7:0) Digital Output Green Port A (Y) Output Data. See DR_A(7:0). 80-87 DG_B(7:0) Digital Output Green Port B (Y) Output Datasheet. See DR_A(7:0). 70-77 DB_A(7:0) Digital Output Blue Port A (U) Output Data. See DR_A(7:0). 57-64 DB_B(7:0) Digital Output Blue Port B (U) Output Data. See DR_A(7:0). Sync. Outputs Data Clock Output Data Outputs Voltage Reference Bypass 2 REF BYPASS Analog Bypass Internal Reference Bypass. A 0.1 μF capacitor will be connected from this pin to ground, to provide a low impedance decoupling for the internal 1.23V bandgap voltage reference. 9 RMIDSCV (NC) Analog Bypass Red (V) Channel midscale Voltage Bypass. No external bypass is required for the midscale voltage. Therefore, this pin is not connected to the internal circuitry. To maintain compatibility with other designs external capacitors can be connected without affecting operation, performance, or reliability. 24 BMIDSCV (NC) Analog Bypass Blue (U) Channel midscale Voltage Bypass. No external bypass is required for the midscale voltage. Therefore, this pin is not connected to the internal circuitry. To maintain compatibility with other designs external capacitors can be connected without affecting operation, performance, or reliability. PLL Loop Filter Submit Documentation Feedback Copyright © 2000–2013, Texas Instruments Incorporated Product Folder Links: ADCS9888 5 OBSOLETE ADCS9888 SNAS203C – JAN 2000 – REVISED APRIL 2013 www.ti.com Pin Descriptions (continued) Pin 50 Label FILT Type Description PLL VCO Bypass Phase Locked Loop - Voltage Controlled Oscillator filter connection. An R/C filter circuit is used to maintain the VCO control voltage. This circuit should be isolated from all other circuitry to minimize clock jitter. The circuit is connected to the PVD bus to provide the maximum isolation from noisy power and ground buses. Refer to the Application Information section for more information. 1, 6, 7, 10, 14, 18, 21, VD 25, 26, 34, 37 Power Supply Main power supply for analog and digital circuitry inside the IC. The data outputs and PLL are powered from separate buses for additional noise isolation. 56, 69, 79, 89, 98, 102, 112, 122 VDD Power Supply Power supply for digital data outputs. This voltage can be operated at voltages below the Main Power Supply, down to 2.5V, to provide convenient interfaces to lower voltage circuitry. 47, 48, 52 PVD Power Supply Phase Locked Loop Power Supply. This input should be well filtered, isolated, and decoupled, to provide a very stable, low noise, voltage source for the PLL and VCO circuitry in the ADCS9888. 3, 4, 11, 15, 19, 22, GND 27, 28, 35, 36, 40, 41, 46, 49, 51, 55, 65-68, 78, 88, 99-101, 111, 121, 128 Ground Ground Return. Ground return for all circuitry on the chip. For best performance, the printed circuit board should be designed using a single solid ground plane. Other ICs should be placed to minimize the effects of noisy digital ground returns interfering with the ADCS9888 operation. 39, 39 NC To ensure compliance with designs using the AD9888, these pins are not connected to the IC die. They may be physically connected to either VD or PVD with no effect on operation, performance, or reliability. Power Supply 6 NC Submit Documentation Feedback Copyright © 2000–2013, Texas Instruments Incorporated Product Folder Links: ADCS9888 OBSOLETE ADCS9888 www.ti.com SNAS203C – JAN 2000 – REVISED APRIL 2013 Absolute Maximum Ratings (1) (2) (3) Positive Supply Voltage (V+ = VD, PVD, VDD) With Respect to GND −0.3V to 5.5V Voltage on VSYNC, HSYNC Input Pin Input Current at any pin (4) Package Input Current 3.6V −0.3V to V+ +0.3V Voltage on Any Input or Output Pin ±25 mA (4) ±50 mA See (5) Package Dissipation at TA = 25°C ESD Susceptibility (6) Human Body Model 6500V Machine Model 250V Soldering Information See (7) Storage Temperature −65°C to +150°C (1) (2) (3) (4) (5) (6) (7) Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for which the device is functional, but do not ensure specific performance limits. For ensured specifications and test conditions, see the Electrical Characteristics. The ensured specifications apply only for the test conditions listed. Some performance characteristics may degrade when the device is not operated under the listed test conditions. All voltages are measured with respect to GND = 0 V, unless otherwise specified. If Military/Aerospace specified devices are required, please contact the Texas Instruments Sales Office/ Distributors for availability and specifications. When the input voltage (VIN) at any pin exceeds the power supplies (VIN < GND or VIN > VA or VD), the current at that pin should be limited to 25 mA. The 50 mA maximum package input current rating limits the number of pins that can simultaneously safely exceed the power supplies with an input current of 25 mA to two. The maximum power dissipation must be derated at elevated temperatures and is dictated by TJMAX, θJA and the ambient temperature, TA. The maximum allowable power dissipation at any temperature is PD = (TJMAX – TA)/θJA. TJMAX = 150°C for this device. The typical thermal resistance (θJA) of this part when board mounted is TBD °C/W for the NND0128A 128 pin QFP package. Human body model is 100 pF capacitor discharged through a 1.5 kΩ resistor. Machine model is 200 pF discharged through a 0 Ω resistor. Soldering process must comply with National Semiconductor's reflow temperature profile specifications. Refer to "www.ti.com/packaging". Operating Ratings (1) Operating Temperature Range TMIN ≤ TA ≤ TMAX ADCS9888CVH 0°C ≤ TA ≤ +70°C VD Supply Voltage +3.0V to +3.6V PVD Supply Voltage +3.0V to +3.6V VDD Supply Voltage +2.2V to +3.6V ≤100 mV (PVD or VDD)-VD, VD-PVD Analog Input Voltage Range −0.05 to VD + 0.05V Digital Input Voltage Range −0.05 to VD + 0.05V (1) All voltages are measured with respect to GND = 0 V, unless otherwise specified. Submit Documentation Feedback Copyright © 2000–2013, Texas Instruments Incorporated Product Folder Links: ADCS9888 7 OBSOLETE ADCS9888 SNAS203C – JAN 2000 – REVISED APRIL 2013 www.ti.com Electrical Characteristics The following specifications apply for GND = 0 V, VD = VDD = PVD = +3.3 VDC, ADC Clock = 205 MHz, unless otherwise specified. Boldface limits apply for TA = TMIN to TMAX; all other limits TA = 25°C. Symbol Parameter Conditions Min (1) Typical (2) Max (1) Units ANALOG VIDEO CHANNEL CHARACTERISTICS Resolution 8 Bits DC ACCURACY DNL Differential Non-Linearity Integral Non-Linearity Error (3) INL CODES No Missing Codes 140 MSPS +0.5 –0.4 +1.35 −1.0 170 MSPS +0.6 –0.5 +1.5 −1.0 205 MSPS +0.8 –0.6 +1.80 −1.0 140 MSPS +1.0 −0.7 +2.0 –2.0 170 MSPS +1.0 −0.9 +2.25 –2.25 205 MSPS +1.2 −1.0 +2.75 –2.75 25°C LSBs LSBs Guaranteed ANALOG INPUT CHARACTERISTICS VIN Input Voltage Range Minimum 25°C Input Voltage Range Maximum 0.5 VPP 1.0 Gain Tempco 25°C IIN Input Bias Current 25°C Full Temp. Range (4) 100 ppm/°C CIN Input Capacitance Full Temp. Range RIN Input Resistance Full Temp. Range (4) VOS Input Offset Voltage Full Temp. Range 12 105 mV Input Full-Scale Matching Full Temp. Range 1 9 %FS Offset Adjustment Range Full Temp. Range 41 49 57 %FS 1.15 1.225 1.30 V 1 2 3 μA pF 1 MΩ INTERNAL VOLTAGE REFERENCE CHARACTERISTICS VREF (1) (2) (3) (4) 8 Output Voltage Full Temp. Range Temperature Coefficient Full Temp. Range ±50 ppm/°C Test limits are specified to National's AOQL (Average Outgoing Quality Level). Typical figures are at TJ = TA = 25°C, with the ADC Clock at the stated speed, and represent most likely parametric norm. Full channel integral non-linearity error is defined as the deviation of the analog value, expressed in LSBs from the straight line that best fits the actual transfer function of the AFE. These values are specified by design and characterization testing. Submit Documentation Feedback Copyright © 2000–2013, Texas Instruments Incorporated Product Folder Links: ADCS9888 OBSOLETE ADCS9888 www.ti.com SNAS203C – JAN 2000 – REVISED APRIL 2013 AC Electrical Characteristics The following specifications apply for GND = 0 V, VD = VDD = PVD = +3.3 VDC, ADC Clock = 205 MHz, unless otherwise specified. Boldface limits apply for TA = TMIN to TMAX; all other limits TA = 25°C. Symbol Parameter Conditions Maximum Conversion Rate Full Temp. Range Minimum Conversion Rate Full Temp. Range (3) Data to Clock Skew Full Temp. Range Min (1) Typical (2) Max (1) 140 170 205 Units MSPS 10 MSPS 0.9 ns tBUFF Full Temp. Range 4.7 μs tSTAH Full Temp. Range 4.0 μs tDHO Full Temp. Range 0 μs tDAL Full Temp. Range 4.7 μs tDAH Full Temp. Range 4.0 μs tDSU Full Temp. Range 259 ns tSTASU Full Temp. Range 4.7 μs tSTOSU (1) (2) (3) μs Full Temp. Range 4.0 HSYNC Input Frequency Full Temp. Range 15 Maximum PLL Clock Rate Full Temp. Range 100/140 170 205 Minimum PLL Clock Rate Full Temp. Range PLL Jitter 25°C (3) 570 Sampling Phase Tempco Full Temp. Range (3) 15 110 kHz MHz 15 MHz 800 ps p-p ps/°C Test limits are specified to National's AOQL (Average Outgoing Quality Level). Typical figures are at TJ = TA = 25°C, with the ADC Clock at the stated speed, and represent most likely parametric norm. These values are specified by design and characterization testing. DC and Logic Electrical Characteristics The following specifications apply for GND = 0 V, VD = VDD = PVD = +3.3 VDC, ADC Clock = 205 MHz, unless otherwise specified. Boldface limits apply for TA = TMIN to TMAX; all other limits TA = 25°C. Symbol Parameter Conditions Min (1) Typical (2) Max (1) Units DIGITAL INPUT CHARACTERISTICS VIN(1) Logical “1” Output Voltage 2.5 V VIN(0) Logical “0” Output Voltage 0.8 V IIH Input Leakage Current See (3) −1.0 μA IIL Input Leakage Current See (3) 1.0 μA CIN Input Capacitance 3 pF DIGITAL OUTPUT CHARACTERISTICS VOUT(1) Logic “1” Output Voltage VOUT(0) Logic “0” Output Voltage Duty Cycle DATACK, DATACK_B VDD-0.1 See (3) 44 Output Coding V 49 0.1 V 55 % Binary POWER SUPPLY CHARACTERISTICS (1) (2) (3) VD Supply Voltage See (3) 3.0 3.3 3.6 V VDD Supply Voltage See (3) 2.2 3.3 3.6 V PVD Supply Voltage See (3) 3.0 3.3 3.6 V Test limits are specified to National's AOQL (Average Outgoing Quality Level). Typical figures are at TJ = TA = 25°C, with the ADC Clock at the stated speed, and represent most likely parametric norm. These values are specified by design and characterization testing. Submit Documentation Feedback Copyright © 2000–2013, Texas Instruments Incorporated Product Folder Links: ADCS9888 9 OBSOLETE ADCS9888 SNAS203C – JAN 2000 – REVISED APRIL 2013 www.ti.com DC and Logic Electrical Characteristics (continued) The following specifications apply for GND = 0 V, VD = VDD = PVD = +3.3 VDC, ADC Clock = 205 MHz, unless otherwise specified. Boldface limits apply for TA = TMIN to TMAX; all other limits TA = 25°C. Symbol ID Parameter Conditions Core Supply Current IDD (4) I/O Supply Current IPVD PLL Supply Current Total Power Dissipation (4) Min (1) Typical (2) 25°C - 140 MSPS 259 25°C - 170 MSPS 275 25°C - 205 MSPS 316 25°C - 140 MSPS 38 25°C - 170 MSPS 40 25°C - 205 MSPS 57 25°C - 140 MSPS 13 25°C - 170 MSPS 14 Max (1) Units mA mA mA 25°C - 205 MSPS 18 Full Temp. – 140 MSPS 320 365 Full Temp. – 170 MSPS 330 375 mA Full Temp. – 205 MSPS 390 420 Power Down Supply Current Full Temp. 8.4 15 mA Power Down Dissipation Full Temp. 28 50 mW The output supply current (IDD) includes the power required to drive a typical digital bus and load circuit at the stated test frequency. The actual output supply current will depend on the load capacitance of the printed circuit board and connected load device, and the operating frequency and output mode in the application. Analog Channel Characteristics The following specifications apply for GND = 0 V, VD = VDD = PVD = +3.3 VDC, VDD = +3.3 VDC, ADC Clock = 205 MHz, unless otherwise specified. Boldface limits apply for TA = TMIN to TMAX; all other limits TA = 25°C (1). Symbol SNR SNR Parameter Conditions Min (2) Typical (3) Max (2) Units Analog Bandwidth, Full Power 25°C 500 MHz Transient Response 25°C 2 ns Overvoltage Recovery Time 25°C 1.5 ns Signal to Noise Ratio (Without Harmonics) 25°C – 140 MSPS 40.7 44 dB 25°C –170 MSPS 40.7 43.5 25°C –205 MSPS 40.5 43.5 Signal to Noise Ratio (Without Harmonics) Crosstalk Full temp. – 140 MSPS 44 Full Temp. – 170 MSPS 43.5 Full Temp. – 205 MSPS 43.5 Full Temp. dB 50 dBc THERMAL CHARACTERISTICS θJC Junction to Case Thermal Resistance 12.3 °C/W θJA Junction to Ambient Thermal Resistance 30.2 °C/W (1) Two diodes clamp the OS analog inputs to AGND and VA as shown below. This input protection, in combination with the external clamp capacitor and the output impedance of the video source, prevents damage to the ADCS9888 from transients during power-up. VA TO INTERNAL CIRCUITRY VIDEO INPUT AGND (2) (3) 10 Test limits are specified to National's AOQL (Average Outgoing Quality Level). Typical figures are at TJ = TA = 25°C, with the ADC Clock at the stated speed, and represent most likely parametric norm. Submit Documentation Feedback Copyright © 2000–2013, Texas Instruments Incorporated Product Folder Links: ADCS9888 OBSOLETE ADCS9888 www.ti.com SNAS203C – JAN 2000 – REVISED APRIL 2013 TEST CIRCUIT DIAGRAMS Timing Diagrams RGBIN P0 P1 P3 P2 P4 P5 P6 P7 | HSYNC DATACK DOUTA D0 D1 D2 D3 D4 D5 D6 D7 | HSOUT Note 1) Absolute latency from HSYNC to HSOUT is not indicated or implied by this timing diagram. The latency may change by plus or minus one pixel period due to adjustments in the sampling phase register. The latency may also change by plus or minus one pixel period if the input signal is removed and reapplied, or if the ADCS9888 power is removed, and then reapplied, even if the same register settings are loaded. Note 2) Based upon the relationship of the input HSYNC to P0, the D0 pixel may arrive one pixel earlier or later than shown on the diagram. Figure 1. Single Channel Mode RGBIN P0 P1 P2 P3 P4 P5 P6 P7 | HSYNC DATACK D0 DOUTA D2 D4 D6 | HSOUT Note 1) Absolute latency from HSYNC to HSOUT is not indicated or implied by this timing diagram. The latency may change by plus or minus one pixel period due to adjustments in the sampling phase register. The latency may also change by plus or minus one pixel period if the input signal is removed and reapplied, or if the ADCS9888 power is removed, and then reapplied, even if the same register settings are loaded. Note 2) Based upon the relationship of the input HSYNC to P0, the D0 pixel may arrive one pixel earlier or later than shown on the diagram. Figure 2. Single Channel Mode - 2 Pixels per Clock (Even Pixels) Submit Documentation Feedback Copyright © 2000–2013, Texas Instruments Incorporated Product Folder Links: ADCS9888 11 OBSOLETE ADCS9888 SNAS203C – JAN 2000 – REVISED APRIL 2013 RGBIN www.ti.com P0 P1 P2 P3 P4 P5 P6 P7 | HSYNC DATACK DOUTA D1 D3 D7 D5 | HSOUT Note 1) Absolute latency from HSYNC to HSOUT is not indicated or implied by this timing diagram. The latency may change by plus or minus one pixel period due to adjustments in the sampling phase register. The latency may also change by plus or minus one pixel period if the input signal is removed and reapplied, or if the ADCS9888 power is removed, and then reapplied, even if the same register settings are loaded. Note 2) Based upon the relationship of the input HSYNC to P0, the D0 pixel may arrive one pixel earlier or later than shown on the diagram. Figure 3. Single Channel Mode - 2 Pixels per Clock (Odd Pixels) RGBIN P0 P1 P2 P3 P4 P5 P6 P7 | HSYNC DATACK D0 DOUTA DOUTB D4 D2 D1 D3 D6 D5 D7 | HSOUT Note 1) Absolute latency from HSYNC to HSOUT is not indicated or implied by this timing diagram. The latency may change by plus or minus one pixel period due to adjustments in the sampling phase register. The latency may also change by plus or minus one pixel period if the input signal is removed and reapplied, or if the ADCS9888 power is removed, and then reapplied, even if the same register settings are loaded. Note 2) Based upon the relationship of the input HSYNC to P0, the D0 pixel may arrive one pixel earlier or later than shown on the diagram. Note 3) If Register 15H, Bit 5 is set to 1, HSOUT transitions on the rising edge of DATACK instead of the falling edge. Figure 4. Dual Channel Mode - Interleaved Outputs 12 Submit Documentation Feedback Copyright © 2000–2013, Texas Instruments Incorporated Product Folder Links: ADCS9888 OBSOLETE ADCS9888 www.ti.com SNAS203C – JAN 2000 – REVISED APRIL 2013 RGBIN P0 P1 P2 P3 P4 P5 P6 P7 | HSYNC DATACK DOUTA D0 D2 D4 D6 DOUTB D1 D3 D5 D7 | HSOUT Note 1) Absolute latency from HSYNC to HSOUT is not indicated or implied by this timing diagram. The latency may change by plus or minus one pixel period due to adjustments in the sampling phase register. The latency may also change by plus or minus one pixel period if the input signal is removed and reapplied, or if the ADCS9888 power is removed, and then reapplied, even if the same register settings are loaded. Note 2) Based upon the relationship of the input HSYNC to P0, the D0 pixel may arrive one pixel earlier or later than shown on the diagram. Note 3) If Register 15H, Bit 5 is set to 1, HSOUT transitions on the rising edge of DATACK instead of the falling edge. Figure 5. Dual Channel Mode - Parallel Outputs RGBIN P0 P1 P2 P3 P4 P5 P6 P7 | HSYNC DATACK DOUTA D0 DOUTB D8 D4 D2 D6 D12 D10 D14 | HSOUT Note 1) Absolute latency from HSYNC to HSOUT is not indicated or implied by this timing diagram. The latency may change by plus or minus one pixel period due to adjustments in the sampling phase register. The latency may also change by plus or minus one pixel period if the input signal is removed and reapplied, or if the ADCS9888 power is removed, and then reapplied, even if the same register settings are loaded. Note 2) Based upon the relationship of the input HSYNC to P0, the D0 pixel may arrive one pixel earlier or later than shown on the diagram. Note 3) If Register 15H, Bit 5 is set to 1, HSOUT transitions on the rising edge of DATACK instead of the falling edge. Figure 6. Dual Channel Mode - Interleaved Outputs - 2 Pixels/Clock - Even Pixels Submit Documentation Feedback Copyright © 2000–2013, Texas Instruments Incorporated Product Folder Links: ADCS9888 13 OBSOLETE ADCS9888 SNAS203C – JAN 2000 – REVISED APRIL 2013 RGBIN www.ti.com P0 P1 P2 P3 P4 P5 P6 P7 | HSYNC DATACK D1 DOUTA D3 DOUTB D9 D5 D13 D11 D7 D15 | HSOUT Note 1) Absolute latency from HSYNC to HSOUT is not indicated or implied by this timing diagram. The latency may change by plus or minus one pixel period due to adjustments in the sampling phase register. The latency may also change by plus or minus one pixel period if the input signal is removed and reapplied, or if the ADCS9888 power is removed, and then reapplied, even if the same register settings are loaded. Note 2) Based upon the relationship of the input HSYNC to P0, the D0 pixel may arrive one pixel earlier or later than shown on the diagram. Note 3) If Register 15H, Bit 5 is set to 1, HSOUT transitions on the rising edge of DATACK instead of the falling edge. Figure 7. Dual Channel Mode - Interleaved Outputs - 2 Pixels/Clock - Odd Pixels RGBIN P0 P1 P2 P3 P4 P5 P6 P7 | HSYNC DATACK DOUTA D0 D4 D8 D12 DOUTB D2 D6 D10 D14 | HSOUT Note 1) Absolute latency from HSYNC to HSOUT is not indicated or implied by this timing diagram. The latency may change by plus or minus one pixel period due to adjustments in the sampling phase register. The latency may also change by plus or minus one pixel period if the input signal is removed and reapplied, or if the ADCS9888 power is removed, and then reapplied, even if the same register settings are loaded. Note 2) Based upon the relationship of the input HSYNC to P0, the D0 pixel may arrive one pixel earlier or later than shown on the diagram. Note 3) If Register 15H, Bit 5 is set to 1, HSOUT transitions on the rising edge of DATACK instead of the falling edge. Figure 8. Dual Channel Mode - Parallel Outputs - 2 Pixels/Clock - Even Pixels 14 Submit Documentation Feedback Copyright © 2000–2013, Texas Instruments Incorporated Product Folder Links: ADCS9888 OBSOLETE ADCS9888 www.ti.com SNAS203C – JAN 2000 – REVISED APRIL 2013 RGBIN P0 P1 P2 P3 P4 P5 P6 P7 | HSYNC DATACK DOUTA D1 D5 D9 D13 DOUTB D3 D7 D11 D15 | HSOUT Note 1) Absolute latency from HSYNC to HSOUT is not indicated or implied by this timing diagram. The latency may change by plus or minus one pixel period due to adjustments in the sampling phase register. The latency may also change by plus or minus one pixel period if the input signal is removed and reapplied, or if the ADCS9888 power is removed, and then reapplied, even if the same register settings are loaded. Note 2) Based upon the relationship of the input HSYNC to P0, the D0 pixel may arrive one pixel earlier or later than shown on the diagram. Note 3) If Register 15H, Bit 5 is set to 1, HSOUT transitions on the rising edge of DATACK instead of the falling edge. Figure 9. Dual Channel Mode - Parallel Outputs - 2 Pixels/Clock - Odd Pixels RGBIN P0 P1 P2 P3 P4 P5 P6 P7 | HSYNC DATACK GOUTA Y0 Y1 Y2 Y3 Y4 Y5 Y6 Y7 ROUTA U0 V0 U2 V2 U4 V4 U6 V6 | HSOUT Note 1) Absolute latency from HSYNC to HSOUT is not indicated or implied by this timing diagram. The latency may change by plus or minus one pixel period due to adjustments in the sampling phase register. The latency may also change by plus or minus one pixel period if the input signal is removed and reapplied, or if the ADCS9888 power is removed, and then reapplied, even if the same register settings are loaded. Note 2) Based upon the relationship of the input HSYNC to P0, the D0 pixel may arrive one pixel earlier or later than shown on the diagram. Figure 10. 4:2:2 Output Mode Submit Documentation Feedback Copyright © 2000–2013, Texas Instruments Incorporated Product Folder Links: ADCS9888 15 OBSOLETE ADCS9888 SNAS203C – JAN 2000 – REVISED APRIL 2013 www.ti.com tPER tDCYCLE DATACK DATACK tSKEW tSKEW DOUT HSOUT Figure 11. Data Output Timing SDA tBUFF tDSU tDHO tSTAH tSTOSU tSTASU tDAL SCL tDAH Figure 12. Configuration Register Serial Timing SDA BIT7 BIT6 BIT5 BIT4 BIT3 BIT2 BIT0 BIT1 ACK SCL Figure 13. Serial Interface Protocol Configuration Register Descriptions Address (Hex) Write/Read or Read Only Bits POR Value 00H RO 7:0 Revision 01H W/R 7:0 02H W/R 7:4 16 Name Bit Name/Description Chip Revision 8 bit value that indicates the silicon version. 00000000 = Rev. 0 01101001 PLL Divisor MSB The upper 8 MSBs of the 12 bit PLL divider value. Larger divisors cause the PLL to generate a higher frequency clock. This register should be loaded first, then register 02H, whenever the divider is changed. The PLL divider value is only updated when the LSB value in register 02H is updated. The actual PLL divider value = (PLL register value + 1), so setting a value of 1055d in registers 01H and 02H will result in a divide value of 1056. 1101**** PLL Divisor LSB Lower 4 LSBs of the 12 bit PLL divisor value. See register 01H. Submit Documentation Feedback Copyright © 2000–2013, Texas Instruments Incorporated Product Folder Links: ADCS9888 OBSOLETE ADCS9888 www.ti.com SNAS203C – JAN 2000 – REVISED APRIL 2013 Address (Hex) Write/Read or Read Only Bits POR Value 03H W/R 7:6 01****** 5:3 **001*** Name Bit Name/Description VCO RNG/CPMP Sets the VCO frequency range for the desired pixel rate. 00 = 15 - 41 MHz 01 = 41 - 82 MHz 10 = 82 - 150 MHz 11 = 150+ MHz Sets the VCO charge pump current for the desired pixel rate. 000 = 50 μA 001 = 100 μA 010 = 150 μA 011 = 250 μA 100 = 350 μA 101 = 500 μA 110 = 750 μA 111 = 1500 μA 04H W/R 7:3 10000*** Sample Phase Adjust 5 bit value that adjusts the ADC sample timing relative to HSYNC. LSB = 1/32 of one pixel period or 11.25 degrees of phase. The power up default value is 16D. 05H W/R 7:0 00001000 Clamp Placement Sets the Clamp starting point N pixel periods after the trailing edge of the Hsync signal. Settings from 1 to 255 are legal values for Clamp Placement. DO NOT SET = 0. 06H W/R 7:0 00010100 Clamp Duration Sets the Clamp duration to N pixel periods. Settings from 1 to 255 are legal values. DO NOT SET = 0. 07H W/R 7:0 00100000 HSOUT Pulsewidth Sets the number of pixel periods that HSOUT is active. The leading edge of HSOUT is set by an internally generated phase-adjusted PLL output. The chip then counts the number of pixel periods set by HSOUT Pulsewidth and triggers the trailing edge of HSOUT. 08H W/R 7:0 10000000 Red Gain 09H W/R 7:0 10000000 Green Gain 0AH W/R 7:0 10000000 Blue Gain Controls the ADC input range for the RGB video inputs. Default setting provides a nominal signal range of 0.7 VPP. Higher settings increase the signal range up to 1.0 VPP typ. Lower settings reduce the signal range to a minimum of 0.5 VPP typ. 0BH W/R 7:1 1000000* Red Offset OCH W/R 7:1 1000000* Green Offset ODH W/R 7:1 1000000* Blue Offset OEH W/R 7 0******* 6 *1****** Hsync Input Polarity. 0 = active low, 1 = active high. 5 **0***** Hsync Output Polarity. 0 = logic high HSOUT, 1 = logic low HSOUT. 4 ***0**** Active Hsync Override. 1 = Hsync source determined by user setting in Register 0EH, bit 3. 0 = determined by chip results in Register 14H, bit 6. 3 ****0*** Active Hsync Select. 0 = HSYNC input is Hsync source. 1 = output of SOGIN sync slicer is Hsync source. This bit only takes effect if Register 0EH bit 4 is 1, or if both Hsync sources are active. 2 *****0** Vsync Output Invert. 0 = inverted. 1 = not inverted. 1 ******0* Active Vsync Override. 1 = source determined by user setting in Register 0EH, bit 0. 0 = source determined by chip results in Register 14H, bit 3. 0 *******0 Active Vsync Select. 0 = VSYNC input is Vsync source. 1 = Sync separator output is Vsync source. This bit only has effect if Register 0EH, bit 1 = 1. Sync Control Controls the DC offset correction prior to analog to digital conversion. Default setting is for no offset. Settings higher than 10H make resulting image less bright, settings lower than 10H makes image more bright. Absolute offset amount is also dependent on setting of corresponding gain channel. See description of Offset/Gain functions for more information. Hsync Polarity Override. 0 = polarity determined by chip, 1 = polarity set by Register 0EH, bit 6. Submit Documentation Feedback Copyright © 2000–2013, Texas Instruments Incorporated Product Folder Links: ADCS9888 17 OBSOLETE ADCS9888 SNAS203C – JAN 2000 – REVISED APRIL 2013 www.ti.com Address (Hex) Write/Read or Read Only Bits POR Value 0FH W/R 7 0******* 6 *1****** 5 **0***** 4 ***0**** COAST Polarity Override. 0 = determined by chip. 1 = determined by Register 0FH, bit 3. 3 ****1*** COAST Polarity. 0 = active low, 1 = active high. This bit only has an effect when Register 0FH, bit 5 = 0, and Register 0FH bit 4 = 1. 2 *****1** Seek Override Seek Mode Override. 0 = don’t allow low power mode. 1 = allow low power mode when sync inputs inactive. In seek mode operation the HSOUT, VSOUT, DATACK and DATACK, and all 48 data outputs are placed in a high impedance state. The SOGOUT pin is still active. The voltage references, sync detection and processing, and serial register sub-system (for obvious reasons) are maintained in an active state to provide a rapid transition to normal operation. 1 ******1* PWRDN Full chip power down. 0 = power down. 1 = normal operation. In power down mode, the HSOUT, VSOUT, DATACK, DATACK, and all 48 data outputs are placed in a high impedance state. The SOGOUT pin is still active. The voltage reference, sync detection and processing, and serial register sub-system (for obvious reasons) are maintained in an active state to provide a rapid transition to normal operation. 7:3 01111*** Sync-On-Green Threshold Set the voltage of the sync slicer threshold. 00H to 1FH. LSB size is 10 mV. Setting of 00h gives a nominal threshold of 10 mV, while maximum setting of 1FH gives a nominal threshold of 330 mV. Optimal settings will be lower than those used with the Analog Devices AD9888. 2 *****0** Red Clamp Select 0 = clamp to ground. 1 = clamp to RMIDSCV. 1 ******0* Blue Clamp Select 0 = clamp to ground. 1 = clamp to BMIDSCV. 10H 18 W/R Name Clamp Control Bit Name/Description Clamp Select. 0 = clamp timing determined by internal chip counters derived from hsync. 1 = clamp timing determined by external CLAMP signal. CLAMP Polarity. 0 active high, 1 = active low. This bit only has effect if Register 0FH, bit 7 = 1. COAST Control COAST Select. 0 = COAST input pin is PLL coast source. 1 = VSYNC is PLL coast source. 11H W/R 7:0 00100000 Sync Separator Threshold Sets how many internal 5 MHz clock periods the sync separator will count to before toggling high or low. This value should be set to some amount greater than the widest expected hsync or equalization pulse width. 12H W/R 7:0 00000000 Pre-coast Sets the number of Hsync periods that the PLL coast becomes active prior to Vsync. This setting is only valid when Vsync is used as the PLL coast source. 13H W/R 7:0 00000000 Post-Coast Sets the number of Hsync periods that the PLL coast stays active after Vsync becomes inactive. This setting is only valid when Vsync is used as the PLL coast source. Submit Documentation Feedback Copyright © 2000–2013, Texas Instruments Incorporated Product Folder Links: ADCS9888 OBSOLETE ADCS9888 www.ti.com SNAS203C – JAN 2000 – REVISED APRIL 2013 Address (Hex) Write/Read or Read Only Bits 14H RO 7 15H W/R POR Value Name Sync Detect Status Bit Name/Description Hsync Detect. 1 = activity is detected on the HSYNC input pin. 0 = no activity detected. 6 AHS - Active Hsync Select. The bit indicates which Hsync source will automatically be used by the chip. 0 = HSYNC input pin. 1 = output of sync slicer. This can be overridden by asserting the Active Hsync Override bit at Register 0EH, bit 4 and setting the Hsync source at Register 0EH, bit 3. 5 Input Hsync Polarity Detect. 0 = active low. 1 = active high. 4 Vsync Detect. 1 = activity is detected on the VSYNC input pin. 0 = no activity detected. 3 AVS - Active Vsync Select. This bit indicates which Vsync source will automatically be used by the chip. 0 = VSYNC input pin. 1 = output of sync separator. This can be overridden by asserting the Active Vsync Override bit at Register 0EH, bit 1 and setting the Vsync source at Register 0EH, bit 0. 2 VSOUT Polarity Detect. 0 = active high, 1 = active low. 1 SOGIN Activity Detect. This bit indicates if there is activity at the output of the sync slicer. 0 = no activity. 1 = activity detected. 0 Coast Polarity Detect. This bit indicates the polarity of the signal being applied to the PLL coast function. 0 = active low, 1 = active high. 7 1******* Channel Mode Sets the channel mode of the data outputs. 0 = single channel mode. 1 = dual channel mode. In dual channel mode, the DATACK output clocks operate at 1/2 of the pixel conversion rate, and pixel data is updated on the A and B output ports. See also Register 15H, bit 6. 6 *1****** Output Mode Sets the output mode of the data outputs. 0 = interleaved mode, 1 = parallel mode. In interleaved mode, one output port is updated on the rising edge of DATACK, the other output port is updated on the falling edge of DATACK. 5 **0***** A/B Even/Odd When this bit is set to 1, HSOUT transitions on the rising edge of DATACK. (Instead of the falling edge as shown in the timing diagrams). 4 ***0**** 4:2:2 Output Mode Selects 4:2:2 subsampled output formatting mode, for use with YUV type video signals. 0 = normal output formatting, 1 = 4:2:2 output formatting. In YUV 4:2:2 mode, the channel connections and data output are as follows: Input Signal Output Red Channel V U/V Green Y Y Blue U High Z 3 ****0*** Input Mux Selects which video input source is used. 0 = port 0, 1 = port 1. 2:1 *****11* Input Bandwidth Sets the analog input bandwidth. 11 = 500 MHz 10 = 300 MHz 01 = 150 MHz 00 = 75 MHz 0 *******0 External Clock Determines whether the internal Hsync referenced PLL is used as the clock source, or the CKEXT source is used. 0 = internal PLL. 1 = CKEXT is used. 16H W/R 7:0 11111111 Test Register 17H W/R 7:0 00000000 Test Register 18H RO 7:0 Test Register 19H RO 7:0 Test Register Submit Documentation Feedback Copyright © 2000–2013, Texas Instruments Incorporated Product Folder Links: ADCS9888 19 OBSOLETE ADCS9888 SNAS203C – JAN 2000 – REVISED APRIL 2013 www.ti.com Application Information 1.0 INTRODUCTION The ADCS9888 is a complete 8 bit, 205 MSPS monolithic analog front end for capturing analog component video in digital video applications. The high sampling rate allows it to support video capture at full frame rate at resolutions up to 1600 by 1200 at 75 Hz. Higher resolution (and therefore pixel rate) video can be captured by subsampling even and odd columns (pixels) of video on alternating frames. This highly integrated solution incorporates all of the functions necessary to convert standard computer video signals into digital output data suitable for acquisition by video scaler and similar processing systems. Included components are a 2 channel mux to allow 2 independent video sources to be selected. A full sync processing and clock generation system is included to generate the sampling pixel clock based on the horizontal synchronization signal. 3 inputs with 500 MHz bandwidth are used to capture component RGB or YUV video data. Video clamp circuitry is included to provide the proper AC coupling and black level restoration required in this application. Video is captured at up to 205 MSPS by 8 bit analog to digital converters, and output to a highly flexible output interface. Data can be output on a single 8 bit parallel output per channel, or on dual 8 bit parallel interfaces for each color channel for the higher pixel rate settings. A variety of different output formats are supported to ensure flexible interfacing to a variety of video processing solutions. 2.0 VIDEO SIGNAL PATH 2.1 Input Muxes The ADCS9888 supports two complete video input channels #0 and #1. This allows two sources of video input to be used for dual input panels, monitors and projectors. All analog video signals and sync signals are muxed. 2.2 Input Termination Video input signals are normally received from 75Ω sources. In this case, the signal path should be properly impedance matched through the incoming connectors, and across the printed circuit board up to the video inputs on the ADCS9888. The signal traces should be designed for the proper characteristic impedance, and should be continuous traces that stay on the same side of the printed circuit board, avoiding vias and sharp bends in the trace that can introduce impedance discontinuities. The 75Ω/47 nF termination network shown should be located as close as possible to the video input pins to minimize unmatched stub impedances and resulting signal distortion. The 75Ω termination resistance should be connected to the system ground plane using a via directly to the plane. 47nF RAIN RGB INPUT GAIN BAIN 75: 2.3 Video Input Clamp The analog video inputs will be AC coupled using 47 nF capacitors. Clamping on the inputs is done to ensure the proper DC level of the converted signals. Red, Green and Blue channels will normally be clamped to the zero scale level of the ADC when a black level signal is present on the inputs. This normally happens during the back porch period of the horizontal blanking interval. Register controlled options allow the Red and Blue channels to be clamped to the ADC mid scale point. This allows YUV signal processing where the U and V channels are at a mid scale voltage during “Black”. 47nF RED VIDEO RAIN 47nF BLUE VIDEO BAIN 47nF GREEN VIDEO ADCS9888 GAIN 1nF SOGIN 20 Submit Documentation Feedback Copyright © 2000–2013, Texas Instruments Incorporated Product Folder Links: ADCS9888 OBSOLETE ADCS9888 www.ti.com SNAS203C – JAN 2000 – REVISED APRIL 2013 2.4 Gain/Offset Adjustment Gain and Offset adjustment is provided to support video signal ranges of 0.5 Vp-p to 1.0 Vp-p. When the 8 bit Gain registers are set to the maximum value, the signal range is largest at 1.0 Vp-p typical. When the Gain registers are set to the minimum values of 00h, the signal range is smallest at 0.5 Vp-p. This means that for a given video input signal, maximum settings of Gain will reduce the contrast or range of the converted data, while minimum settings of Gain will increase the contrast or range of the converted data. The "power on defalt" values for Gain are 80h which give a nominal input range of 0.7 Vp-p. The 7 bit Offset registers provide a ±63 step adjustment. High values of Offset will lower the value of the converted output data, low values of Offset setting will increase the value of the converted output data. As the Gain and Offset adjustments cause the ADC reference voltages to change, they also cause shifts in the RMIDSCV and BMIDSCV voltages. 2.5 Analog To Digital Converter Three 8 bit, 205 MSPS analog to digital converters are included. One for each video input channel. 2.6 Output Data Ports Two 8 bit data ports are provided at the output of each video color channel. This allows a variety of different video output formats for ease of processing by the attached video scaler/processor used in different applications. Supported modes include: • Single channel mode, where all data is present on the A output port for each color channel. • Parallel Dual Channel mode, where data is presented on A and B outputs simultaneously, updated at one half the pixel conversion rate. • Interleaved Dual Channel mode, where data is presented alternately on A and B outputs one new sample with each incoming pixel clock. • In both Dual Channel modes, the output data sequence can be altered to provide all Odd pixels on Port B or on Port A, controlled by Bit 5 of Register 15h. The timing relationship between the data outputs, output clocks, and HSOUT are all synchronized. When the sample phase is adjusted, all of these digital outputs will be shifted together with respect to the source Hsync signal. In dual channel output modes, if Register 15H, Bit 5 is set to one, then HSOUT will transition on the rising edge of DATACK instead of the falling edge as shown in the timing diagrams. All DATA and DATACK outputs are placed in high impedance tri-state mode when the chip is in power down. No pull-up or pull-down features are present in the high impedance state. Refer to the specific sections regarding the other logic outputs for their configuration during power down or low power modes of chip operation. 2.6.1 Output Termination All data and timing outputs are high speed CMOS drivers and should be properly terminated to reduce EMI and optimize signal integrity. Each output should have a series terminating resistor located as close to the output pin as possible. The value of the terminating resistor is dependant on the printed circuit board trace impedance. The optimum performance will be when the output impedance of the chip plus the terminating resistor is equal to the characteristic impedance of the printed circuit board trace. Typical output impedance of the ADCS9888 SOGOUT, DATACK and DATACKB is around 30Ω, while the HSOUT, VSOUT and DATA are 90Ω. So for a 150Ω trace impedance, the optimum terminating resistor values would be 120Ω and 60Ω respectively. OUTPUT LOAD RTERM PCB TRACE ZOUTPUT + RTERM = ZTRACE Submit Documentation Feedback Copyright © 2000–2013, Texas Instruments Incorporated Product Folder Links: ADCS9888 21 OBSOLETE ADCS9888 SNAS203C – JAN 2000 – REVISED APRIL 2013 www.ti.com 3.0 SYNC INPUTS AND PROCESSING SYNC SLICER ACTIVITY DETECT SOGIN0 MUX5 NEGATIVE PEAK CLAMP + - SOGIN1 COMP SYNC SYNC SEPARATOR MUX1 INTEGRATOR VSYNC 1/S MUX5 SOGOUT HSYNC0 HSYNC1 ACTIVITY DETECT MUX2 POLARITY DETECT HSOUT CKINV CKEXT PLL AND CLOCK GENERATOR MUX3 PIXEL CLOCK COAST MUX5 ACTIVITY DETECT VSYNC0 POLARITY DETECT POLARITY DETECT MUX4 VSOUT VSYNC1 3.1 SYNC On Green Input The Sync-On-Green input is provided to support applications where separate TTL Hsync and Vsync inputs are not provided. In these applications, the composite sync information is provided on the Green video signal. The SOG input accepts an AC coupled version of the green input signal. This signal is clamped, and then further processed to extract the horizontal and vertical sync signals. 3.1.1 Sync Slicer The Sync Slicer is an adjustable clamp/comparator. First the input is clamped so that the most negative voltage is set to equal an internal reference voltage. This clamped signal is then fed into a 5 bit adjustable comparator to provide a logic level signal with the analog video data removed and only the sync signals remaining. The default comparator setting is 160 mV above the reference voltage. Adjustment increments are in 10 mV intervals with a resulting comparator range from 10 mV to 330 mV. Optimal settings will be lower than those used with the Analog Devices AD9888. The recommended starting value is a setting of 01111b, but the best setting is dependent on amplitude of the input video signal and synchronizing pulse. The Sync Slicer output has the same polarity as the input signal. “Normal” video with white positive and black negative will produce sync pulses that are active low. Normal synchronization signals will be mainly high with pulses going low. The Sync Slicer circuit will provide an active logic output from many signals which do not have sync on green present. Video with no Sync On Green signal present will still cause the output of the Sync Slicer circuit to toggle. The timing of this output will be much different than that caused by a signal where Sync On Green information is included. In addition, when no Sync On Green information is present, timing will always be provided on the VSYNC and/or HSYNC timing inputs. 3.1.2 Sync on Green Activity Detect The SOGIN activity detect circuit detects the absence or presence of a signal at the output of the Sync Slicer. The result of this detection is sent to Register 14h, Bit 1. (1 = Active, 0 = Inactive) 22 Submit Documentation Feedback Copyright © 2000–2013, Texas Instruments Incorporated Product Folder Links: ADCS9888 OBSOLETE ADCS9888 www.ti.com SNAS203C – JAN 2000 – REVISED APRIL 2013 3.2 HSYNC Input In most computer video applications, a TTL horizontal sync pulse is output by the graphics card. This TTL signal is connected to the ADCS9888 HSYNC input. In other applications a TTL composite sync signal may be used. To support this, the composite sync signal from the HSYNC input can be processed by the Sync Separator circuit to generate a Vsync signal. Either Hsync signal (from HSYNC input or from SOGIN via the Sync Slicer) can be used as the reference clock for the PLL in the clock generation block. 3.2.1 HSYNC Activity Detect The HSYNC activity detect circuit detects the absence or presence of an HSYNC input signal. The result of this detection is sent to Register 14h, Bit 7. (1 = Active, 0 = Inactive) 3.2.2 AHS - Active HSYNC Selection The Clock Generator will use either the HSYNC input, or the output from the Sync Slicer as the reference for the PLL. The AHS performs an automatic selection of the PLL reference source based on the following table: Reg. 14h Bit 7 Hsync Detect Reg. 14h Bit 1 SOG Detect Reb. 0Eh Bit 4 Override AHS Output 0 0 0 0 – use HSYNC 0 1 0 1 – use SOG 1 0 0 0 – use HSYNC 1 1 0 0Eh, Bit 3 X X 1 0Eh, Bit 3 3.2.3 Hsync Polarity Detection The Hsync signal input to the Clock Generator can be an active high or active low signal. A polarity detection circuit is used to detect the state of the Hsync signal. Signals that are mostly low with pulses high will be reported as active high or positive, while signals that are mostly high with pulses low will be reported as active low or negative. The results of this detection are reported in Register 14h, Bit 5. (0 = Negative, 1 = Positive). Regardless of the polarity of the Hsync signal at the detector, an automatic polarity correction circuit is used to ensure that the proper polarity signal is used to drive the PLL reference clock input. 3.3 SYNC Separator Either the SOGIN or HSYNC signals can have a composite sync signal as the input. MUX1 is used to feed this composite sync from either source into the sync separator. The sync separator is a digital low pass filter that has an adjustable number of clock ticks from 0 to 255. The default setting is 32 ticks. This filter rejects changes in the composite sync signal that are shorter than the period set. Thus, only long duration changes in the digital composite sync signal, i.e. the vertical sync pulse, are allowed to pass through. The separator uses an internal clock with a nominal frequency of 5 MHz as the filter timebase. 3.4 VSYNC Input The VSYNC input accepts a TTL vertical sync pulse provided by the video source. This signal or the vertical sync signal output by the Sync Separator can be used to control the Coast function in the clock generation circuitry. 3.4.1 Vsync Activity Detect The Vsync activity detect circuit detects the absence or presence of a Vsync input signal. The result of this detection is sent to Register 14h, Bit 4. (1 = Active, 0 = Inactive). 3.4.2 Vsync Polarity Detect The Vsync signal can be an active high or active low signal. A polarity detection circuit is used to detect the active state. The polarity is determined by observing the high/low duty cycle of the VSOUT signal to determine whether the signal is mostly high or mostly low. If the signal is mostly low, then the polarity is set as Positive. If the signal is mostly high, then the polarity is set to Negative. (0 = Negative, 1 = Positive) The results of this detection are sent to Register 14h, Bit 2. Submit Documentation Feedback Copyright © 2000–2013, Texas Instruments Incorporated Product Folder Links: ADCS9888 23 OBSOLETE ADCS9888 SNAS203C – JAN 2000 – REVISED APRIL 2013 www.ti.com 3.4.3 AVS - Active Vsync Detection There are two possible signal sources for VSOUT. The Vsync input can be used, or the output of the SYNC SEPARATOR can be used. The AVS automatically selects the source for VSOUT based on the results and settings described in the following table. Reg. 14h Bit 4 Vsync Detect Reg. 14h Bit 1 SOG Detect Reg. 0Eh Bit 1 Override AHS Output 0 0 0 Reg 0Eh, Bit 0 0 1 0 1 – use SOG 1 0 0 0 – use VSYNC 1 1 0 0 – use VSYNC X X 1 Reg 0Eh, Bit 0 4.0 CLOCK GENERATION The PLL clock generator provides a high frequency pixel clock that is phase aligned to the horizontal sync signal. The horizontal sync signal can be provided by the HSYNC input, or the output of the sync slicer circuit. The pixel clock is used as the timing source for the analog to digital conversion and data output processing in the IC. 4.1 PLL The PLL generates a high frequency pixel clock that is frequency locked and phase aligned to the horizontal sync signal. The main controls for the PLL are as described in the following subsections. 4.1.1 PLL Divider The PLL divider is a 12 bit counter with an adjustment range of 17 to 4096. The divider setting is configured in registers 01h, and 02h. The actual divider value used is the divider register setting + 1, so loading a value of 1055 decimal results in a divider of 1056. The PLL divider value sets the number of pixel periods per line. This value consists of the active video pixels, plus the horizontal blanking overhead. The overhead is typically 20 to 30% of the total line time. VESA (Video Equipment Standards Association) has established a series of standards for the different computer video settings (resolution and frame rate). These can be used to determine the proper settings of the PLL divider for many applications. Some applications will use non-standard video timings. In these cases, more advanced methods will be required to determine the proper divider setting to use. The power up default value of the PLL divide registers is 1693d for a real divider setting of 1694d. 4.1.2 VCO Filter Circuit The Voltage Controlled Oscillator uses an external filter circuit to smooth the charge pump current pulses, and optimize the VCO performance. This circuit connects between the FILT pin and PVD power bus. The filter circuit, and the PVD power must be well isolated from other circuitry to achieve the best PLL performance and low jitter. 3.3V 3.9nF 39nF PVD 3.3k: ADCS9888 FILT 24 Submit Documentation Feedback Copyright © 2000–2013, Texas Instruments Incorporated Product Folder Links: ADCS9888 OBSOLETE ADCS9888 www.ti.com SNAS203C – JAN 2000 – REVISED APRIL 2013 4.1.3 VCO Frequency Range Control The VCO frequency range setting selects the gain of the VCO. By optimizing the gain, the VCO performance can be optimized for different operating frequency ranges. The value is set via the two most significant bits of register 03h. PV1 PV0 Pixel Clock Range (MHz) 0 0 15-41 31 KVCO Gain (MHz/V) 0 1 41-82 61 1 0 82-150 122 1 1 >150 200 4.1.4 VCO Charge Pump Current Control The PLL charge pump current can be set to different values to help optimize the performance for different frequency ranges of operation. The value is set via bits 5:3 of Register 03h. IP2 IP1 IP0 0 0 0 50 Charge Pump Current (μA) 0 0 1 100 0 1 0 150 0 1 1 250 1 0 0 350 1 0 1 500 1 1 0 750 1 1 1 1500 The VCO charge pump current can be calculated using the following equation, and the values for Kvco from the table in the previous section. Ip = [(HsyncFreq x 2 x π )/19.2]^2 x [(Ct x N)/Kvco)] where • • • • • • • Ip = Target Charge Pump current. Round this value up to the next highest available setting HsyncFreq = Frequency of Hsync reference clock π = 3.1415927 (approximately) 19.2 = The PLL stability ratio for the ADCS9888 Ct = Loop filter capacitance N = PLL divider value (register setting in 04h, 05h +1) Kvco = VCO gain in MHz/V (1) 4.1.5 PLL Coast The PLL clock generator provides a high frequency pixel clock that is phase aligned to the horizontal sync signal. During portions of the video signal, this horizontal sync signal may be absent or may have a frequency that is different than the "normal" frequency. During these times, application of the coast signal to the PLL causes it to maintain its current operating frequency and phase (according to the voltage held on the VCO filter capacitor) and “coast”, without attempting to synchronize with the horizontal sync waveform. When the coast signal is deasserted, the PLL will again try to phase lock with the horizontal sync input. In most applications, the coast signal is derived from the vertical synchronization pulse from the VSYNC input or from one of the composite sync sources (either SOGIN or HSYNC) after being processed in the sync separator. The COAST input allows the user to provide a separate external coast control signal. Register 0Fh, bit 5 is used to select which source is used. Submit Documentation Feedback Copyright © 2000–2013, Texas Instruments Incorporated Product Folder Links: ADCS9888 25 OBSOLETE ADCS9888 SNAS203C – JAN 2000 – REVISED APRIL 2013 www.ti.com 4.1.6 Pre-Coast and Post-Coast When Vsync is used as the coast source, the coast signal can be extended earlier and later by setting the PreCoast and Post-Coast settings in Registers 12h and 13h. This feature requires the chip to calculate the number of Hsync pulses (lines) per Vsync (frame). An 11 bit counter is provided to support frame sizes up to 2048 lines (active lines plus vertical blanking overhead). Once the frame size has been calculated, the chip will anticipate when the next VSYNC begins, and the coast signal can be generated up to 255 lines earlier than the anticipated Vsync. Similarly, the Post-coast setting allows the PLL coast signal to be maintained as many as 255 lines following the de-assertion of Vsync. 4.1.7 Coast Polarity Detection The coast signal input to the Clock Generator can be an active high or active low signal. A polarity detection circuit determines the polarity of the Coast signal. The polarity is determined by observing the high/low duty cycle of the COAST signal to determine whether the signal is mostly high or mostly low. If the signal is mostly low, then the polarity is set as Positive. If the signal is mostly high, then the polarity is set to Negative. (0 = Negative, 1 = Positive) The results of this detection are sent to Register 14h, Bit 0. Table 1. Clock Generation Setting Mode Resolution (Pixel/Lines) Refresh Rate Hz HSYNC Frequency kHz Pixel Rate MHz VCO RNGE VCO CPMP PLL DIV Setting VGA 640 x 480 60 31.5 25.175 00 010 799 72 37.7 31.500 00 011 831 75 37.5 31.500 00 011 839 85 43.3 36.000 00 011 831 56 35.1 36.000 00 011 1023 60 37.9 40.000 00 011 1055 72 48.1 50.000 01 011 1039 75 46.9 49.500 01 011 1055 85 53.7 56.250 01 011 1047 60 48.4 65.000 01 011 1343 70 56.5 75.000 01 100 1327 75 60.0 78.750 01 100 1311 80 64.0 85.500 10 011 1335 85 68.3 94.500 10 011 1375 60 64.0 108.000 10 011 1687 75 80.0 135.000 10 101 1687 85 91.1 157.500 11 100 1727 60 75.0 162.000 11 100 2159 65 81.3 175.500 11 100 2159 70 87.5 189.000 11 100 2159 75 93.8 202.500 11 101 2159 85 106.3 229.500 * 10 101 1079 SVGA XGA SXGA UXGA 800 x 600 1024 x 768 1280 x 1024 1600 x 1200 NOTE * Alternate pixel sampling mode. See 4.2.1 CKINV Input 4.2 Pixel Clock Generation And Timing AdjustmenT Several features are provided that are related to the pixel clock timing. These include: • Clock Phase Adjust • CKINV - This is discussed in more detail in the next section, “CKINV Input”. • Clamp Placement setting 26 Submit Documentation Feedback Copyright © 2000–2013, Texas Instruments Incorporated Product Folder Links: ADCS9888 OBSOLETE ADCS9888 www.ti.com • SNAS203C – JAN 2000 – REVISED APRIL 2013 Clamp Duration setting Please refer to Configuration Register Descriptions for more details on these adjustments. 4.2.1 CKINV Input This is a digital input that causes the ADC sampling clock to be inverted. In effect, this causes an additional 180 degrees of phase shift in the ADC sampling point. This input is used in support of Alternate Pixel Sampling mode, which allows higher frequency video signals to be captured. In this mode, only every second pixel is sampled and converted. This is easily achieved by setting the PLL divider value to achieve one half of the true video pixel rate. On one video frame, all odd video pixels will be converted and sent to the video processor. On the next video frame, the state of CKINV will be inverted, and all even pixels will be converted and output. Frame re-assembly and display will be performed by the video scaler or other video processing system. This input should only change state during the vertical blanking interval, as it may produce several samples of corrupted ADC data during the phase shift. This input should be connected to ground when not in use. 4.2.2 CKEXT Input While most applications will use the built in PLL to generate a pixel clock, in some cases, the user will drive the CKEXT input with an external pixel clock source. In these applications, the PLL is not used and will be placed in a minimum power state. The ADC Sample Phase adjustment is available when CKEXT is used. 5.0 TIMING OUTPUTS 5.1 SOGOUT This pin outputs either the output from the sync slicer, or a delayed but unprocessed version of the HSYNC input. The signal at SOGOUT is the same polarity as the input signal. 5.2 HSOUT This pin outputs a reconstructed and phase aligned version of the HSYNC input. Both the polarity and duration of this signal are controlled via register settings. 5.3 VSOUT This pin outputs a delayed but unprocessed (except for selectable inversion via register 0Eh, bit 3) version of the vertical sync signal. This signal can be selected from either the VSYNC input, or the output of the Sync Separator. 5.4 DATACK/DATACKB These pins provide a complementary output pixel clock that will be used to capture the digital data and HSOUT into the connected digital logic. The output frequency of the clock is dependent on the data output mode being used. Refer to the description for register 15h. 6.0 CONFIGURATION REGISTERS All device settings are controlled via the configuration registers. These registers are accessed via a serial control bus which consists of 3 inputs/outputs (Serial Data, Serial Clock and A0). 6.1 Serial Control Interface The serial control interface consists of a bi-directional Data line and an input only Clock line. All clock information is controlled by the Master or Host device, which will usually be a microcontroller or microprocessor. The data line will be driven by the Master or Host during the control/address portions of the protocol. Data portions of the transfer can be driven by either the Master or the ADCS9888, depending on the direction of data flow. The two bus lines will have pullup resistors to a power supply bus, and all devices connected to the bus will use opendrain drivers to activate the clock and data lines. This allows multiple Master and Slave devices to coexist on the same serial interface without bus contention. Submit Documentation Feedback Copyright © 2000–2013, Texas Instruments Incorporated Product Folder Links: ADCS9888 27 OBSOLETE ADCS9888 SNAS203C – JAN 2000 – REVISED APRIL 2013 www.ti.com 6.2 Serial Protocol The serial protocol is made up of a number of basic protocol elements. A typical transaction will consist of: • Start Signal • (Slave Address + Read/Write Bit) Byte • Base Register Address Byte • Data Byte • Stop Signal 6.2.1 Start Signal Initially, when the bus is inactive, both SCL and SDA will be in a high logic state. A start signal consists of the SDA line transitioning from high to low, while the SCL line remains high. 6.2.2 Stop Signal When the bus is active, the data line will normally be high or low, and the clock will transition from low, to high, then return to low, to register the next bit in the sequence. A stop signal consists of the SDA line transitioning to a low state, followed by the SCL line transitioning to a high state, followed by the SDA line transitioning to the high state. 6.2.3 Repeat Start Signal A repeat start occurs in a sequence where a slave address and base address have already been transferred, but the mode of communications will be changing from Write to Read. This occurs during Read operations, since any Read operation first begins with a Write to specify the base register address. 6.2.4 Slave Address BYTE The slave address byte is used to distinguish between the different devices that may be connected to a common serial bus. Devices have a 7 bit address, with many devices having some bits configurable via external pin connections. The ADCS9888 address byte is configured as follows: Bit 7 Bit 6 Bit 5 Bit 4 Bit 3 Bit 2 Bit 1 Bit 0 A6 A5 A4 A3 A2 1 0 0 1 1 A1 A0 R/W 0 A0 Pin 0 6.2.5 Register Address BYTE ADCS9888 register addresses are an 8 bit value. Please refer to the Register Address table at the beginning of the datasheet for more detailed information. 6.2.6 Serial Interface Timeout The serial interface incorporates a timeout feature. This is present to ensure that the bus cannot become ‘locked’ if the master and slave become out of sync due to noise or other system issues. An internal timer is used to ensure that the interface is reset if the SCL line is held low. This is used to prevent problems in the case where the ADCS9888 is driving a low on the SDA line and the master device is reset. This allows the master to reset the state of the serial interface on the ADCS9888 by simply driving a low on SCL for more than 50 ms. The serial bus interface circuitry will be reset to the idle state if the SCL line is held low for more than 50 ms. The bus may be reset to idle if the SCL line is held low from 25 to 50 ms. The bus will not be reset if the SCL line is held low for less than 25 ms. 6.3 Specific Types Of Transfers 6.3.1 Write to Single Register • • • 28 Start Signal Slave Address Byte (R/W Bit = 0) Register Address Byte Submit Documentation Feedback Copyright © 2000–2013, Texas Instruments Incorporated Product Folder Links: ADCS9888 OBSOLETE ADCS9888 www.ti.com • • SNAS203C – JAN 2000 – REVISED APRIL 2013 Data Byte to Register Stop Signal 6.3.2 Burst Write to Multiple (3) Registers • • • • • • • Start Signal Slave Address Byte (R/W Bit = 0) Register Address Byte Data Byte to Register Data Byte to Register+1 Data Byte to Register+2 Stop Signal 6.3.3 Read from Single Register • • • • • • • Start Signal Slave Address Byte (R/W Bit = 0) Register Address Byte Start Signal Slave Address Byte (R/W Bit = 1) Data Byte to Register Stop Signal 6.3.4 Read from Multiple (3) Registers • • • • • • • • • Start Signal Slave Address Byte (R/W Bit = 0) Register Address Byte Start Signal Slave Address Byte (R/W Bit = 1) Data Byte to Register Data Byte to Register+1 Data Byte to Register+2 Stop Signal Submit Documentation Feedback Copyright © 2000–2013, Texas Instruments Incorporated Product Folder Links: ADCS9888 29 OBSOLETE ADCS9888 SNAS203C – JAN 2000 – REVISED APRIL 2013 SDA www.ti.com A6 A5 A4 A3 A2 A1 A0 /W ACK RA7 RA6 RA5 RA4 RA3 RA2 RA1 RA0 ACK D7 D6 D5 D4 D3 D2 D1 D0 ACK START SCL SDA SCL SDA STOP SCL Figure 14. Write to Single Register 30 Submit Documentation Feedback Copyright © 2000–2013, Texas Instruments Incorporated Product Folder Links: ADCS9888 OBSOLETE ADCS9888 www.ti.com SNAS203C – JAN 2000 – REVISED APRIL 2013 SDA ACK SLAVE ADDRESS AND WRITE COMMAND A6 A5 A4 A3 A2 A1 A0 /W RA7 RA6 RA5 RA4 RA3 RA2 RA1 RA0 ACK D7 D6 D5 D4 D3 D2 D1 D0 ACK DATA WRITE AT REGISTER ADDRESS D7 D6 D5 D4 D3 D2 D1 D0 ACK DATA WRITE AT REGISTER ADDRESS+1 D7 D6 D5 D4 D3 D2 D1 D0 ACK DATA WRITE AT REGISTER ADDRESS+2 SCL START SDA REGISTER ADDRESS SCL SDA SCL SDA SCL SDA SCL STOP Figure 15. Write to Multiple (3) Registers Submit Documentation Feedback Copyright © 2000–2013, Texas Instruments Incorporated Product Folder Links: ADCS9888 31 OBSOLETE ADCS9888 SNAS203C – JAN 2000 – REVISED APRIL 2013 SDA SCL www.ti.com A6 A5 A4 A3 A2 A1 A0 /W ACK RA7 RA6 RA5 RA4 RA3 RA2 RA1 RA0 ACK A6 A5 A4 A3 A2 A1 A0 R ACK D6 D5 D4 D3 D2 D1 D0 ACK SLAVE ADDRESS AND WRITE COMMAND START SDA REGISTER ADDRESS SCL SDA SLAVE D7 ADDRESS AND READ COMMAND SCL REPEAT START SDA D7 DATA READ AT REGISTER ADDRESS SCL STOP Figure 16. Read from Single Register 32 Submit Documentation Feedback Copyright © 2000–2013, Texas Instruments Incorporated Product Folder Links: ADCS9888 OBSOLETE ADCS9888 www.ti.com SNAS203C – JAN 2000 – REVISED APRIL 2013 SDA A6 A5 A4 A3 A2 A1 A0 /W RA7 RA6 RA5 RA4 RA3 RA2 RA1 RA0 ACK A6 A5 A4 A3 A2 A1 A0 R ACK SLAVE ADDRESS AND WRITE COMMAND ACK SCL START SDA REGISTER ADDRESS SCL SDA D7 SLAVE ADDRESS AND READ COMMAND SCL REPEAT START SDA D7 D6 D5 D4 D3 D2 D1 D0 ACK D7 DATA READ AT REGISTER ADDRESS D5 D4 D3 D2 D1 D0 ACK D7 DATA READ AT REGISTER ADDRESS+1 SCL SDA D7 D6 SCL SDA D7 D6 D5 D4 D3 D2 D1 D0 ACK DATA READ AT REGISTER ADDRESS+2 SCL STOP Figure 17. Read from Multiple (3) Registers 6.3.5 Serial Clock Input Noise Filter Because the serial clock and data lines are resistively pulled up to a power bus, there is a possibility that noise will be coupled into the clock or data lines when all devices have released the line. Noise on the clock line can have serious negative effects, by desynchronizing the Master and Slave. To help prevent these problems, a filter is included on the clock input, to prevent higher frequency noise pulses from being recognized by the serial interface. Submit Documentation Feedback Copyright © 2000–2013, Texas Instruments Incorporated Product Folder Links: ADCS9888 33 OBSOLETE ADCS9888 SNAS203C – JAN 2000 – REVISED APRIL 2013 www.ti.com REVISION HISTORY Changes from Revision B (April 2013) to Revision C • 34 Page Changed layout of National Data Sheet to TI format .......................................................................................................... 33 Submit Documentation Feedback Copyright © 2000–2013, Texas Instruments Incorporated Product Folder Links: ADCS9888 IMPORTANT NOTICE Texas Instruments Incorporated and its subsidiaries (TI) reserve the right to make corrections, enhancements, improvements and other changes to its semiconductor products and services per JESD46, latest issue, and to discontinue any product or service per JESD48, latest issue. Buyers should obtain the latest relevant information before placing orders and should verify that such information is current and complete. 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