ADS7811U

® ADS ADS7811 781 1 16-Bit 250kHz Sampling CMOS ANALOG-to-DIGITAL CONVERTER FEATURES q 250kHz SAMPLING RATE q COMPLETE WITH S/H, REF, CLOCK, ETC. q 96dB min SFDR WITH 100kHz INPUT q 84dB min SINAD q ±2.5V INPUT RANGE q 28-LEAD SOIC DESCRIPTION The ADS7811 is a complete 16-bit sampling analogto-digital (A/D) converter featuring excellent AC performance and a 250kHz throughput rate. The design includes a 16-bit capacitor-based SAR A/D converter with an inherent sample and hold (S/H), a precision reference, and an internal clock. Spuriousfree dynamic range with a 100kHz full-scale sinewave input is typically greater than 100dB. The ±2.5V input range allows development of precision systems using only ±5V supplies. The converter is available in a 28-lead SOIC package specified for operation over the industrial –25°C to +85°C temperature range. APPLICATIONS q WIRELESS BASE STATIONS q SPECTRUM ANALYSIS q IMAGING SYSTEMS q DATA ACQUISITION Clock R/C Successive Approximation Register and Control Logic CS BUSY CDAC ±2.5V Input Output Latches and Comparator Three State Drivers Buffer 5kΩ Internal +2.5V Ref Parallel Data Bus REF Out/In International Airport Industrial Park • Mailing Address: PO Box 11400, Tucson, AZ 85734 • Street Address: 6730 S. Tucson Blvd., Tucson, AZ 85706 • Tel: (520) 746-1111 • Twx: 910-952-1111 Internet: http://www.burr-brown.com/ • FAXLine: (800) 548-6133 (US/Canada Only) • Cable: BBRCORP • Telex: 066-6491 • FAX: (520) 889-1510 • Immediate Product Info: (800) 548-6132 ® © 1997 Burr-Brown Corporation PDS-1300A 1 Printed in U.S.A. November, 1997 ADS7811 SPECIFICATIONS At TA = –25°C to +85°C, fS = 250kHz, +VS = +5V, and –VS = –5V, using internal reference, unless otherwise specified. ADS7811U PARAMETER RESOLUTION ANALOG INPUT Voltage Range Impedance Capacitance THROUGHPUT SPEED Conversion Cycle Throughput Rate DC ACCURACY Integral Linearity Error No Missing Codes Transition Noise(2) Full Scale Error(3) Full Scale Error Drift Full Scale Error(3) Full Scale Error Drift Bipolar Zero Error Bipolar Zero Error Drift Power Supply Sensitivity AC ACCURACY Spurious-Free Dynamic Range Total Harmonic Distortion Signal-to-(Noise+Distortion) Signal-to-Noise Usable Bandwidth(5) Aperture Delay REFERENCE Internal Reference Voltage Internal Reference Source Current Internal Reference Drift External Reference Voltage Range External Reference Current Drain DIGITAL INPUTS Logic Levels VIL VIH IIL IIH DIGITAL OUTPUTS Data Format Data Coding VOL VOH Leakage Current Output Capacitance DIGITAL TIMING Bus Access Time Bus Relinquish Time POWER SUPPLIES +VS –VS +IS –IS Power Dissipation TEMPERATURE RANGE Specified Performance Storage +4.75 –5.25 +5 –5 +30 –10 200 ±2.5V 100 30 4.0 250 ±4 15 0.8 ±7 ±0.2 2 ±2 ±6 96 84 84 100 –98 87 28 87 1 40 2.5 1 15 2.5 ±0.5 CONDITIONS MIN TYP MAX 16 UNITS Bits V MΩ pF µs kHz LSB(1) Bits LSB % ppm/° C % ppm/° C mV ppm/° C LSB dB(4) dB dB dB dB MHz ns V µA ppm/° C V µA After Input Capacitor is Charged Acquire and Convert External 2.5000V Reference External 2.5000V Reference ±10 ±16 +VS ±5%, –VS ±5% fIN = 100kHz fIN = 100kHz fIN = 100kHz –60dB Input fIN = 100kHz –96 2.48 2.52 VREF = +2.5V 100 –0.3 +2.8 +0.8 +VS +0.3V ±10 ±10 Parallel 16 bits Binary Two’s Complement V V µA µA ISINK = 1.6mA ISOURCE = 200µA High-Z State, VOUT = 0V to VDIG High-Z State +0.4 +4 ±5 15 83 83 +5.25 –4.75 V V µA pF ns ns V V mA mA mW °C °C 250 +85 +125 –25 –55 NOTES: (1) LSB means Least Significant Bit. For the 16-bit, ±2.5V input ADS7811, one LSB is 76µV. (2) Typical rms noise at worst case transitions and temperatures. (3) Full scale error is the worst case of –Full Scale or +Full Scale untrimmed deviation from ideal first and last code transitions, divided by the transition voltage (not divided by the full-scale range) and includes the effect of offset error. (4) All specifications in dB are referred to a full-scale ±2.5V input. (5) Usable Bandwidth defined as Full-Scale input frequency at which Signal-to-(Noise+Distortion) degrades to 60dB, or 10 bits of accuracy. ® ADS7811 2 ABSOLUTE MAXIMUM RATINGS Analog Inputs: VIN .............................................. –VS – 0.3V to +VS + 0.3V REF ................................................... – 0.3V to +VS + 0.3V CAP ............................................... Indefinite Short to GND Momentary Short to +VS +VS ......................................................................................................... 7V –VS ...................................................................................................... –7V Digital Inputs .............................................................. –0.3V to +VS + 0.3V Maximum Junction Temperature ................................................... +165°C Internal Power Dissipation ............................................................. 825mW Lead Temperature (soldering, 10s) ................................................ +300°C PACKAGE/ORDERING INFORMATION PACKAGE DRAWING NUMBER(1) 217 TEMPERATURE RANGE –25° C to +85°C PRODUCT ADS7811U PACKAGE 28-Pin SOIC NOTE: (1) For detailed drawing and dimension table, please see end of data sheet, or Appendix C of Burr-Brown IC Data Book. ELECTROSTATIC DISCHARGE SENSITIVITY This integrated circuit can be damaged by ESD. Burr-Brown recommends that all integrated circuits be handled with appropriate precautions. Failure to observe proper handling and installation procedures can cause damage. ESD damage can range from subtle performance degradation to complete device failure. Precision integrated circuits may be more susceptible to damage because very small parametric changes could cause the device not to meet its published specifications. The information provided herein is believed to be reliable; however, BURR-BROWN assumes no responsibility for inaccuracies or omissions. BURR-BROWN assumes no responsibility for the use of this information, and all use of such information shall be entirely at the user’s own risk. Prices and specifications are subject to change without notice. No patent rights or licenses to any of the circuits described herein are implied or granted to any third party. BURR-BROWN does not authorize or warrant any BURR-BROWN product for use in life support devices and/or systems. ® 3 ADS7811 PIN # 1 2 3 4 5 6 7 8 9 10 11 12 13 14 15 16 17 18 19 20 21 22 23 24 25 26 NAME VIN GND REF CAP GND D15 (MSB) D14 D13 D12 D11 D10 D9 D8 GND D7 D6 D5 D4 D3 D2 D1 D0 (LSB) –VS R/C CS BUSY DESCRIPTION Analog Input. Full-scale input range is ±2.5V. Ground. Reference Input/Output. Outputs internal reference of +2.5V nominal. Can also be driven by external system reference. In both cases, connect to ground with a 0.1µF ceramic capacitor in parallel with 2.2µF tantalum capacitor. Reference compensation capacitor. Use a parallel combination of a 0.1µF ceramic capacitor and a 2.2µF tantalum capacitor. Ground. Data Bit 15. Most Significant Bit (MSB) of conversion results. Hi-Z state when CS is HIGH, when R/C is LOW or when a conversion is in progress. Data Bit 14. Hi-Z state when CS is HIGH, when R/C is LOW or when a conversion is in progress. Data Bit 13. Hi-Z state when CS is HIGH, when R/C is LOW or when a conversion is in progress. Data Bit 12. Hi-Z state when CS is HIGH, when R/C is LOW or when a conversion is in progress. Data Bit 11. Hi-Z state when CS is HIGH, when R/C is LOW or when a conversion is in progress. Data Bit 10. Hi-Z state when CS is HIGH, when R/C is LOW or when a conversion is in progress. Data Bit 9. Hi-Z state when CS is HIGH, when R/C is LOW or when a conversion is in progress. Data Bit 8. Hi-Z state when CS is HIGH, when R/C is LOW or when a conversion is in progress. Ground. Data Bit 7. Hi-Z state when CS is HIGH, when R/C is LOW or when a conversion is in progress. Data Bit 6. Hi-Z state when CS is HIGH, when R/C is LOW or when a conversion is in progress. Data Bit 5. Hi-Z state when CS is HIGH, when R/C is LOW or when a conversion is in progress. Data Bit 4. Hi-Z state when CS is HIGH, when R/C is LOW or when a conversion is in progress. Data Bit 3. Hi-Z state when CS is HIGH, when R/C is LOW or when a conversion is in progress. Data Bit 2. Hi-Z state when CS is HIGH, when R/C is LOW or when a conversion is in progress. Data Bit 1. Hi-Z state when CS is HIGH, when R/C is LOW or when a conversion is in progress. Data Bit 0. Least Significant Bit (LSB) of conversion results. Hi-Z state when CS is HIGH, when R/C is LOW or when a conversion is in progress. Negative supply input. Nominally –5V. Decouple to analog ground with 0.1µF ceramic and 10µF tantalum capacitors. Read/convert input. With R/C HIGH, CS going LOW will enable the output data bits if a conversion is not in progress. With R/C LOW, CS going LOW will start a conversion if one is not already in progress. Chip select. With R/C LOW, CS going LOW will initiate a conversion if one is not already in progress. With R/C HIGH, CS going LOW will enable the output data bits if a conversion is not in progress. Busy output. Falls when a conversion is started, and remains LOW until the conversion is completed. With CS LOW and R/C HIGH, output data will be valid when BUSY rises, so that the rising edge can be used to latch the data. CS or R/C must be HIGH within 250ns after BUSY rises or another conversion will start without time for signal acquisition. Positive supply input. Nominally +5V. Connect directly to pin 28. Positive supply input. Nominally +5V. Connect directly to pin 27. Decouple to ground with 0.1µF ceramic and 10µF tantalum capacitors. 27 28 +VS +VS TABLE I. Pin Assignments. PIN CONFIGURATION Top View SOIC VIN GND REF CAP GND D15 (MSB) D14 D13 D12 1 2 3 4 5 6 7 ADS7811 8 9 28 +VS 27 +VS 26 BUSY 25 CS 24 R/C 23 –VS 22 D0 (LSB) 21 D1 20 D2 19 D3 18 D4 17 D5 16 D6 15 D7 D11 10 D10 11 D9 12 D8 13 GND 14 ® ADS7811 4 TYPICAL PERFORMANCE CURVES At TA = –25°C to +85° C, fS = 250kHz, +VS = +5V, and –VS = –5V, using internal reference, unless otherwise specified. FREQUENCY SPECTRUM (4096 Point FFT; fIN = 9.9kHz, –0.5dB) 0 –20 –40 0 –20 –40 FREQUENCY SPECTRUM (4096 Point FFT; fIN = 99kHz, –0.5dB) Amplitude (dB) –60 –80 –100 –120 –140 0 25 50 75 100 125 Frequency (kHz) Amplitude (dB) –60 –80 –100 –120 –140 0 25 50 75 100 125 Frequency (kHz) FREQUENCY SPECTRUM (4096 Point FFT; fIN = 247kHz, –0.5dB) 0 –20 –40 INTEGRAL LINEARITY ERROR AND DIFFERENTIAL LINEARITY ERROR vs OUTPUT CODE 4 2 0 –2 –4 4 Amplitude (dB) –60 –80 –100 –120 –140 0 25 50 75 100 125 Frequency (kHz) ILE (LSB) DLE (LSB) 2 0 –2 –4 8000h C000h 0000h Hex BTC Code 4000h 7FFFh CONVERSION TIME (t2 + t4) vs TEMPERATURE 3.70 3.65 2.520 2.515 REFERENCE VOLTAGE vs TEMPERATURE 3.55 3.50 3.45 3.40 3.35 3.30 –30 –10 10 30 50 70 90 Temperature (°C) Reference Voltage (V) Conversion Time (µs) 3.60 2.510 2.505 2.500 2.495 2.490 2.485 2.480 –30 –10 10 30 50 70 90 Temperature (°C) ® 5 ADS7811 BASIC OPERATION Figure 1 shows the recommended circuit for operation of the ADS7811. A falling edge on the convert pulse signal places the sample and hold into the hold mode and initiates a conversion. When the conversion is complete, the pins D15 through D0 become active and the result of the conversion is placed on these outputs. In the circuit shown in Figure 1, the rising edge of BUSY latches the result into the 74HC574s. After the conversion is complete, the ADS7811 sample and hold returns to the sample mode and begins acquiring the input signal for the next conversion. Allowing 4µs between falling edges of the convert pulse signal assures adequate acquisition time for the internal sample and hold. R1 75Ω +5V OPA628 R2 10Ω 1 VIN GND REF CAP GND D15 +VS 28 +VS 27 BUSY 26 CS 25 R/C 24 –VS 23 0.1µF C7 74HC00 10µF + C8 –5V 100ns min 3.3µs max 0.1µF C1 + 10µF C2 +5V –5V 2.2µF C3 2.2µF C4 + 2 0.1µF C5 0.1µF C6 3 4 5 6 7 8 9 10 11 12 13 14 Convert Pulse + D0 22 D14 ADS7811 D1 21 D13 D12 D11 D10 D9 D8 GND D2 20 D3 19 D4 18 D5 17 D6 16 D7 15 OC 1 10 2 3 4 5 6 7 8 9 OC CLK 1D 2D 3D 4D 5D 6D 7D 8D 1Q 2Q 3Q 4Q 5Q 6Q 7Q 8Q µProcessor Bus 74HC574 1 10 2 3 4 5 6 7 8 9 OC CLK 1D 2D 3D 4D 5D 6D 7D 8D 1Q 2Q 3Q 4Q 5Q 6Q 7Q 8Q µProcessor Bus 74HC574 FIGURE 1. Basic Operation. ® ADS7811 6 TIMING The timing shown in Figure 2 and Table II is the recommended method of operating the ADS7811. The falling edge of CS initiates the conversion. During the conversion, the digital outputs are tri-stated and BUSY is LOW. Near the end of the conversion, the digital outputs become active with the most recent conversion result. After a brief delay (see time t11 in Figure 2 and Table II), BUSY rises. The rising edge of BUSY is used to latch the digital result in Figure 1. R/C AND CS The R/C (read/convert) and CS signals control the start of conversion and, when a conversion is not in progress, the status of the digital outputs D15 through D0. It is possible to start a conversion by taking CS LOW and then taking R/C LOW. However, this is not recommended and will result in a significant decrease in signal-to-noise ratio. This is due to the digital outputs tri-stating while the sample and hold transitions to the hold mode. The change in digital outputs results in noise being coupled onto the hold capacitor. If a conversion is not in progress or is just about to finish, the digital outputs will be active when R/C is HIGH and CS is LOW. This is shown in Figure 2 and Figure 3. It is possible to return CS HIGH during the initial part of the conversion (as is done with R/C) and prevent the digital outputs from becoming active. At a later time, the digital results could be read by taking CS LOW. It is also possible to leave R/C LOW, take CS HIGH during the conversion, and read the results at a later time by taking R/C HIGH and CS LOW. Following a conversion, if R/C and CS are both LOW 250ns after BUSY rises, then a new conversion will be initiated without allowing the proper acquisition period for the sample and hold. R/C must remain HIGH or CS must be taken HIGH within 250ns of BUSY rising. R/C and CS should remain static prior to that start of conversion and during the later part of a conversion. To start SYMBOL t1 t2 t3 t4 t5 t6 t7 t8 t9 t10 t11 t12 DESCRIPTION CS to R/C Delay CS to BUSY Delay Aperture Delay BUSY LOW R/C LOW to CS LOW BUSY HIGH to CS HIGH Bus Access Time Bus Relinquish Time Throughput Time Conversion Time Data Valid to BUSY HIGH CS to R/C Setup Time MIN t2 TYP MAX 200 UNITS ns ns ns µs ns 40 40 3.5 100 250 10 83 83 4 3.4 25 40 35 t12 R/C t7 CS t8 ns ns ns µs µs ns ns D15 - D0 Hi-Z State DataValid Hi-Z State MODE Acquire TABLE II. Conversion Timing. FIGURE 3. Bus Timing. t1 R/C t5 t6 CS t2 BUSY t4 t9 t8 D15 - D0 Hi-Z State DataValid Hi-Z State t11 t3 MODE Acquire Convert t10 Acquire FIGURE 2. ADS7811 Timing. ® 7 ADS7811 a conversion, R/C should be taken LOW at least 100ns before CS is taken LOW. R/C and/or CS should be taken HIGH during the early part of the conversion, preferably within 200ns of the start of the conversion. If these times are not observed, then there is risk that the transition of these digital signals may affect the conversion result. The three NAND gates shown in Figure 1 can be used to generate R/C and CS signals from a single negative going pulse. The pulse must not be longer than 3.3µs or a second conversion may be initiated immediately after the first. BUSY BUSY goes LOW when a conversion is started and remains LOW throughout the conversion. Just prior to BUSY going HIGH, the digital outputs become active with the conversion result. Time t11, shown in Figure 2, should provide adequate time for the ADS7811 to drive the digital outputs to a valid logic state before BUSY rises. As shown in Figure 1 and 2, the rising edge of BUSY can be used to latch the digital result into an external component. to that listed in the Specifications Table. The range for the external reference is 2.3V to 2.7V. While the ADS7811 will operate using an external reference, the specifications are only guaranteed when the internal reference is used. REF PIN The REF pin itself should be bypassed with a 0.1µF ceramic capacitor in parallel with a 2.2µF tantalum capacitor. While both capacitors should be physically close to the ADS7811, it is very important that the ceramic capacitor be placed as close as possible. The REF voltage should not be used to drive a large load or any load which is dynamic. A large load will reduce the reference voltage and the corresponding input range of the converter. A dynamic load will modulate the reference voltage and this modulation will be present in the converter’s output data. CAP PIN The voltage on the CAP pin is the output of the reference buffer. This pin should be bypassed with a 0.1µF ceramic capacitor in parallel with a 2.2µF tantalum capacitor. While both capacitors should be physically close to the ADS7811, it is very important that the ceramic capacitor be placed as close as possible. The CAP pin connects to the internal reference buffer and directly to the binary weighted capacitor array of the converter. Thus, the signal at the CAP pin has high-frequency glitches which occur at each bit decision. For this reason, the CAP voltage should not be used to provide a reference voltage for external circuitry. DIGITAL OUTPUT The ADS7811’s digital output is in Binary Two’s Complement (BTC) format. Table III shows the relationship between the digital output word and analog input voltage under ideal conditions. DIGITAL OUTPUT ANALOG INPUT ±2.5V 76µV 2.499924V 0V –76 µV –2.5V 0111 1111 1111 1111 0000 0000 0000 0000 1111 1111 1111 1111 1000 0000 0000 0000 7FFF 0000 FFFF 8000 BINARY TWO’S COMPLEMENT BINARY CODE HEX CODE DESCRIPTION Full Scale Range Least Significant Bit (LSB) +Full Scale (2.5V – 1LSB) Midscale One LSB below Midscale –Full Scale LAYOUT The layout of the ADS7811 and accompanying components will be critical for optimum performance. Use of an analog ground plane is essential. Use of +5V and –5V power planes is not critical as long as the supplies are well bypassed, and the traces connecting +5V and –5V to the power connector are not too long or too thin. The two +VS power pins of the ADS7811 must be tied together. The voltage source for these pins should also power the input buffer and the 74HC00 shown in Figure 1. This supply should separate from the positive +5V supply for the system’s digital logic Three ground pins are present on the ADS7811: pin 2, pin 5, and pin 14. These should all be tied to the analog ground plane. The analog ground plane should extend underneath all analog signal conditioning components and up to the 74HC574s (or equivalent components) shown in Figure 1. The 74HC574s should not be located more than several inches from the ADS7811. The ground for the 74HC574s should be connected to the digital ground. The analog ground plane should extend up to Table III. Ideal Input Voltages and Output Codes. REFERENCE The ADS7811 can be operated with the internal 2.5V reference or an external reference. By applying an external reference to the REF pin, the internal reference is bypassed. The reference voltage at REF is buffered internally. The voltage at the reference input sets the full-scale range of the converter. With the internal 2.5V reference, the input range is ±2.5V. Thus, the input range of the converter’s analog input is simply ±VREF, where VREF is the voltage at the reference input. Because of internal gain and offset error, the input range will not be exactly ±VREF. The full-scale error of the converter with an external reference will typically be 0.25% or less. The bipolar zero error will be similar ® ADS7811 8 the 74HC574s but should be kept at least 1/4" (6mm) distant from the digital ground plane (if present). The analog and digital grounds planes should not overlap at any point. INTERMEDIATE LATCHES The 74HC574s shown in Figure 1 isolate the ADS7811 from digital signals on a microprocessor, digital signal processor (DSP), or microcontroller bus. This is necessary because of the precision needed within the ADS7811. The weight of a single LSB in the ADS7811 is 76µV, and the comparator must be able to resolve differences in voltage to this level. External digital signals which transition during the conversion can easily couple onto the substrate and produce voltages larger than this. In place of the 74HC574s, it might be possible to use a FIFO or similar type of memory device. For many systems, it may be difficult to go directly from the ADS7811 into a microcontroller or DSP even if the ADS7811 is not connected to shared bus. The reason for this is that the outputs are active only during the acquisition period. SIGNAL CONDITIONING The ADS7811 input essentially consists of a switch and a capacitor. In the acquisition or sample mode, the switch is closed and the input signal drives the capacitor directly. When a conversion is started, the switch is opened capturing the input signal at that moment. This voltage is held on the capacitor for the remainder of the conversion. While this provides for a wide bandwidth sample and hold function and results in excellent AC performance, this architecture requires a high bandwidth, precision op amp to drive the analog input. The op amp and configuration shown in Figure 1 is highly recommended. The amplifier should be placed within 1 to 2 inches (25 to 50mm) of the ADS7811, and the layout guidelines in the OPA628 data sheet should be strictly followed. ® 9 ADS7811