ADS803EG4

ADS803 AD S 803 E SBAS074B – JANUARY 1997 – REVISED SEPTEMBER 2002 12-Bit, 5MHz Sampling ANALOG-TO-DIGITAL CONVERTER FEATURES APPLICATIONS ● ● ● ● ● ● ● IF AND BASEBAND DIGITIZATION ● CCD IMAGING SCANNERS ● TEST INSTRUMENTATION HIGH SFDR: 82dB at NYQUIST HIGH SNR: 69dB LOW POWER: 115mW LOW DLE: 0.25LSB FLEXIBLE INPUT RANGE OVER-RANGE INDICATOR DESCRIPTION The ADS803 is a high-speed, high dynamic range, 12-bit pipelined Analog-to-Digital (A/D) converter. This converter includes a high-bandwidth track-and-hold that gives excellent spurious performance up to and beyond the Nyquist rate. This high-bandwidth, linear track-and-hold minimizes harmonics and has low jitter, leading to excellent SNR performance. The ADS803 is also pin-compatible with the 10MHz ADS804 and the 20MHz ADS805. The ADS803 provides an internal reference and can be programmed for a 2Vp-p input range for the best spurious performance and ease of driving. Alternatively, the 5Vp-p input range can be used for the lowest input referred noise of 0.09LSBs rms giving superior imaging performance. There is also a capability to set the input range in between the 2Vp-p and 5Vp-p input ranges or to use an external reference. The ADS803 also provides an over-range indicator flag to indicate an input range that exceeds the full-scale input range of the converter. This flag can be used to reduce the gain of the frontend gain-ranging circuitry. The ADS803 employs digital error-correction techniques to provide excellent differential linearity for demanding imaging applications. Its low distortion and high SNR give the extra margin needed for communications, medical imaging, video, and test instrumentation applications. The ADS803 is available in an SSOP-28 package. +VS CLK VDRV ADS803 Timing Circuitry VIN IN IN 12-Bit Pipelined ADC T&H Error Correction Logic 3-State Outputs D0 • • • D11 CM OVR Reference Ladder and Driver Reference and Mode Select REFT VREF SEL REFB OE Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet. Copyright © 1997, Texas Instruments Incorporated PRODUCTION DATA information is current as of publication date. Products conform to specifications per the terms of Texas Instruments standard warranty. Production processing does not necessarily include testing of all parameters. www.ti.com ABSOLUTE MAXIMUM RATINGS(1) ELECTROSTATIC DISCHARGE SENSITIVITY +VS ....................................................................................................... +6V Analog Input ........................................................... (–0.3V) to (+VS +0.3V) Logic Input ............................................................. (–0.3V) to (+VS +0.3V) Case Temperature ......................................................................... +100°C Junction Temperature .................................................................... +150°C Storage Temperature ..................................................................... +150°C This integrated circuit can be damaged by ESD. Texas Instruments recommends that all integrated circuits be handled with appropriate precautions. Failure to observe proper handling and installation procedures can cause damage. NOTE: (1) Stresses above those listed under “Absolute Maximum Ratings” may cause permanent damage to the device. Exposure to absolute maximum conditions for extended periods may affect device reliability. ESD damage can range from subtle performance degradation to complete device failure. Precision integrated circuits may be more susceptible to damage because very small parametric changes could cause the device not to meet its published specifications. PACKAGE/ORDERING INFORMATION SPECIFIED TEMPERATURE RANGE PACKAGE MARKING PRODUCT PACKAGE-LEAD PACKAGE DESIGNATOR(1) ADS803E SSOP-28 DB –40°C to +85°C ADS803E ADS803E Rails, 48 " " " " ADS803E/1K Tape and Reel, 1000 " ORDERING NUMBER TRANSPORT MEDIA, QUANTITY NOTE: (1) For the most current specifications and package information, refer to our web site at www.ti.com. ELECTRICAL CHARACTERISTICS At TA = full specified temperature range, VS = +5V, specified input range = 1.5V to 3.5V, single-ended input and sampling rate = 5MHz, unless otherwise specified. ADS803E PARAMETER CONDITIONS MIN RESOLUTION –40 CONVERSION CHARACTERISTICS Sample Rate Data Latency 10k DYNAMIC CHARACTERISTICS Differential Linearity Error (Largest Code Error) f = 500kHz No Missing Codes Spurious-Free Dynamic Range(1) f = 2.48MHz (–1dB input) 2-Tone Intermodulation Distortion(3) f = 1.8M and 1.9M (–7dBFS each tone) Signal-to-Noise Ratio (SNR) f = 2.48MHz (–1dB input) Signal-to-(Noise + Distortion) (SINAD) f = 2.48MHz (–1dB input) Effective Number of Bits at 2.48MHz(4) Input Referred Noise Integral Nonlinearity Error f = 500kHz Aperture Delay Time Aperture Jitter Over-Voltage Recovery Time Full-Scale Step Acquisition Time 2 MAX 12 Tested SPECIFIED TEMPERATURE RANGE ANALOG INPUT Single-Ended Input Range Standard Optional Single-Ended Input Range Common-Mode Voltage Standard Optional Common-Mode Voltage Input Capacitance Track-Mode Input Bandwidth TYP Bits +85 °C 5M Samples/s Clk Cycles 3.5 5 V V V V pF MHz ±0.75 LSB 6 1.5 0 2.5 1 20 270 –3dBFS Input ±0.25 Tested 0V to 5V Input 1.5V to 3.5V Input 1.5 • FS Input UNITS 74 82 74 dBFS(2) dBc 66.5 69 dB 65 68 11 0.09 0.23 dB Bits LSBs rms LSBs rms ±1 1 4 2 50 ±2 LSB ns ps rms ns ns ADS803 www.ti.com SBAS074B ELECTRICAL CHARACTERISTICS (Cont.) At TA = full specified temperature range, VS = +5V, specified input range = 1.5V to 3.5V, single-ended input and sampling rate = 5MHz, unless otherwise specified. ADS803E PARAMETER DIGITAL INPUTS Logic Family Convert Command High Level Input Current (VIN = 5V)(5) Low Level Input Current (VIN = 0V) High Level Input Voltage Low Level Input Voltage Input Capacitance DIGITAL OUTPUTS Logic Family Logic Coding Low Output Voltage Low Output Voltage High Output Voltage High Output Voltage 3-State Enable Time 3-State Disable Time Output Capacitance ACCURACY (5Vp-p Input Range) Zero Error (Referred to –FS) Zero Error Drift (Referred to –FS) Gain Error(6) Gain Error Drift(6) Gain Error(7) Gain Error Drift(7) Power-Supply Rejection of Gain Reference Input Resistance Internal Voltage Reference Tolerance (VREF = 2.5V) Internal Voltage Reference Tolerance (VREF = 1.0V) POWER-SUPPLY REQUIREMENTS Supply Voltage: +VS Supply Current: +IS Power Dissipation Thermal Resistance, θJA SSOP-28 CONDITIONS MIN TYP MAX CMOS Compatible Rising Edge of Convert Clock Start Conversion 100 ±10 +3.5 +1.0 5 CMOS/TTL Compatible Straight Offset Binary (IOL = 50µA) (IOL = 1.6mA) (IOH = 50µA) (IOH = 0.5mA) OE = L OE = H +4.5 +2.4 20 2 5 40 10 0.2 ±5 ±1.5 At 25°C ±15 At 25°C 60 ±15 82 1.6 At 25°C At 25°C Operating Operating Operating +4.7 +5.0 23 115 50 µA µA V V pF V 0.1 0.4 fS = 2.5MHz At 25°C ∆VS = ±5% UNITS V V V V ns ns pF ±35 ±14 %FS ppm/°C %FS ppm/°C %FS ppm/°C dB kΩ mV mV 5.3 27 135 V mA mW ±2.0 ±1.5 °C/W NOTES: (1) Spurious-Free Dynamic Range refers to the magnitude of the largest harmonic. (2) dBFS means dB relative to full-scale. (3) 2-tone intermodulation distortion is referred to the largest fundamental tone. This number will be 6dB higher if it is referred to the magnitude of the 2-tone fundamental envelope. (4) Effective number of bits (ENOB) is defined by (SINAD – 1.76)/6.02. (5) Internal 50kΩ pull-down resistor. (6) Includes internal reference. (7) Excludes internal reference. ADS803 SBAS074B www.ti.com 3 PIN DESCRIPTIONS PIN CONFIGURATION Top View SSOP OVR 1 28 VDRV B1 2 27 +VS B2 3 26 GND B3 4 25 IN B4 5 24 GND B5 6 23 IN B6 7 22 REFT B7 8 21 CM B8 9 20 REFB B9 10 19 VREF B10 11 18 SEL B11 12 17 GND B12 13 16 +VS CLK 14 15 OE ADS803 PIN DESIGNATOR 1 2 3 4 5 6 7 8 9 10 11 12 13 14 15 16 17 18 19 20 21 22 23 24 25 26 27 28 OVR B1 B2 B3 B4 B5 B6 B7 B8 B9 B10 B11 B12 CLK OE +VS GND SEL VREF REFB CM REFT IN GND IN GND +VS VDRV DESCRIPTION Over-Range Indicator Data Bit 1 (MSB) Data Bit 2 Data Bit 3 Data Bit 4 Data Bit 5 Data Bit 6 Data Bit 7 Data Bit 8 Data Bit 9 Data Bit 10 Data Bit 11 Data Bit 12 (LSB) Convert Clock Input Output Enable +5V Supply Ground Input Range Select Reference Voltage Select Bottom Reference Common-Mode Voltage Top Reference Complementary Analog Input Analog Ground Analog Input (+) Analog Ground +5V Supply Output Driver Voltage TIMING DIAGRAM N+2 N+1 Analog In N+4 N+3 N tD N+5 tL tCONV N+7 N+6 tH Clock 6 Clock Cycles t2 Data Out N–6 N–5 N–4 N–3 N–2 N–1 N Data Invalid SYMBOL tCONV tL tH tD t1 t2 4 N+1 t1 DESCRIPTION MIN Convert Clock Period Clock Pulse LOW Clock Pulse HIGH Aperture Delay Data Hold Time, CL = 0pF New Data Delay Time, CL = 15pF max 200 96 96 TYP MAX 1• 105(ns) 99 99 3 3.9 12 UNITS ns ns ns ns ns ns ADS803 www.ti.com SBAS074B TYPICAL CHARACTERISTICS At TA = full specified temperature range, VS = +5V, specified input range = 1.5V to 3.5V, and single-ended input and sampling rate = 5MHz, unless otherwise specified. SPECTRAL PERFORMANCE SPECTRAL PERFORMANCE 0 0 fIN = 2.48MHz –20 –20 –40 –40 Amplitude (dB) Amplitude (dB) fIN = 500kHz –60 –80 –100 –60 –80 –100 –120 –120 0 0.5 1.0 1.5 2.0 2.5 0 0.5 1.0 Frequency (MHz) FREQUENCY SPECTRUM 0 2.5 DIFFERENTIAL LINEARITY ERROR fIN = 500kHz 0.5 –40 DLE (LSB) Magnitude (dBFSR) 2.0 1.0 f1 = 1.8MHz at –7dB f2 = 1.9MHz at –7dB IMD (3) = –74dBc –20 1.5 Frequency (MHz) –60 0 –80 –0.5 –100 –120 –1.0 0 0.5 1.0 1.5 2.0 2.5 0 1024 2048 Frequency (MHz) 3072 INTEGRAL LINEARITY ERROR SWEPT POWER SFDR 4.0 100 fIN = 2.48MHz fIN = 500kHz 80 SFDR (dBFS, dBc) 2.0 ILE (LSB) 4096 Output Code 0 –2.0 dBFS 60 dBc 40 20 0 –4.0 0 1024 2048 3072 4096 –60 Output Code –40 –30 –20 –10 0 Input Amplitude (dBFS) ADS803 SBAS074B –50 www.ti.com 5 TYPICAL CHARACTERISTICS (Cont.) At TA = full specified temperature range, VS = +5V, specified input range = 1.5V to 3.5V, and single-ended input and sampling rate = 5MHz, unless otherwise specified. DYNAMIC PERFORMANCE vs INPUT FREQUENCY (Differential Input, VIN = 5Vp-p) DYNAMIC PERFORMANCE vs INPUT FREQUENCY 85 85 SFDR SFDR, SNR (dBFS) SFDR, SNR (dBFS) SFDR 80 80 75 70 SNR 65 75 70 SNR 65 60 60 0.1 1 0.1 10 1 10 Frequency (MHz) Frequency (MHz) DIFFERENTIAL LINEARITY ERROR vs TEMPERATURE SPURIOUS-FREE DYNAMIC RANGE vs TEMPERATURE 85 0.40 fIN = 500kHz 0.30 SFDR (dBFS) DLE (LSB) fIN = 500kHz fIN = 2.48MHz 0.20 80 fIN = 2.48MHz 75 70 0.10 –50 –25 0 25 50 75 100 –50 –25 0 Temperature (°C) 25 50 75 100 Temperature (°C) SIGNAL-TO-NOISE RATIO AND SIGNAL-TO-(NOISE + DISTORTION) vs TEMPERATURE POWER DISSIPATION vs TEMPERATURE 117 72 70 SNR fIN = 500kHz 68 SINAD fIN = 2.48MHz fIN = 2.48MHz Power (mW) SINAD, SNR (dBFS) fIN = 500kHz 115 66 114 64 –50 –25 0 25 50 75 –50 100 –25 0 25 50 75 100 Temperature (°C) Temperature (°C) 6 116 ADS803 www.ti.com SBAS074B TYPICAL CHARACTERISTICS (Cont.) At TA = full specified temperature range, VS = +5V, specified input range = 1.5V to 3.5V, and single-ended input and sampling rate = 5MHz, unless otherwise specified. OUTPUT NOISE HISTOGRAM (DC Input, VIN = 5Vp-p Range) 800k 800k 600k 600k Counts Counts OUTPUT NOISE HISTOGRAM (DC Input, VIN = 2Vp-p) 400k 400k 200k 200k 0 0 N–2 N–1 N N+1 N–2 N+2 N–1 N N+1 N+2 Code Code APPLICATION INFORMATION to be 2Vp-p. This signal is ac-coupled in single-ended form to the ADS803 using the low-distortion voltage-feedback amplifier OPA642. As is generally necessary for singlesupply components, operating the ADS803 with a full-scale input signal swing requires a level-shift of the amplifier’s zero-centered analog signal to comply with the A/D converter’s input range requirements. Using a DC blocking capacitor between the output of the driving amplifier and the converter’s input, a simple level-shifting scheme can be implemented. In this configuration, the top and bottom references (REFT and REFB) provide an output voltage of +3V and +2V, respectively. Here, two resistor pairs (2 • 2kΩ) are used to create a common-mode voltage of approximately +2.5V to bias the inputs of the ADS803 (IN, IN) to the required DC voltage. DRIVING THE ANALOG INPUT The ADS803 allows its analog inputs to be driven either single-ended or differentially. The focus of the following discussion is on the single-ended configuration. Typically, its implementation is easier to achieve and the rated specifications for the ADS803 are characterized using the singleended mode of operation. AC-COUPLED INPUT CONFIGURATION Given in Figure 1 is the circuit example of the most common interface configuration for the ADS803. With the VREF pin connected to the SEL pin, the full-scale input range is defined +5V –5V +VIN 2Vp-p VIN 0.1µF RS 24.9Ω 2kΩ IN OPA642 0V –VIN REFT (+3V) 2kΩ 100pF RF 402Ω ADS803 2kΩ RG 402Ω +2.5VDC IN 0.1µF 2kΩ (+2V) REFB (+1V) VREF SEL FIGURE 1. AC-Coupled Input Configuration for 2Vp-p Input Swing and Common-Mode Voltage at +2.5V Derived from Internal Top and Bottom Reference. ADS803 SBAS074B www.ti.com 7 An advantage of ac-coupling is that the driving amplifier still operates with a ground-based signal swing. This will keep the distortion performance at its optimum since the signal swing stays within the linear region of the op amp and sufficient headroom to the supply rails can be maintained. Consider using the inverting gain configuration to eliminate CMR induced errors of the amplifier. The addition of a small series resistor (RS) between the output of the op amp and the input of the ADS803 will be beneficial in almost all interface configurations. This will decouple the op amp’s output from the capacitive load and avoid gain peaking, which can result in increased noise. For best spurious and distortion performance, the resistor value should be kept below 50Ω. Furthermore, the series resistor together with the 100pF capacitor, establish a passive low-pass filter, limiting the bandwidth for the wideband noise thus help improving the SNR performance. DC-COUPLED WITHOUT LEVEL SHIFT In some applications the analog input signal may already be biased at a level which complies with the selected input range and reference level of the ADS803. In this case, it is only necessary to provide an adequately low source impedance to the selected input, IN or IN. Always consider wideband op amps, since their output impedance will stay low over a wide range of frequencies. For those applications requiring the driving amplifier to provide a signal amplification (with a gain ≥ 3), consider using the decompensated voltage-feedback op amp OPA643. DC-COUPLED WITH LEVEL SHIFT Several applications may require that the bandwidth of the signal path includes DC, in which case the signal has to be DC-coupled to the A/D converter. In order to accomplish this, the interface circuit has to provide a DC-level shift. The circuit presented in Figure 2 employs an op amp, A1, to sum the ground centered input signal with a required DC offset. The ADS803 typically operates with a +2.5V common-mode voltage, which is established at the center tap of the ladder and connected to the IN input of the converter. Amplifier A1 operates in inverting configuration. Here, resistors R1 and R2 set the DC bias level for A1. Due to the op amp’s noise gain of +2V/V (assuming RF = RIN), the DC offset voltage applied to its noninverting input has to be divided down to +1.25V, resulting in a DC output voltage of +2.5V. DC voltage differences between the IN and IN inputs of the ADS803 will effectively produce an offset, which can be corrected for by adjusting the values of resistors R1 and R2. The bias current of the op amp may also result in an undesired offset. The selection criteria of the appropriate op amp should include the input bias current, output voltage swing, distortion, and noise specification. Note that in this example the overall signal phase is inverted. To re-establish the original signal polarity it is always possible to interchange the IN and IN connections. SINGLE-ENDED-TO-DIFFERENTIAL CONFIGURATION (TRANSFORMER COUPLED) In order to select the best suited interface circuit for the ADS803, the performance requirements must be known. If an ac-coupled input is needed for a particular application, the next step is to determine the method of applying the signal; either single-ended or differentially. The differential input configuration may provide a noticeable advantage of achieving good SFDR performance based on the fact that in the differential mode, the signal swing can be reduced to half of the swing required for single-ended drive. Secondly, by driving the ADS803 differentially, the even-order harmonics will be reduced. See Figure 3 for the schematic of the suggested transformer coupled interface circuit. The resistor across the secondary side (RT) should be set to get an input impedance match (e.g., RT = n2 • RG). RF RIN +1V 0 +VS VIN REFT 2kΩ RS 24.9Ω IN OPA691 –1V 2Vp-p 100pF R1 ADS803 R2 +VS +2.5V 0.1µF + 10µF IN 0.1µF REFB (+1V) VREF SEL 2kΩ NOTE: RF = RIN, G = –1 FIGURE 2. DC-Coupled, Single-Ended Input Configuration with DC-Level Shift. 8 ADS803 www.ti.com SBAS074B MODE INPUT FULL-SCALE RANGE REQUIRED VREF CONNECT TO Internal 2Vp-p +1V SEL VREF RG 0.1µF 22Ω 1:n VIN IN 100pF ADS803 RT Internal 5Vp-p +2.5V SEL GND Internal 2V ≤ FSR < 5V 1V < VREF < 2.5V R1 VREF and SEL SEL and GND 22Ω IN External CM FSR = 2 x VREF VREF = 1 + (R1/R2) R2 1V < FSR < 5V 0.5V < VREF < 2.5V SEL +VS VREF Ext. VREF 100pF + TABLE I. Selected Reference Configuration Examples. 4.7µF 0.1µF FIGURE 3. Transformer-Coupled Input REFERENCE OPERATION Integrated into the ADS803 is a bandgap reference circuit including logic that provides either a +1V or +2.5V reference output by simply selecting the corresponding pin-strap configuration. Different reference voltages can be generated by the use of two external resistors, which will set a different gain for the internal reference buffer. For more design flexibility, the internal reference can be shut off and an external reference voltage used. Table I provides an overview of the possible reference options and pin configurations. A simple model of the internal reference circuit is shown in Figure 4. The internal blocks are a 1V-bandgap voltage reference, buffer, the resistive reference ladder, and the drivers for the top and bottom reference that supply the necessary current to the internal nodes. As shown, the output of the buffer appears at the VREF pin. The full-scale input span of the ADS803 is determined by the voltage at VREF, according to Equation 1: Full-Scale Input Span = 2 • VREF (1) Note that the current drive capability of this amplifier is limited to approximately 1mA and should not be used to drive low loads. The programmable reference circuit is controlled by the voltage applied to the select pin (SEL). Refer to Table I for an overview. Disable Switch SEL VREF 1VDC to A/D REFT Resistor Network and Switches 800Ω Bandgap and Logic Reference Driver CM 800Ω REFB to A/D ADS803 FIGURE 4. Equivalent Reference Circuit. ADS803 SBAS074B www.ti.com 9 The top reference (REFT) and the bottom reference (REFB) are brought out mainly for external bypassing. For proper operation with all reference configurations, it is necessary to provide solid bypassing to the reference pins in order to keep the clock feedthrough to a minimum. Figure 5 shows the recommended decoupling network. 5V VIN IN 0V ADS803 IN ADS803 REFB REFT VREF SEL +2.5V CM VREF 0.1µF FIGURE 7. Internal Reference with 0V to 5V Input Range. 10µF + 0.1µF + 0.1µF 0.1µF 10µF 0.1µF 3.5V VIN FIGURE 5. Recommended Reference Bypassing Scheme. IN 1.5V ADS803 In addition, the common-mode voltage (CMV) may be used as a reference level to provide the appropriate offset for the driving circuitry. However, care must be taken not to appreciably load this node, which is not buffered and has a high impedance. An alternate method of generating a common-mode voltage is given in Figure 6. Here, two external precision resistors (tolerance 1% or better) are located between the top and bottom reference pins. The common-mode level will appear at the midpoint. The output buffers of the top and bottom reference are designed to supply approximately 2mA of output current. +2.5V ext. IN VREF SEL +1V FIGURE 8. Internal Reference with 1.5V to 3.5V Input Range. 4V IN 1V ADS803 IN REFT +2.5V ext. 0.1µF IN R1 ADS803 VREF SEL R1 5kΩ CMV R2 IN REFB VREF = 1V 1 + 0.1µF R1 +1.5V R2 R2 10kΩ FSR = 2 • VREF FIGURE 6. Alternative Circuit to Generate CM Voltage. FIGURE 9. Internal Reference with 1V to 4V Input Range. SELECTING THE INPUT RANGE AND REFERENCE Figures 7 through 9 show a selection of circuits for the most common input ranges when using the internal reference of the ADS803. All examples are for single-ended inputs and operate with a nominal common-mode voltage of +2.5V. 10 EXTERNAL REFERENCE OPERATION Depending on the application requirements, it might be advantageous to operate the ADS803 with an external reference. This may improve the DC accuracy if the external ADS803 www.ti.com SBAS074B reference circuitry is superior in its drift and accuracy. To use the ADS803 with an external reference, the user must disable the internal reference, as shown in Figure 10. By connecting the SEL pin to +VS, the internal logic will shut down the internal reference. At the same time, the output of the internal reference buffer is disconnected from the VREF pin, which must now be driven with the external reference. Note that a similar bypassing scheme should be maintained as described for the internal reference operation. 4.5V VIN ADS803 + VREF SEL 0.1µF 10µF 1.24kΩ +2VDC OVR Under = H Therefore, this edge should have the lowest possible jitter. The jitter noise contribution to total SNR is given by the following equation. If this value is near your system requirements, input clock jitter must be reduced. +2.5V ext. IN +5V JitterSNR = 20 log 1 rms signal to rms noise 2π ƒ IN t A where: ƒIN is Input Signal Frequency tA is rms Clock Jitter 4.99kΩ FIGURE 10. External Reference, Input Range 0.5V to 4.5V (4Vp-p), with +2.5V Common-Mode Voltage. DIGITAL INPUTS AND OUTPUTS Over-Range (OVR) One feature of the ADS803 is its ‘Over-Range’ (OVR) digital output. This pin can be used to monitor any out-of-range condition, which occurs every time the applied analog input voltage exceeds the input range (set by VREF). The OVR output is LOW when the input voltage is within the defined input range. It becomes HIGH when the input voltage is beyond the input range. This is the case when the input voltage is either below the bottom reference voltage or above the top reference voltage. OVR will remain active until the analog input returns to its normal signal range and another conversion is completed. Using the MSB and its complement in conjunction with OVR, a simple clue logic can be built that detects the over-range and under-range conditions, as shown in Figure 11. It should be noted that OVR is a digital output that is updated along with the bit information corresponding to the particular sampling incidence of the analog signal. Therefore, the OVR data is subject to the same pipeline delay (latency) as the digital data. CLOCK INPUT REQUIREMENTS Clock jitter is critical to the SNR performance of high-speed, high-resolution A/D converters. It leads to aperture jitter (tA) which adds noise to the signal being converted. The ADS803 samples the input signal on the rising edge of the CLK input. Particularly in undersampling applications, special consideration should be given to clock jitter. The clock input should be treated as an analog input in order to achieve the highest level of performance. Any overshoot or undershoot of the clock signal may cause degradation of the performance. When digitizing at high sampling rates, the clock should have a 50% duty cycle (tH = tL), along with fast rise and fall times of 2ns or less. DIGITAL OUTPUTS The digital outputs of the ADS803 are designed to be compatible with both high speed TTL and CMOS logic families. The driver stage for the digital outputs is supplied through a separate supply pin, VDRV, which is not connected to the analog supply pins. By adjusting the voltage on VDRV, the digital output levels will vary respectively. Therefore, it is possible to operate the ADS803 on a +5V analog supply while interfacing the digital outputs to 3V logic. It is recommended to keep the capacitive loading on the data lines as low as possible (≤ 15pF). Larger capacitive loads demand higher charging currents as the outputs are changing. Those high current surges can feed back to the analog portion of the ADS803 and influence the performance. If necessary, external buffers or latches may be used, which provide the added benefit of isolating the ADS803 from any digital noise activities on the bus coupling back high-frequency noise. In addition, resistors in series with each data line may help maintain the ac performance of the ADS803. Their use depends on the capacitive loading seen by the converter. Values in the range of 100Ω to 200Ω will limit the instantaneous current the output stage has to provide for recharging the parasitic capacitances as the output levels change from LOW to HIGH or HIGH to LOW. ADS803 SBAS074B Over = H FIGURE 11. External Logic for Decoding Under- and OverRange Conditions. IN 0.5V REF1004 +2.5V MSB www.ti.com 11 GROUNDING AND DECOUPLING Proper grounding and bypassing, short lead length, and the use of ground planes are particularly important for highfrequency designs. Multi-layer PC boards are recommended for best performance, since they offer distinct advantages like minimizing ground impedance, separation of signal layers by ground layers, etc. It is recommended that the analog and digital ground pins of the ADS803 be joined together at the IC and be connected only to the analog ground of the system. analog supplies. In most cases, 0.1µF ceramic chip capacitors are adequate to keep the impedance low over a wide frequency range. Their effectiveness largely depends on the proximity to the individual supply pin. Therefore, they should be located as close to the supply pins as possible. In addition, a larger size bipolar capacitor (1µF to 22µF) should be placed on the PC board in close proximity to the converter circuit. The ADS803 has analog and digital supply pins, however, the converter should be treated as an analog component and all supply pins should be powered by the analog supply. This will ensure the most consistent results, since digital supply lines often carry high levels of noise that would otherwise be coupled into the converter and degrade the achievable performance. Due to the pipeline architecture, the converter also generates high-frequency current transients and noise that are fed back into the supply and reference lines. This requires that the supply and reference pins be sufficiently bypassed. Figure 12 shows the recommended decoupling scheme for the 12 ADS803 +VS 27 GND 26 +VS 16 0.1µF GND 17 0.1µF VDRV 28 0.1µF 2.2µF + +5V +5V/+3V FIGURE 12. Recommended Bypassing for Analog Supply Pins. ADS803 www.ti.com SBAS074B PACKAGE OPTION ADDENDUM www.ti.com 10-Dec-2020 PACKAGING INFORMATION Orderable Device Status (1) Package Type Package Pins Package Drawing Qty Eco Plan (2) Lead finish/ Ball material MSL Peak Temp Op Temp (°C) Device Marking (3) (4/5) (6) ADS803E ACTIVE SSOP DB 28 50 RoHS & Green NIPDAU Level-2-260C-1 YEAR -40 to 85 ADS803E ADS803E/1K ACTIVE SSOP DB 28 1000 RoHS & Green NIPDAU Level-2-260C-1 YEAR -40 to 85 ADS803E (1) The marketing status values are defined as follows: ACTIVE: Product device recommended for new designs. LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect. NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design. PREVIEW: Device has been announced but is not in production. Samples may or may not be available. OBSOLETE: TI has discontinued the production of the device. (2) RoHS: TI defines "RoHS" to mean semiconductor products that are compliant with the current EU RoHS requirements for all 10 RoHS substances, including the requirement that RoHS substance do not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, "RoHS" products are suitable for use in specified lead-free processes. TI may reference these types of products as "Pb-Free". RoHS Exempt: TI defines "RoHS Exempt" to mean products that contain lead but are compliant with EU RoHS pursuant to a specific EU RoHS exemption. Green: TI defines "Green" to mean the content of Chlorine (Cl) and Bromine (Br) based flame retardants meet JS709B low halogen requirements of