ADS930E/1KG4

ADS930 ADS 930 E SBAS059A – MARCH 2001 8-Bit, 30MHz Sampling ANALOG-TO-DIGITAL CONVERTER TM FEATURES ● ● ● ● ● ● ● DESCRIPTION +3V TO +5V SUPPLY OPERATION INTERNAL REFERENCE SINGLE-ENDED INPUT RANGE: 1V to 2V LOW POWER: 66mW at +3V HIGH SNR: 46dB LOW DNL: 0.4LSB SSOP-28 PACKAGE The ADS930 is a high speed pipelined Analog-to-Digital Converter (ADC) specified to operate from nominal +3V or +5V power supplies with tolerances of up to 10%. This complete converter includes a high bandwidth track/hold, a 8-bit quantizer and an internal reference. The ADS930 employs digital error correction techniques to provide excellent differential linearity for demanding imaging applications. Its low distortion and high SNR give the extra margin needed for telecommunications, video and test instrumentation applications. APPLICATIONS ● ● ● ● ● This high performance ADC is specified for performance at a 30MHz sampling rate. The ADS930 is available in a SSOP-28 package. BATTERY POWERED EQUIPMENT CAMCORDERS PORTABLE TEST EQUIPMENT COMPUTER SCANNERS COMMUNICATIONS CLK LVDD ADS930 Timing Circuitry 2V IN 1V T/H IN (Opt.) Pipeline A/D Error Correction 3-State Outputs 8-Bit Digital Data Internal Reference LpBy CM LnBy 1VREF Pwrdn OE Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet. Copyright © 2001, Texas Instruments Incorporated PRODUCTION DATA information is current as of publication date. Products conform to specifications per the terms of Texas Instruments standard warranty. Production processing does not necessarily include testing of all parameters. www.ti.com ABSOLUTE MAXIMUM RATINGS ELECTROSTATIC DISCHARGE SENSITIVITY +VS ....................................................................................................... +6V Analog Input ............................................................................... +VS +0.3V Logic Input ................................................................................. +VS +0.3V Case Temperature ......................................................................... +100°C Junction Temperature .................................................................... +150°C Storage Temperature ..................................................................... +150°C This integrated circuit can be damaged by ESD. Texas Instruments recommends that all integrated circuits be handled with appropriate precautions. Failure to observe proper handling and installation procedures can cause damage. ESD damage can range from subtle performance degradation to complete device failure. Precision integrated circuits may be more susceptible to damage because very small parametric changes could cause the device not to meet its published specifications. PACKAGE/ORDERING INFORMATION PRODUCT PACKAGE PACKAGE DRAWING NUMBER ADS930E SSOP-28 324 –40°C to +85°C " " " " SPECIFIED TEMPERATURE RANGE PACKAGE MARKING ORDERING NUMBER(1) TRANSPORT MEDIA ADS930E ADS930E ADS930E ADS930E/1K Rails Tape and Reel NOTE: (1) Models with a slash (/) are available only in Tape and Reel in the quantities indicated (e.g., /1K indicates 1000 devices per reel). Ordering 1000 pieces of “ADS930E/1K” will get a single 1000-piece Tape and Reel. ELECTRICAL CHARACTERISTICS At TA = +25°C, VS = +3V, Single-ended Input and Sampling Rate = 30MHz, unless otherwise specified. ADS930E PARAMETER RESOLUTION Specified Temperature Range ANALOG INPUT Differential Full Scale Input Range Single-Ended Full Scale Input Range Common-mode Voltage Analog Input Bias Current Input Impedance CONDITIONS Signal-to-(Noise + Distortion) (SINAD) f = 500kHz (–1dBFS input) f = 3.58MHz (–1dBFS input) f = 12MHz (–1dBFS input) 2 TYP MAX UNITS Bits °C 8 –40 +85 0.5Vp-p 1Vp-p +1.25 +1.0 +1.75 +2.0 1.5 1 1.25 || 5 V V V µA MΩ || pF TTL/HCT Compatible CMOS 2.0 VDD 0.8 ±10 ±10 5 V V µA µA pF Full Rising Edge of Convert Clock 10k 30M 5 Samples/s Clk Cyc Full Full Full ±0.4 ±0.4 Guaranteed ±1 LSB LSB Full ±1.0 ±2.5 LSB Full CONVERSION CHARACTERISTICS Start Conversion Sample Rate Data Latency Integral Nonlinearity Error, f = 500kHz Spurious Free Dynamic Range(1) f = 500kHz (–1dBFS input) f = 12MHz (–1dB input) Two-Tone Intermodulation Distortion(3) f = 3.4MHz and 3.5MHz (–7dBFS each tone) Signal-to-Noise Ratio (SNR) f = 500kHz (–1dBFS input) f = 12MHz (–1dBFS input) MIN Ambient Air DIGITAL INPUTS Logic Family High Input Voltage, VIH Low Input Voltage, VIL High Input Current, IIH Low Input Current, IIL Input Capacitance DYNAMIC CHARACTERISTICS Differential Linearity Error f = 500kHz f = 12MHz No Missing Codes TEMP Largest Code Error Largest Code Error Full Full Full Full Full Full Full 51 50 dBFS(2) dBFS 54 dBc 44 46 46 dB dB 42 45 45 45 dB dB dB 46 ADS930 SBAS059A ELECTRICAL CHARACTERISTICS (Cont.) At TA = +25°C, VS = +3V, Single-ended Input and Sampling Rate = 30MHz, unless otherwise specified. ADS930E PARAMETER Differential Gain Error Differential Phase Error Output Noise Aperture Delay Time Aperture Jitter Analog Input Bandwidth Small Signal Full Power Overvoltage Recovery Time(4) DIGITAL OUTPUTS Logic Family Logic Coding High Output Voltage, VOH Low Output Voltage, VOL 3-State Enable Time 3-State Disable Time Internal Pull-Down Power-Down Enable Time Power-Down Disable Time Internal Pull-Down ACCURACY Gain Error Input Offset Power Supply Rejection (Gain) Power Supply Rejection (Offset) Internal Positive Reference Voltage Internal Negative Reference Voltage POWER SUPPLY REQUIREMENTS Supply Voltage: +VS Supply Current: +IS Power Dissipation Power Dissipation (Power Down) Thermal Resistance, θJA SSOP-28 CONDITIONS TEMP MIN TYP MAX UNITS NTSC, PAL NTSC, PAL Input Grounded 2.3 1 0.2 2 7 % degrees LSBs rms ns ps rms –20dBFS Input 0dBFS Input 350 100 2 MHz MHz ns TTL/HCT Compatible CMOS Straight Offset Binary +2.4 LVDD 0.4 20 40 2 10 50 133 18 50 V V ns ns kΩ ns ns kΩ 5.9 ±10 56 56 +1.75 +1.25 10 ±60 %FS mV dB dB V V +3.0 22 66 168 10 15 +5.25 V mA mW mW mW mW CL = 15pF OE = L OE = H PwrDn = L PwrDn = H fS = 2.5MHz Referred to Ideal Midscale ∆ VS = +10% Operating Operating, +3V Operating, +3V Operating, +5V Operating, +3V Operating, +5V Full Full Full Full Full Full Full Full Full Full Full Full +2.7 89 84 °C/W NOTES: (1) Spurious Free Dynamic Range refers to the magnitude of the largest harmonic. (2) dBFS means dB relative to full scale. (3) Two-tone intermodulation distortion is referred to the largest fundamental tone. This number will be 6dB higher if it is referred to the magnitude of the two-tone fundamental envelope. (4) No “Rollover” of bits. ADS930 SBAS059A 3 PIN CONFIGURATION PIN DESCRIPTIONS Top View SSOP +VS 1 28 +VS LVDD 2 27 +IN NC 3 26 CM NC 4 25 LnBy LSB Bit 8 5 24 IN Bit 7 6 23 1VREF Bit 6 7 22 NC Bit 5 8 21 LpBy Bit 4 9 20 GND Bit 3 10 19 GND Bit 2 11 18 +VS MSB Bit 1 12 17 Pwrdn GND 13 16 OE GND 14 15 CLK ADS930 PIN DESIGNATOR 1 2 3 4 5 6 7 8 9 10 11 12 13 14 15 16 17 18 19 20 21 22 23 24 25 26 27 28 +VS LVDD NC NC Bit 8 (LSB) Bit 7 Bit 6 Bit 5 Bit 4 Bit 3 Bit 2 Bit 1(MSB) GND GND CLK OE Pwrdn +VS GND GND LpBy NC 1VREF IN LnBy CM +IN +VS DESCRIPTION Analog Supply Output Logic Driver Supply Voltage No Connection No Connection Data Bit 8 (D7) Data Bit 7 (D6) Data Bit 6 (D5) Data Bit 5 (D4) Data Bit 4 (D3) Data Bit 3 (D2) Data Bit 2 (D1) Data Bit 1 (D0) Analog Ground Analog Ground Convert Clock Input Output Enable, Active Low Power Down Pin Analog Supply Analog Ground Analog Ground Positive Ladder Bypass No Connection 1V Reference Output Complementary Input Negative Ladder Bypass Common-Mode Voltage Output Analog Input Analog Supply TIMING DIAGRAM N+2 N+1 Analog In N+4 N+3 N tD N+5 tL tCONV N+6 N+7 tH Clock 5 Clock Cycles t2 Data Out N–5 N–4 N–3 N–2 N–1 N Data Invalid SYMBOL tCONV tL tH tD t1 t2 4 N+1 N+2 t1 DESCRIPTION MIN Convert Clock Period Clock Pulse Low Clock Pulse High Aperture Delay Data Hold Time, CL = 0pF New Data Delay Time, CL = 15pF max 33 15.5 15.5 TYP MAX UNITS 100µs ns ns ns ns ns ns 16.5 16.5 2 3.9 12 ADS930 SBAS059A TYPICAL CHARACTERISTICS At TA = +25°C, VS = +3V, Single-ended Input and Sampling Rate = 30MHz, unless otherwise specified. SPECTRAL PERFORMANCE SPECTRAL PERFORMANCE 0 0 fIN = 500kHz fIN = 3.58MHz –20 Amplitude (dB) Amplitude (dB) –20 –40 –60 –40 –60 –80 –80 –100 –100 0 5 10 0 15 5 10 SPECTRAL PERFORMANCE TWO-TONE INTERMODULATION 0 0 fIN = 12MHz f1 = 3.5MHz at –7dBFS f2 = 3.4MHz at –7dBFS 2f1 –f2 = 54.7dBFS 2f2 –f1 = 54.2dBFS –20 Magnitude (dBFS) Amplitude (dB) –20 –40 –60 –80 –40 –60 –80 –100 –100 0 5 10 15 0 2 4 Frequency (MHz) 6 8 10 Frequency (MHz) DIFFERENTIAL LINEARITY ERROR DIFFERENTIAL LINEARITY ERROR 2.0 2.0 fIN = 500kHz fIN = 12MHz 1.0 DLE (LSB) 1.0 DLE (LSB) 15 Frequency (MHz) Frequency (MHz) 0.0 0.0 –1.0 –1.0 –2.0 –2.0 0 64 128 Output Code ADS930 SBAS059A 192 256 0 64 128 192 256 Output Code 5 TYPICAL CHARACTERISTICS (Cont.) At TA = +25°C, VS = +3V, Single-ended Input and Sampling Rate = 30MHz, unless otherwise specified. SWEPT POWER SFDR INTEGRAL LINEARITY ERROR 100 4.0 fIN = 500kHz SFDR (dBFS, dBc) 2.0 ILE (LSB) dBFS 80 0 –2.0 60 40 20 dBc –4.0 0 64 128 192 0 256 –50 –40 Output Code –20 –10 0 UNDERSAMPLING (With Differential Input) DYNAMIC PERFORMANCE vs INPUT FREQUENCY 0 52 fIN = 20MHz fS = 16MHz –20 Amplitude (dB) SFDR SFDR, SNR (dB) –30 Input Amplitude (dBFS) 50 48 –40 –60 –80 SNR –100 –120 46 0.1 1 10 0 100 1.6 3.2 4.8 6.4 Frequency (MHz) Frequency (MHz) DIFFERENTIAL LINEARITY ERROR vs TEMPERATURE SPURIOUS FREE DYNAMIC RANGE vs TEMPERATURE 0.7 8.0 54 fIN = 500kHz 0.6 SFDR (dBFS) DLE (LSB) 52 0.5 0.4 50 fIN = 12MHz 48 0.3 fIN = 500kHz fIN = 10MHz 0.2 46 –50 –25 0 25 50 Temperature (°C) 6 75 100 –50 –25 0 25 50 75 100 Temperature (°C) ADS930 SBAS059A TYPICAL CHARACTERISTICS (Cont.) At TA = +25°C, VS = +3V, Single-ended Input and Sampling Rate = 30MHz, unless otherwise specified. SIGNAL-TO-NOISE RATIO vs TEMPERATURE POWER DISSIPATION vs TEMPERATURE 48 SNR (dB) 47 Power Dissipation (mW) 69 fIN = 12MHz 46 fIN = 500kHz 45 44 –50 68 67 66 65 –25 0 25 50 75 100 –50 –25 0 Temperature (°C) GAIN ERROR vs TEMPERATURE 50 75 100 OFFSET ERROR vs TEMPERATURE 6.5 7 6.0 6 Offset Error (mV) Gain (%FSR) 25 Temperature (°C) 5.5 5.0 5 4 4.5 3 –50 –25 0 25 50 75 100 –50 –25 Temperature (°C) 0 25 50 75 100 Temperature (°C) OUTPUT NOISE HISTOGRAM (DC Input) 12 Counts (x 105) 10 8 6 4 2 0 N–2 N–1 N N+1 N+2 Output Code ADS930 SBAS059A 7 THEORY OF OPERATION Op Amp Bias The ADS930 is a high speed sampling ADC that utilizes a pipeline architecture. The fully differential topology and digital error correction guarantee 8-bit resolution. The track/ hold circuit is shown in Figure 1. The switches are controlled by an internal clock which has a non-overlapping two phase signal, φ1 and φ2. At the sampling time the input signal is sampled on the bottom plates of the input capacitors. In the next clock phase, φ2, the bottom plates of the input capacitors are connected together and the feedback capacitors are switched to the op amp output. At this time the charge redistributes between CI and CH, completing one track/hold cycle. The differential output is a held DC representation of the analog input at the sample time. In the normal mode of operation, the complementary input is tied to the common-mode voltage. In this case, the track/hold circuit converts a single-ended input signal into a fully differential signal for the quantizer. Consequently, the input signal gets amplified by a gain or two, which improves the signal-to-noise performance. Other parameters such as smallsignal and full-power bandwidth, and wideband noise are also defined in this stage. IN IN φ1 CH φ2 CI IN IN (Opt.) φ1 φ2 OUT φ1 OUT φ1 CI φ2 CH φ1 φ1 Input Clock (50%) Op Amp Bias VCM Internal Non-overlapping Clock φ1 φ2 φ1 FIGURE 1. Input Track/Hold Configuration with Timing Signals. Digital Delay Input T/H (Opt.) 2-Bit Flash STAGE 1 φ1 VCM 2-Bit DAC + Σ – x2 Digital Delay 2-Bit Flash 2-Bit DAC Digital Error Correction B1 (MSB) STAGE 2 + Σ – x2 B2 B3 B4 B5 B6 B7 B8 (LSB) Digital Delay 2-Bit Flash STAGE 6 2-Bit DAC + Σ – x2 STAGE 7 2-Bit Flash Digital Delay FIGURE 2. Pipeline ADC Architecture. 8 ADS930 SBAS059A The pipelined quantizer architecture has 7 stages with each stage containing a two-bit quantizer and a two bit Digitalto-Analog Converter (DAC), as shown in Figure 2. Each two-bit quantizer stage converts on the edge of the subclock, which is the same frequency of the externally applied clock. The output of each quantizer is fed into its own delay line to time-align it with the data created from the subsequent quantizer stages. This aligned data is fed into a digital error correction circuit which can adjust the output data based on the information found on the redundant bits. This technique provides the ADS930 with excellent differential linearity and guarantees no missing codes at the 8-bit level. The ADS930 includes an internal reference circuit that provides the bias voltages for the internal stages (for details see “Internal Reference”). A midpoint voltage is established by the built-in resistor ladder which is made available at pin 26 “CM”. This voltage can be used to bias the inputs up to the recommended common-mode voltage or to level shift the input driving circuitry. The ADS930 can be used in both a single-ended or differential input configuration. When operated in single-ended mode, the reference midpoint (pin 26) should be tied to the inverting input, pin 24. To accommodate a bipolar signal swing, the ADS930 operates with a common-mode voltage (VCM) which is derived from the internal references. Due to the symmetric resistor ladder inside the ADS930, VCM is situated between the top and bottom reference voltage. The following equation can be used for calculating the common-mode voltage level: VCM = (REFT +REFB)/2 signal. The capacitor C1 and resistor R1 form a high-pass filter with the –3dB frequency set at f–3dB = 1/(2 π R1 C1) (2) The values for C1 and R1 are not critical in most applications and can be set freely. The values shown in Figure 3 correspond to a corner frequency of 1.6kHz. Figure 4 depicts a circuit that can be used in single-supply applications. The mid-reference biases the op amp up to the appropriate common-mode voltage, for example VCM = +1.5V. With the use of capacitor CG, the DC gain for the non-inverting op amp input is set to +1V/V. As a result, the transfer function is modified to VOUT = VIN {(1 + RF/RG) + VCM} (3) Again, the input coupling capacitor C1 and resistor R1 form a high-pass filter. At the same time, the input impedance is defined by R1. Resistor RS isolates the op amp’s output from the capacitive load to avoid gain peaking or even oscillation. It can also be used to establish a defined bandwidth to reduce the wideband noise. Its value is usually between 10Ω and 100Ω. +3V +5V VIN (1) C1 10Ω 0.1µF OPA650 OPA658 IN IN R1 1kΩ –5V APPLICATIONS ADS930 CM 402Ω VCM DRIVING THE ANALOG INPUTS Figure 3 shows an example of an ac-coupled, single-ended interface circuit using high-speed op amps which operate on dual supplies (OPA650, OPA658). The mid-point reference voltage, (VCM), biases the bipolar, ground-referenced input 402Ω FIGURE 3. AC-Coupled Driver. +3V +5V C1 0.1µF 0.1µF RS 50Ω VIN IN OPA680 R1 1kΩ 22pF IN ADS930 CM VCM RF 402Ω RG 402Ω CG 0.1µF 0.1µF RP 402Ω FIGURE 4. Interface Circuit Example Using the Voltage Feedback Amplifier OPA680. ADS930 SBAS059A 9 DC-COUPLED INTERFACE CIRCUIT Figure 5 illustrates an example of a DC-coupled interface circuit using one high-speed op amp to level-shift the groundreferenced input signal. This serves to condition it for the input requirements of the ADS930. With a +3V supply the input signal swings 1Vp-p centered around a typical common-mode voltage of +1.5V. This voltage can be derived from the internal bottom reference (REFB) and then fed back through a resistor divider (R1, R2) to level-shift the driving op amp (A1). A capacitor across R2 will shunt most of the wideband noise to ground. Depending on the configured gain, the values of resistors R1 and R2 must be adjusted since the offsetting voltage (VOS) is amplified by the noninverting gain, 1 + (RF / RIN). This example assumes the sum of R1 and R2 to be 5kΩ, drawing only 250µA from the bottom reference. Considerations for the selection of a proper op amp should include its output swing, input common-mode range, and bias current. This circuit can easily be modified for a +5V operation of the ADC, requiring a higher common-mode level (+2.5V). Figure 6, each end of the resistor ladder (REFT and REFB) are driven by a buffer amplifier. The ladder has a nominal resistance of 4kΩ (±15%). The two outputs of the buffers are brought out at pin 21 (LpBy) and pin 25 (LnBy), primarily to connect external bypass capacitors, typically 0.1µF. They will shunt the high frequency switching noise that is fed back into the reference circuit and improve the performance. The buffers can drive limited external loads, for example level-shifting of the converter’s interface circuit. However, the current draw should be limited to approximately 1mA. Derived from the top reference of +1.75V is an additional voltage of +1.0V. Note that this voltage, available on pin 23, is not buffered and care should be taken when external loads are applied. In normal operation, this pin is left unconnected and no bypassing components are required. CLOCK INPUT The clock input of the ADS930 is designed to accommodate either +5V or +3V CMOS logic levels. To drive the clock input with a minimum amount of duty cycle variation and support the maximum sampling rate (30MSPS), high speed or advanced CMOS logic should be used (HC/HCT, AC/ACT). When digitizing at high sampling rates, a 50% duty cycle, along with fast rise and fall times (2ns or less), INTERNAL REFERENCE The ADS930 features an internal reference that provides fixed reference voltages for the internal stages. As shown in +5V RF +3V VCM = 1.5V RIN RS VIN ADS930 IN OPA680 22pF IN REFB +1.25V CM VOS 0.1µF 0.1µF R2 R1 0.1µF I = 250µA FIGURE 5. Single-supply, DC-coupled Interface Circuit. ADS930 +1.75V 21 REFT LpBy 0.1µF 2kΩ CM 2.1kΩ 23 26 +1VREF 2.8kΩ 0.1µF 2kΩ +1.25V REFB 25 LnBy 0.1µF FIGURE 6. Internal Reference Structure and Recommended Reference Bypassing. 10 ADS930 SBAS059A are recommended to meet the rated performance specifications. However, the ADS930 performance is tolerant to duty cycle variations of as much as ±10%, which should not affect the performance. For applications operating with input frequencies up to Nyquist (fCLK/2) or undersampling applications, special considerations must be made to provide a clock with very low jitter. Clock jitter leads to aperture jitter (tA) which can be the ultimate limitation in achieving good SNR performance. The following equation shows the relationship between aperture jitter, input frequency and the signal-to-noise ratio: SNR = 20log10 [1/(2 π fIN tA)] SINGLE-ENDED INPUT (IN = 1.5V DC) STRAIGHT OFFSET BINARY (SOB) PIN 12 FLOATING or LO +FS (IN = +2V) +FS –1LSB +FS –2LSB +3/4 Full Scale +1/2 Full Scale +1/4 Full Scale +1LSB Bipolar Zero (IN +1.5V) –1LSB –1/4 Full Scale –1/2 Full Scale –3/4 Full Scale –FS +1LSB –FS (IN = +1V) 11111111 11111111 11111110 11100000 11000000 10100000 10000001 10000000 01111111 01100000 01000000 00100000 00000001 00000000 (4) TABLE I. Coding Table for the ADS930. DIGITAL OUTPUTS There is a 5.0 clock cycle data latency from the start convert signal to the valid output data. The standard output coding is Straight Offset Binary where a full scale input signal corresponds to all “1’s” at the output. The digital outputs of the ADS930 can be set to a high impedance state by driving the OE (pin 16) with a logic “HI”. Normal operation is achieved with pin 16 “LO” or Floating due to internal pulldown resistors. This function is provided for testability purposes but is not recommended to be used dynamically. The digital outputs of the ADS930 are standard CMOS stages and designed to be compatible to both high speed TTL and CMOS logic families. The logic thresholds are for low-voltage CMOS: VOL = 0.4V, VOH = 2.4V, which allows the ADS930 to directly interface to 3V-logic. The digital output driver of the ADS930 uses a dedicated digital supply pin (pin 2, LVDD) see Figure 7. By adjusting the voltage on +VS LVDD, the digital output levels will vary respectively. It is recommended to limit the fan-out to one in order to keep the capacitive loading on the data lines below the specified 15pF. If necessary, external buffers or latches may be used to provide the added benefit of isolating the ADC from any digital activities on the bus coupling back high frequency noise which degrades the performance. POWER-DOWN MODE The ADS930’s low power consumption can be reduced even further by initiating a power-down mode. For this, the Power Down Pin (Pin 17) must be tied to a logic “High” reducing the current drawn from the supply by approximately 70%. In normal operation, the power-down mode is disabled by an internal pull-down resistor (50kΩ). During power-down, the digital outputs are set in 3-state. With the clock applied, the converter does not accurately process the sampled signal. After removing the power-down condition, the output data from the following 5 clock cycles is invalid (data latency). DECOUPLING AND GROUNDING CONSIDERATIONS The ADS930 has several supply pins, one of which is dedicated to supply only the output driver (LVDD). The remaining supply pins are not divided into analog and digital supply pins since they are internally connected on the chip. For this reason, it is recommended that the converter be treated as an analog component and to power it from the analog supply only. Digital supply lines often carry high levels of noise which can couple back into the converter and limit performance. Because of the pipeline architecture, the converter also generates high frequency transients and noise that are fed back into the supply and reference lines. This requires that the supply and reference pins be sufficiently bypassed. Figure 8 shows the recommended decoupling scheme for the analog supplies. In most cases 0.1µF ceramic chip capacitors are adequate to keep the impedance low over a wide frequency range. Their effectiveness largely depends on the proximity to the individual supply pin. Therefore, they should be located as close as possible to the supply pins. ADS930 VS 1 GND 13 14 GND 19 20 VS 28 +LVDD 0.1µF ADS930 VS 18 Digital Output Stage 0.1µF 0.1µF FIGURE 8. Recommended Bypassing for Analog Supply Pins. FIGURE 7. Independent Supply Connection for Output Stage. ADS930 SBAS059A 11 PACKAGE OPTION ADDENDUM www.ti.com 10-Dec-2020 PACKAGING INFORMATION Orderable Device Status (1) Package Type Package Pins Package Drawing Qty Eco Plan (2) Lead finish/ Ball material MSL Peak Temp Op Temp (°C) Device Marking (3) (4/5) (6) ADS930E ACTIVE SSOP DB 28 50 RoHS & Green NIPDAU Level-2-260C-1 YEAR -40 to 85 ADS930E ADS930E/1K ACTIVE SSOP DB 28 1000 RoHS & Green NIPDAU Level-1-260C-UNLIM -40 to 85 ADS930E (1) The marketing status values are defined as follows: ACTIVE: Product device recommended for new designs. LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect. NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design. PREVIEW: Device has been announced but is not in production. Samples may or may not be available. OBSOLETE: TI has discontinued the production of the device. (2) RoHS: TI defines "RoHS" to mean semiconductor products that are compliant with the current EU RoHS requirements for all 10 RoHS substances, including the requirement that RoHS substance do not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, "RoHS" products are suitable for use in specified lead-free processes. TI may reference these types of products as "Pb-Free". RoHS Exempt: TI defines "RoHS Exempt" to mean products that contain lead but are compliant with EU RoHS pursuant to a specific EU RoHS exemption. Green: TI defines "Green" to mean the content of Chlorine (Cl) and Bromine (Br) based flame retardants meet JS709B low halogen requirements of