CDCLVD2102
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SCAS904A – MAY 2010 – REVISED JUNE 2010
Dual 1:2 Low Additive Jitter LVDS Buffer
Check for Samples: CDCLVD2102
FEATURES
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Dual 1:2 Differential Buffer
Low Additive Jitter 3000 V
Stresses beyond those listed under “absolute maximum ratings” may cause permanent damage to the device. These are stress ratings
only and functional operation of the device at these or any other conditions beyond those indicated under recommended operating
conditions” is not implied. Exposure to absolute–maximum–rated conditions for extended periods may affect device reliability.
The outputs can handle permanent short.
RECOMMENDED OPERATING CONDITIONS
Device supply voltage, VCC
Ambient temperature, TA
MIN
TYP
MAX
2.375
2.5
2.625
–40
85
UNITS
V
oC
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THERMAL INFORMATION
CDCLVD2102
THERMAL METRIC (1)
RGT
UNITS
16 PINS
qJA
Junction-to-ambient thermal resistance
51.3
qJC(top)
Junction-to-case(top) thermal resistance
85.4
qJB
Junction-to-board thermal resistance
20.1
yJT
Junction-to-top characterization parameter
1.3
yJB
Junction-to-board characterization parameter
19.4
qJC(bottom)
Junction-to-case(bottom) thermal resistance
6
(1)
°C/W
For more information about traditional and new thermal metrics, see the IC Package Thermal Metrics application report, SPRA953.
ELECTRICAL CHARACTERISTICS:
At VCC = 2.375 V to 2.625 V and TA = –40°C to 85°C (unless otherwise noted).
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
EN PIN INPUT CHARACTERISTICS
VdI3
3-State
VdIH
Input high voltage
Open
VdIL
Input low voltage
IdIH
Input high current
VCC = 2.625 V, VIH = 2.625 V
IdIL
Input low current
VCC = 2.625 V, VIL = 0 V
Rpull(EN)
Input pull-up/ pull-down resistor
0.5×VCC
V
0.7×VCC
V
0.2×VCC
V
30
mA
–30
mA
200
kΩ
2.5V LVCMOS (see Figure 7) INPUT CHARACTERISTICS
fIN
Input frequency
External threshold voltage applied
to complementary input
Vth
Input threshold voltage
VIH
Input high voltage
VIL
Input low voltage
IIH
Input high current
VCC = 2.625 V, VIH = 2.625 V
IIL
Input low current
VCC = 2.625 V, VIL = 0 V
ΔV/ΔT
Input edge rate
20% – 80%
CIN
Input capacitance
200
MHz
1.5
V
Vth + 0.1
VCC
V
0
Vth – 0.1
V
10
mA
1.1
–10
1.5
mA
V/ns
2.5
pF
DIFFERENTIAL INPUT CHARACTERISTICS
fIN
Input frequency
Clock input
VIN,
Differential input voltage
peak-to-peak
VICM = 1.25 V
VICM
Input common-mode voltage range
VIN, DIFF, PP > 0.4V
IIH
Input high current
VCC = 2.625 V, VIH = 2.625 V
IIL
Input low current
VCC = 2.625 V, VIL = 0 V
ΔV/ΔT
Input edge rate
20% to 80%
CIN
Input capacitance
4
DIFF
800
MHz
0.3
1.6
VP-P
1
VCC – 0.3
V
10
mA
–10
mA
0.75
V/ns
2.5
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pF
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SCAS904A – MAY 2010 – REVISED JUNE 2010
ELECTRICAL CHARACTERISTICS: (continued)
At VCC = 2.375 V to 2.625 V and TA = –40°C to 85°C (unless otherwise noted).
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
250
450
mV
–15
15
mV
1.1
1.375
–15
15
LVDS OUTPUT CHARACTERISTICS
|VOD|
Differential output voltage magnitude
ΔVOD
Change in differential output voltage
magnitude
VOC(SS)
Steady-state common mode output
voltage
ΔVOC(SS)
Steady-state common mode output
voltage
VIN, DIFF, PP = 0.6 V,RL = 100 Ω
Vring
Output overshoot and undershoot
Percentage of output amplitude
VOD
VOS
Output ac common mode
VIN, DIFF, PP = 0.6 V, RL = 100 Ω
IOS
Short-circuit output current
VOD = 0 V
tPD
Propagation delay
VIN, DIFF, PP = 0.3 V
tSK, PP
Part-to-part skew
tSK, O_WB
Within bank output skew
tSK,O_BB
Bank-to-bank output skew
Both inputs are phase aligned
tSK,P
Pulse skew(with 50% duty cycle
input)
Crossing-point-to-crossing-point
distortion
tRJIT
Random additive jitter (with 50% duty
cycle input)
Edge speed = 0.75V/ns,
10 kHz – 20 MHz
tR/tF
Output rise/fall time
20% to 80%,100 Ω, 5 pF
300
ps
ICCSTAT
Static supply current
Outputs unterminated, f = 0 Hz
27
45
mA
ICC100
Supply current
All outputs enabled, RL = 100 Ω,
f = 100 MHz
49
77
mA
ICC800
Supply current
All outputs enabled, RL = 100 Ω,
f = 800 MHz
76
106
mA
1.25
1.35
V
VIN, DIFF, PP = 0.3 V,RL = 100 Ω
V
mV
10%
25
1.5
–50
70
mVPP
±24
mA
2.5
ns
600
ps
15
ps
100
ps
50
ps
0.3 ps, RMS
50
VAC_REF CHARACTERISTICS
VAC_REF
Reference output voltage
VCC = 2.5 V, Iload = 100 µA
1.1
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Typical Additive Phase Noise Characteristics for 100 MHz Clock
PARAMETER
MIN
TYP
MAX
UNIT
phn100
Phase noise at 100 Hz offset
-132.9
dBc/Hz
phn1k
Phase noise at 1 kHz offset
-138.8
dBc/Hz
phn10k
Phase noise at 10 kHz offset
-147.4
dBc/Hz
phn100k
Phase noise at 100 kHz offset
-153.6
dBc/Hz
phn1M
Phase noise at 1 MHz offset
-155.2
dBc/Hz
phn10M
Phase noise at 10 MHz offset
-156.2
dBc/Hz
phn20M
Phase noise at 20 MHz offset
-156.6
dBc/Hz
tRJIT
Random additive jitter from 10 kHz to 20 MHz
171
fs, RMS
Typical Additive Phase Noise Characteristics for 737.27 MHz Clock
PARAMETER
phn100
Phase noise at 100 Hz offset
phn1k
Phase noise at 1 kHz offset
phn10k
Phase noise at 10 kHz offset
phn100k
MIN
TYP
MAX
UNIT
-80.2
dBc/Hz
-114.3
dBc/Hz
-138
dBc/Hz
Phase noise at 100 kHz offset
-143.9
dBc/Hz
phn1M
Phase noise at 1 MHz offset
-145.2
dBc/Hz
phn10M
Phase noise at 10 MHz offset
-146.5
dBc/Hz
phn20M
Phase noise at 20 MHz offset
-146.6
dBc/Hz
tRJIT
Random additive jitter from 10 kHz to 20 MHz
65
fs, RMS
6
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SCAS904A – MAY 2010 – REVISED JUNE 2010
TYPICAL CHARACTERISTICS
INPUT CLOCK AND OUTPUT CLOCK PHASE NOISES
vs
FREQUENCY FROM THE CARRIER (TA = 25°C and VCC = 2.5V)
Input clock jitter is 32 fs from 10 kHz to 20 MHz and additive RMS jitter is 152 fs
Figure 3. 100 MHz Input and Output Phase Noise Plot
Differential Output Voltage
vs
Frequency
VOD − Differential Output Voltage − mV
350
TA = 25oC
340
2.625V
330
320
2.5V
310
300
2.375V
290
280
270
260
250
0
100
200
300
400
500
600
700
800
Frequency − MHz
Figure 4.
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SCAS904A – MAY 2010 – REVISED JUNE 2010
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TEST CONFIGURATIONS
Oscilloscope
100 W
LVDS
Figure 5. LVDS Output DC Configuration During Device Test
Phase Noise
Analyzer
LVDS
50 W
Figure 6. LVDS Output AC Configuration During Device Test
Figure 7. DC Coupled LVCMOS Input During Device Test
VOH
OUTNx
VOD
OUTPx
VOL
80%
VOUT,DIFF,PP (= 2 x VOD)
20%
0V
tr
tf
Figure 8. Output Voltage and Rise/Fall Time
8
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SCAS904A – MAY 2010 – REVISED JUNE 2010
INNx
INPx
tPLH0
tPHL0
tPLH1
tPHL1
OUTN0
OUTP0
OUTN1
OUTP1
tPLH2
tPHL2
OUTN2
OUTP2
OUTN3
tPLH3
tPHL3
OUTP3
A.
Output skew is calculated as the greater of the following: As the difference between the fastest and the slowest tPLHn
or the difference between the fastest and the slowest tPHLn (n = 0, 1, 2, 3).
B.
Part-to-part skew is calculated as the greater of the following: As the difference between the fastest and the slowest
tPLHn or the difference between the fastest and the slowest tPHLn across multiple devices (n = 0, 1, 2, 3).
C.
Both inputs (IN0 and IN1) are phase aligned.
Figure 9. Output Skew and Part-to-Part Skew
Vring
OUTNx
VOD
0V Differential
OUTPx
Figure 10. Output Overshoot and Undershoot
VOS
GND
Figure 11. Output AC Common Mode
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SCAS904A – MAY 2010 – REVISED JUNE 2010
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APPLICATION INFORMATION
THERMAL MANAGEMENT
For reliability and performance reasons, the die temperature should be limited to a maximum of 125°C.
The device package has an exposed pad that provides the primary heat removal path to the printed circuit board
(PCB). To maximize the heat dissipation from the package, a thermal landing pattern including multiple vias to a
ground plane must be incorporated into the PCB within the footprint of the package. The Thermal Pad must be
soldered down to ensure adequate heat conduction to of the package. Figure 12 shows a recommended land
and via pattern.
Figure 12. Recommended PCB Layout
POWER-SUPPLY FILTERING
High-performance clock buffers are sensitive to noise on the power supply, which can dramatically increase the
additive jitter of the buffer. Thus, it is essential to reduce noise from the system power supply, especially when
jitter/phase noise is critical to applications.
Filter capacitors are used to eliminate the low-frequency noise from the power supply, where the bypass
capacitors provide the very low impedance path for high-frequency noise and guard the power-supply system
against the induced fluctuations. These bypass capacitors also provide instantaneous current surges as required
by the device and should have low equivalent series resistance (ESR). To properly use the bypass capacitors,
they must be placed very close to the power-supply pins and laid out with short loops to minimize inductance. It
is recommended to add as many high-frequency (for example, 0.1 mF) bypass capacitors as there are supply
pins in the package. It is recommended, but not required, to insert a ferrite bead between the board power supply
and the chip power supply that isolates the high-frequency switching noises generated by the clock driver; these
beads prevent the switching noise from leaking into the board supply. Choose an appropriate ferrite bead with
very low dc resistance because it is imperative to provide adequate isolation between the board supply and the
chip supply, as well as to maintain a voltage at the supply pins that is greater than the minimum voltage required
for proper operation.
Board
Supply
Chip
Supply
Ferrite Bead
1 µF
10 µF
0.1 µF
Figure 13. Power-Supply Decoupling
10
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SCAS904A – MAY 2010 – REVISED JUNE 2010
LVDS OUTPUT TERMINATION
The proper LVDS termination for signal integrity over two 50 Ω lines is 100 Ω between the outputs on the
receiver end. Either dc-coupled termination or ac-coupled termination can be used for LVDS outputs. It is
recommended to place termination resister close to the receiver. If the receiver is internally biased to a voltage
different than the output common mode voltage of the CDCLVD2102, ac-coupling should be used. If the LVDS
receiver has internal 100 ohm termination, external termination must be omitted.
Unused outputs can be left open without connecting any trace to the output pins.
Z = 50 W
100 W
CDCLVD2102
LVDS
Z = 50 W
Figure 14. Output DC Termination
100 nF
Z = 50 W
100 W
CDCLVD2102
LVDS
Z = 50 W
100 nF
Figure 15. Output AC Termination With Receiver Internally Biased
INPUT TERMINATION
The CDCLVD2102 inputs can be interfaced with LVDS, LVPECL, or LVCMOS drivers.
LVDS Driver can be connected to CDCLVD2102 inputs with dc or ac coupling as shown Figure 16 and
Figure 17, respectively.
Z = 50 W
100 W
LVDS
CDCLVD2102
Z = 50 W
Figure 16. LVDS Clock Driver Connected to CDCLVD2102 Input (DC Coupled)
100 nF
Z = 50 W
LVDS
CDCLVD2102
Z = 50 W
100 nF
50 W
50 W
VAC_REF
Figure 17. LVDS Clock Driver Connected to CDCLVD2102 Input (AC Coupled)
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Figure 18 shows how to connect LVPECL inputs to the CDCLVD2102. The series resistors are required to
reduce the LVPECL signal swing if the signal swing is >1.6 VPP.
75 W
100 nF
Z = 50 W
CDCLVD2102
LVPECL
Z = 50 W
100 nF
75 W
150 W
150 W
50 W
50 W
VAC_REF
Figure 18. LVPECL Clock Driver Connected to CDCLVD2102 Input
Figure 19 illustrates how to couple a 2.5 V LVCMOS clock input to the CDCLVD2102 directly. The series
resistance (RS) should be placed close to the LVCMOS driver if needed. 3.3 V LVCMOS clock input swing needs
to be limited to VIH ≤ VCC.
RS
LVCMOS
(2.5V)
Z = 50 W
CDCLVD2102
V
V
Vth = IH + IL
2
Figure 19. 2.5V LVCMOS Clock Driver Connected to CDCLVD2102 Input
If one of the buffers is used, then the other unused buffer should be disabled through the EN pin, and the unused
input pins should be grounded by 1kΩ resistors.
12
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SCAS904A – MAY 2010 – REVISED JUNE 2010
REVISION HISTORY
Changes from Original (May 2010) to Revision A
Page
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Changed Features bullet From: ESD Protection Exceeds 2kV HBM, 500V CDM To: ESD Protection Exceeds 3 kV
HBM, 1 kV CDM ................................................................................................................................................................... 1
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Electrostatic discharge was