LM1894MTBD

LM1894 www.ti.com SNAS551C – DECEMBER 1994 – REVISED APRIL 2013 LM1894 Dynamic Noise Reduction System DNR Check for Samples: LM1894 FEATURES DESCRIPTION • The LM1894 is a stereo noise reduction circuit for use with audio playback systems. The DNR system is non-complementary, meaning it does not require encoded source material. The system is compatible with virtually all prerecorded tapes and FM broadcasts. Psychoacoustic masking, and an adaptive bandwidth scheme allow the DNR to achieve 10 dB of noise reduction. DNR can save circuit board space and cost because of the few additional components required. 1 2 • • • • • Non-Complementary Noise Reduction, “Single Ended” Low Cost External Components, No Critical Matching Compatible with All Prerecorded Tapes and FM 10 dB Effective Tape Noise Reduction CCIR/ARM Weighted Wide Supply Range, 4.5V to 18V 1 Vrms Input Overload APPLICATIONS • • • • • Automotive Radio/Tape Players Compact Portable Tape Players Quality HI-FI Tape Systems VCR Playback Noise Reduction Video Disc Playback Noise Reduction 1 2 Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet. All trademarks are the property of their respective owners. PRODUCTION DATA information is current as of publication date. Products conform to specifications per the terms of the Texas Instruments standard warranty. Production processing does not necessarily include testing of all parameters. Copyright © 1994–2013, Texas Instruments Incorporated LM1894 SNAS551C – DECEMBER 1994 – REVISED APRIL 2013 www.ti.com Typical Application *R1 + R2 = 1 kΩ total. See Application Hints. Figure 1. Component Hook-Up for Stereo DNR System 14-Pin SOIC or PDIP or TSSOP See D or NFF0014A or PW Package These devices have limited built-in ESD protection. The leads should be shorted together or the device placed in conductive foam during storage or handling to prevent electrostatic damage to the MOS gates. Absolute Maximum Ratings (1) (2) Supply Voltage 20V Input Voltage Range, Vpk VS/2 Operating Temperature (3) 0°C to +70°C −65°C to +150°C Storage Temperature PDIP Package Soldering Information (1) (2) (3) 2 SOIC Package Soldering (10 seconds) 260°C Vapor Phase (60 seconds) 215°C Infrared (15 seconds) 220°C “Absolute Maximum Ratings” indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for which the device is functional, but do not ensure specific performance limits. If Military/Aerospace specified devices are required, please contact the Texas Instruments Sales Office/Distributors for availability and specifications. For operation in ambient temperature above 25°C, the device must be derated based on a 150°C maximum junction temperature and a thermal resistance of: (a) 80°C/W junction to ambient for the PDIP package, (b) 105°C/W junction to ambient for the SOIC package, and (c) 150°C/W junction to ambient for the TSSOP package. Submit Documentation Feedback Copyright © 1994–2013, Texas Instruments Incorporated Product Folder Links: LM1894 LM1894 www.ti.com SNAS551C – DECEMBER 1994 – REVISED APRIL 2013 Electrical Characteristics VS = 8V, TA = 25°C, VIN = 300 mV at 1 kHz, circuit shown in Figure 1 unless otherwise specified Parameter Conditions Min Operating Supply Range Supply Current 4.5 VS = 8V Typ Max Units 8 18 V 17 30 mA V/V MAIN SIGNAL PATH DC Ground Pin 9 (1) −0.9 −1 −1.1 3.7 4.0 4.3 V Channel Balance DC Ground Pin 9 −1.0 1.0 dB Minimum Balance AC Ground Pin 9 with 0.1 μFCapacitor (1) 675 1400 Hz Maximum Bandwidth DC Ground Pin 9 (1) 27 34 46 kHz Effective Noise Reduction CCIR/ARM Weighted (2) −10 −14 dB Total Harmonic Distortion DC Ground Pin 9 0.05 0.1 % Input Headroom Maximum VIN for 3% THD 1.0 Vrms VS − 1.5 Vp-p AC Ground Pin 9 79 dB DC Ground Pin 9 77 dB Voltage Gain DC Output Voltage 965 AC Ground Pin 9 Output Headroom Maximum VOUT for 3% THD DC Ground Pin 9 Signal to Noise BW = 20 Hz–20 kHz, re 300 mV CCIR/ARM Weighted re 300 mV (3) AC Ground Pin 9 82 88 dB DC Ground Pin 9 70 76 dB AC Ground Pin 9 77 dB DC Ground Pin 9 64 dB CCIR Peak, re 300 mV (4) Input Impedance Pin 2 and Pin 13 14 20 Channel Separation DC Ground Pin 9 −50 −70 dB Power Supply Rejection C14 = 100 μF, −40 −56 dB VRIPPLE = 500 mVrms, 26 kΩ f = 1 kHz Output DC Shift Reference DVM to Pin 14 and Measuree Output DC Shift from Minimum to Maximum Band-width (1) (2) (3) (4) (5) 4.0 20 mV (5) To force the DNR system into maximum bandwidth, DC ground the input to the peak detector, pin 9. A negative temperature coefficient of −0.5%/°C on the bandwidth, reduces the maximum bandwidth at increased ambient temperature or higher package dissipation. AC ground pin 9 or pin 6 to select minimum bandwidth. To change minimum and maximum bandwidth, see Application Hints. The maximum noise reduction CCIR/ARM weighted is about 14 dB. This is accomplished by changing the bandwidth from maximum to minimum. In actual operation, minimum bandwidth is not selected, a nominal minimum bandwidth of about 2 kHz gives −10 dB of noise reduction. See Application Hints. The CCIR/ARM weighted noise is measured with a 40 dB gain amplifier between the DNR system and the CCIR weighting filter; it is then input referred. Measured using the Rhode-Schwartz psophometer. Pin 10 is DC forced half way between the maximum bandwidth DC level and minimum bandwidth DC level. An AC 1 kHz signal is then applied to pin 10. Its peak-to-peak amplitude is VDC (max BW) − VDC (min BW). Submit Documentation Feedback Copyright © 1994–2013, Texas Instruments Incorporated Product Folder Links: LM1894 3 LM1894 SNAS551C – DECEMBER 1994 – REVISED APRIL 2013 www.ti.com Electrical Characteristics (continued) VS = 8V, TA = 25°C, VIN = 300 mV at 1 kHz, circuit shown in Figure 1 unless otherwise specified Parameter Conditions Min Typ Max Units V/V CONTROL SIGNAL PATH Summing Amplifier Voltage Gain Both Channels Driven 0.9 1 1.1 Gain Amplifier Input Impedance Pin 6 24 30 39 kΩ Pin 6 to Pin 8 21.5 24 26.5 V/V Peak Detector Input Impedance Pin 9 560 700 840 Ω Voltage Gain Pin 9 to Pin 10 30 33 36 V/V Attack Time Measured to 90% of Final Value with 10 kHz Tone Burst 300 500 700 μs Decay Time Measured to 90% of Final Value with 10 kHz Tone Burst 45 75 ms DC Voltage Range Minimum Bandwidth to Maximum Bandwidth 1.1 3.8 V Voltage Gain 4 Submit Documentation Feedback 60 Copyright © 1994–2013, Texas Instruments Incorporated Product Folder Links: LM1894 LM1894 www.ti.com SNAS551C – DECEMBER 1994 – REVISED APRIL 2013 Typical Performance Characteristics Supply Current vs Supply Voltage Channel Separation (Referred to the Output) vs Frequency Figure 2. Figure 3. Power Supply Rejection Ratio (Referred to the Output) vs Frequency THD vs Frequency Figure 4. Figure 5. −3 dB Bandwidth vs Frequency and Control Signal Gain of Control Path vs Frequency (with 10 kHz FM Pilot Filter) Figure 6. Figure 7. Submit Documentation Feedback Copyright © 1994–2013, Texas Instruments Incorporated Product Folder Links: LM1894 5 LM1894 SNAS551C – DECEMBER 1994 – REVISED APRIL 2013 www.ti.com Typical Performance Characteristics (continued) Main Signal Path Bandwidth vs Voltage Control Peak Detector Response Figure 8. Figure 9. Output Response Figure 10. 6 Submit Documentation Feedback Copyright © 1994–2013, Texas Instruments Incorporated Product Folder Links: LM1894 LM1894 www.ti.com SNAS551C – DECEMBER 1994 – REVISED APRIL 2013 External Component Guide (Figure 1) Component Value Purpose C1 0.1 μF–100 μF May be part of power supply, or may be added to suppress power supply oscillation. C2, C13 1 μF Blocks DC, pin 2 and pin 13 are at DC potential of VS/2. C2, C13 form a low frequency pole with 20k RIN. C14 25 μF–100 μF Improves power supply rejection. C3, C12 0.0033 μF Forms integrator with internal gm block and op amp. Sets bandwidth conversion gain of 33 Hz/μA of gm current. C4, C11 1 μF Output coupling capacitor. Output is at DC potential of VS/2. C5 0.1 μF Works with R1 and R2 to attenuate low frequency transients which could disturb control path operation. C6 0.001 μF Works with input resistance of pin 6 to form part of control path frequency weighting. C8 0.1 μF Combined with L8 and CL forms 19 kHz filter for FM pilot. This is only required in FM applications (1). L8, CL 4.7 mH, 0.015 μF Forms 19 kHz filter for FM pilot. L8 is Toko coil CAN-1A185HM (1) (2). C9 0.047 μF Works with input resistance of pin 9 to form part of control path frequency weighting. C10 1 μF Set attack and decay time of peak detector. R1, R2 1 kΩ Sensitivity resistors set the noise threshold. Reducing attenuation causes larger signals to be peak detected and larger bandwidth in main signal path. Total value of R1 + R2 should equal 1 kΩ. R8 100Ω Forms RC roll-off with C8. This is only required in FM applications. (1) When FM applications are not required, pin 8 and pin 9 hook-up as follows: (2) Toko America Inc., 1250 Feehanville Drive, Mt. Prospect IL 60056 Circuit Operation The LM1894 has two signal paths, a main signal path and a bandwidth control path. The main path is an audio low pass filter comprised of a gm block with a variable current, and an op amp configured as an integrator. As seen in Figure 11, DC feedback constrains the low frequency gain to AV = −1. Above the cutoff frequency of the filter, the output decreases at −6 dB/oct due to the action of the 0.0033 μF capacitor. The purpose of the control paths is to generate a bandwidth control signal which replicates the ear's sensitivity to noise in the presence of a tone. A single control path is used for both channels to keep the stereo image from wandering. This is done by adding the right and left channels together in the summing amplifier of Figure 11. The R1, R2 resistor divider adjusts the incoming noise level to open slightly the bandwidth of the low pass filter. Control path gain is about 60 dB and is set by the gain amplifier and peak detector gain. This large gain is needed to ensure the low pass filter bandwidth can be opened by very low noise floors. The capacitors between Submit Documentation Feedback Copyright © 1994–2013, Texas Instruments Incorporated Product Folder Links: LM1894 7 LM1894 SNAS551C – DECEMBER 1994 – REVISED APRIL 2013 www.ti.com the summing amplifier output and the peak detector input determine the frequency weighting as shown in the Typical Performance Characteristics. The 1 μF capacitor at pin 10, in conjunction with internal resistors, sets the attack and decay times. The voltage is converted into a proportional current which is fed into the gm blocks. The bandwidth sensitivity to gm current is 33 Hz/μA. In FM stereo applications at 19 kHz pilot filter is inserted between pin 8 and pin 9 as shown in Figure 1. Figure 12 is an interesting curve and deserves some discussion. Although the output of the DNR system is a linear function of input signal, the −3 dB bandwidth is not. This is due to the non-linear nature of the control path. The DNR system has a uniform frequency response, but looking at the −3 dB bandwidth on a steady state basis with a single frequency input can be misleading. It must be remembered that a single input frequency can only give a single −3 dB bandwidth and the roll-off from this point must be a smooth −6 dB/oct. A more accurate evaluation of the frequency response can be seen in Figure 13. In this case the main signal path is frequency swept, while the control path has a constant frequency applied. It can be seen that different control path frequencies each give a distinctive gain roll-off. PSYCHOACOUSTIC BASICS The dynamic noise reduction system is a low pass filter that has a variable bandwidth of 1 kHz to 30 kHz, dependent on music spectrum. The DNR system operates on three principles of psychoacoustics. 1. White noise can mask pure tones. The total noise energy required to mask a pure tone must equal the energy of the tone itself. Within certain limits, the wider the band of masking noise about the tone, the lower the noise amplitude need be. As long as the total energy of the noise is equal to or greater than the energy of the tone, the tone will be inaudible. This principle may be turned around; when music is present, it is capable of masking noise in the same bandwidth. 2. The ear cannot detect distortion for less than 1 ms. On a transient basis, if distortion occurs in less than 1 ms, the ear acts as an integrator and is unable to detect it. Because of this, signals of sufficient energy to mask noise open bandwidth to 90% of the maximum value in less than 1 ms. Reducing the bandwidth to within 10% of its minimum value is done in about 60 ms: long enough to allow the ambience of the music to pass through, but not so long as to allow the noise floor to become audible. 3. Reducing the audio bandwidth reduces the audibility of noise. Audibility of noise is dependent on noise spectrum, or how the noise energy is distributed with frequency. Depending on the tape and the recorder equalization, tape noise spectrum may be slightly rolled off with frequency on a per octave basis. The ear sensitivity on the other hand greatly increases between 2 kHz and 10 kHz. Noise in this region is extremely audible. The DNR system low pass filters this noise. Low frequency music will not appreciably open the DNR bandwidth, thus 2 kHz to 20 kHz noise is not heard. 8 Submit Documentation Feedback Copyright © 1994–2013, Texas Instruments Incorporated Product Folder Links: LM1894 LM1894 www.ti.com SNAS551C – DECEMBER 1994 – REVISED APRIL 2013 Block Diagram Figure 11. Figure 12. Output vs Frequency Figure 13. −3 dB Bandwidth vs Frequency and Control Signal Submit Documentation Feedback Copyright © 1994–2013, Texas Instruments Incorporated Product Folder Links: LM1894 9 LM1894 SNAS551C – DECEMBER 1994 – REVISED APRIL 2013 www.ti.com APPLICATION HINTS The DNR system should always be placed before tone and volume controls as shown in Figure 1. This is because any adjustment of these controls would alter the noise floor seen by the DNR control path. The sensitivity resistors R1 and R2 may need to be switched with the input selector, depending on the noise floors of different sources, i.e., tape, FM, phono. To determine the value of R1 and R2 in a tape system for instance; apply tape noise (no program material) and adjust the ratio of R1 and R2 to open slightly the bandwidth of the main signal path. This can easily be done by viewing the capacitor voltage of pin 10 with an oscilloscope, or by using the circuit of Figure 14. This circuit gives an LED display of the voltage on the peak detector capacitor. Adjust the values of R1 and R2 (their sum is always 1 kΩ) to light the LEDs of pin 1 and pin 18. The LED bar graph does not indicate signal level, but rather instantaneous bandwidth of the two filters; it should not be used as a signal-level indicator. For greater flexibility in setting the bandwidth sensitivity, R1 and R2 could be replaced by a 1 kΩ potentiometer. To change the minimum and maximum value of bandwidth, the integrating capacitors, C3 and C12, can be scaled up or down. Since the bandwidth is inversely proportional to the capacitance, changing this 0.0039 μF capacitor to 0.0033 μF will change the typical bandwidth from 965 Hz–34 kHz to 1.1 kHz–40 kHz. With C3 and C12 set at 0.0033 μF, the maximum bandwidth is typically 34 kHz. A double pole double throw switch can be used to completely bypass DNR. The capacitor on pin 10 in conjunction with internal resistors sets the attack and decay times. The attack time can be altered by changing the size of C10. Decay times can be decreased by paralleling a resistor with C10, and increased by increasing the value of C10. When measuring the amount of noise reduction of the DNR system, the frequency response of the cassette should be flat to 10 kHz. The CCIR weighting network has substantial gain to 8 kHz and any additional roll-off in the cassette player will reduce the benefits of DNR noise reduction. A typical signal-to-noise measurement circuit is shown in Figure 15. The DNR system should be switched from maximum bandwidth to nominal bandwidth with tape noise as a signal source. The reduction in measured noise is the signal-to-noise ratio improvement. Figure 14. Bar Graph Display of Peak Detector Voltage 10 Submit Documentation Feedback Copyright © 1994–2013, Texas Instruments Incorporated Product Folder Links: LM1894 LM1894 www.ti.com SNAS551C – DECEMBER 1994 – REVISED APRIL 2013 Figure 15. Technique for Measuring S/N Improvement of the DNR System FOR FURTHER READING Tape Noise Levels 1. “A Wide Range Dynamic Noise Reduction System”, Blackmer, “dB” Magazine,August-September 1972, Volume 6, #8. 2. “Dolby B-Type Noise Reduction System”, Berkowitz and Gundry, Sert Journal,May-June 1974, Volume 8. 3. “Cassette vs Elcaset vs Open Reel”, Toole, Audioscene Canada, April 1978. 4. “CCIR/ARM: A Practical Noise Measurement Method”, Dolby, Robinson, Gundry, JAES,1978. Noise Masking 1. “Masking and Discrimination”, Bos and De Boer, JAES, Volume 39, #4, 1966. 2. “The Masking of Pure Tones and Speech by White Noise”, Hawkins and Stevens, JAES, Volume 22, #1, 1950. 3. “Sound System Engineering”, Davis Howard W. Sams and Co. 4. “High Quality Sound Reproduction”, Moir, Chapman Hall, 1960. 5. “Speech and Hearing in Communication”, Fletcher, Van Nostrand, 1953. Submit Documentation Feedback Copyright © 1994–2013, Texas Instruments Incorporated Product Folder Links: LM1894 11 LM1894 SNAS551C – DECEMBER 1994 – REVISED APRIL 2013 www.ti.com Printed Circuit Layout Figure 16. DNR Component Diagram 12 Submit Documentation Feedback Copyright © 1994–2013, Texas Instruments Incorporated Product Folder Links: LM1894 LM1894 www.ti.com SNAS551C – DECEMBER 1994 – REVISED APRIL 2013 REVISION HISTORY Changes from Revision B (April 2013) to Revision C • Page Changed layout of National Data Sheet to TI format .......................................................................................................... 11 Submit Documentation Feedback Copyright © 1994–2013, Texas Instruments Incorporated Product Folder Links: LM1894 13 PACKAGE OPTION ADDENDUM www.ti.com 10-Dec-2020 PACKAGING INFORMATION Orderable Device Status (1) Package Type Package Pins Package Drawing Qty Eco Plan (2) Lead finish/ Ball material MSL Peak Temp Op Temp (°C) Device Marking (3) (4/5) (6) LM1894MX/NOPB ACTIVE SOIC D 14 2500 RoHS & Green SN Level-1-260C-UNLIM 0 to 70 LM1894M (1) The marketing status values are defined as follows: ACTIVE: Product device recommended for new designs. LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect. NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design. PREVIEW: Device has been announced but is not in production. Samples may or may not be available. OBSOLETE: TI has discontinued the production of the device. (2) RoHS: TI defines "RoHS" to mean semiconductor products that are compliant with the current EU RoHS requirements for all 10 RoHS substances, including the requirement that RoHS substance do not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, "RoHS" products are suitable for use in specified lead-free processes. TI may reference these types of products as "Pb-Free". RoHS Exempt: TI defines "RoHS Exempt" to mean products that contain lead but are compliant with EU RoHS pursuant to a specific EU RoHS exemption. Green: TI defines "Green" to mean the content of Chlorine (Cl) and Bromine (Br) based flame retardants meet JS709B low halogen requirements of