User's Guide
SNVA476A – March 2011 – Revised May 2013
AN-2130 LM21215 Evaluation Board
1
Introduction
This evaluation board provides a solution to examine the high efficiency LM21215 buck switching
regulator. The LM21215 is capable of driving up to 15A of continuous load current with excellent output
voltage accuracy due to its ±1% internal reference. The LM21215 is capable of down converting from an
input voltage between 2.95V and 5.5V at a fixed switching frequency of 500 kHz. This device also features
an adjustable current limit that allows the user to set the internal current limit protection value. Other fault
protection features include output power good and output over-voltage protection. The dual function softstart/tracking pin can be used to control the startup response of the LM21215, and the precision enable
pin can be used to easily sequence the LM21215 in applications with sequencing requirements.
The LM21215 evaluation board has been optimized to work from 2.95V to 5.5V, achieving a balance
between overall solution size and regulator efficiency. The evaluation board measures just over 2” × 2” on
a four layer PCB, and exhibits a junction-to-ambient thermal impedance (θJA) of 24°C/W with no air flow.
The power stage and compensation components of the LM21215 evaluation board have been optimized
for an input voltage of 5V, but for testing purposes, the input can be varied across the entire operating
range. The output voltage of the evaluation board is nominally 1.2V, but this voltage can be easily
changed to any voltage between 0.6V and VIN by modifying the feedback resistor network.
2
Evaluation Board Schematic
eTSSOP-20
VIN
SENSE+
SW
11-16
VOUT
RAC
49.9:
5,6,7
PVIN
VIN
R1
1:
4
GND
VIN
SENSE-
REN1
open
ENABLE
AC INJ
AVIN
RC2
10 k:
FB
EN
COMP
2
CSS
C4
100 PF
VOUT
SENSE-
VOUT = 1.2V, up to 15A
19
18
CC1
RC1
1800 pF 9.31 k:
RFB2
10 k:
SS/
TRK
Vin
0.033 PF
1
C3
C9
C5
0.1 PF
165:
LM21215
3
RILIM
0:
820 pF
RFB1
REN2
open
SS_TRK
GND
CC3
C1
1 PF
C8 C7 C6
100 PF
VOUT
SENSE+
SWITCH
L1
0.56 PH
VIN = 2.95V to 5.5V
CC2
68 pF
RPG
ILIM
PGOOD
17
10 k:
PGOOD
PGND AGND
8,9,10
20
Figure 1. Evaluation Board Schematic
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1
Powering and Loading Considerations
3
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Powering and Loading Considerations
Read this entire section prior to attempting to power the evaluation board.
3.1
Quick Setup Procedure
Step 1: Set the input source current limit to 10A. Turn off the input source. Connect the positive output of
the input source to VIN and the negative output to the corresponding GND.
Step 2: Connect the load (with 15A capability) to VOUT for the positive connection and GND for the
negative connection.
Step 3: The ENABLE pin should be left open for normal operation.
Step 4: Set the input source voltage to 5V. The load voltage should be in regulation with a nominal 1.2V
output.
Step 5: Slowly increase the load while monitoring the load voltage at VOUT. It should remain in regulation
with a nominal 1.2V output as the load is increased up to 15A.
Step 6: Slowly sweep the input source voltage from 2.95V to 5.5V. The load voltage should remain in
regulation with a nominal 1.2V output. If desired, the output of the device can be disabled by connecting
the ENABLE pin to GND.
3.2
Powering Up
It is suggested that the load power be kept low during the first power up. Once the device is powered up,
immediately check for 1.2V at the output.
A quick efficiency check is the best way to confirm that everything is operating properly. If something is
amiss you can be reasonably sure that it will affect the efficiency adversely. Few parameters can be
incorrect in a switching power supply without creating losses and potentially damaging heat.
Some voltage supplies can exhibit severe voltage overshoot during high current transients. If a supply
overshoots above 6.0V, damage to the LM21215 can occur. For these supplies, a large capacitor across
the terminals of the supply (1000µF) can alleviate this problem.
3.3
Over Current Protection
The LM21215 features a resistor-programmable current limit that allows the user to set the current limit to
any desired value between 4A and 20A by changing the resistor RILIM. This evaluation board allows the
maximum possible current limit for the LM21215 by populating RILIM with a 0Ω resistor. If the user desires
a lower current limit, the current limit should be set above the peak inductor current under maximum load
and ripple conditions to avoid a current limit event in normal operation. See Section 5.8 for details on how
to determine the RILIM value.
4
Connection Descriptions
Table 1. Connection Descriptions
Terminal Silkscreen
2
Description
VIN
This terminal is the input voltage to the device. The evaluation board will operate over the input voltage
range of 2.95V to 5.5V.
GND
These terminals are the ground connections to the device. The input power ground should be connected
next to the input VIN connection, and the output power ground next to the VOUT connection.
VOUT
This terminal connects to the output voltage of the power supply and should be connected to the load.
ENABLE
This terminal connects to the enable pin of the device. This terminal can be left floating or driven
externally. If left floating, a 2µA current source will pull the pin high, thereby enabling the device. If driven
externally, a voltage typically less than 1.2V will disable the device.
SS/TRK
This terminal provides access to the SS/TRK pin of the device. Connections to this terminal are not
needed for most applications. The feedback pin of the device will track the voltage on the SS/TRK pin if
it is driven with an external voltage source that is below the 0.6V reference.
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Table 1. Connection Descriptions (continued)
Terminal Silkscreen
This terminal connects to the power good output of the device. This pin is pulled up through a 10 kΩ
pull-up resistor to VIN.
AC INJ
This terminal block allows the user to insert an AC injection signal across a 49.9Ω resistor for open-loop
gain bode measurements. A jumper shorts out this resistor when it is not needed.
SWITCH
VIN_SENSE+,
VIN_SENSEVOUT_SENSE+,
VOUT_SENSE-
5
Description
PGOOD
This terminal allows easy probing of the switch node. Do not apply any external voltage source to this
pin.
These terminals allow a sense connection on the board for accurate VIN and VOUT measurements,
respectively.
Component Selection
This section provides a walk-through of the design process of the LM21215 evaluation board. Unless
otherwise indicated, all equations assume units of amps (A) for current, farads (F) for capacitance, henries
(H) for inductance, and volts (V) for voltages.
5.1
Input Capacitors: C1, C2, C3
The required RMS current rating of the input capacitor for a buck regulator can be estimated by the
following equation:
ICIN(RMS) = IOUT D(1 - D)
(1)
The variable D refers to the duty cycle, and can be approximated by:
D=
VOUT
VIN
(2)
From this equation, it follows that the maximum ICIN(RMS) requirement will occur at a full 15A load current
with the system operating at 50% duty cycle. Under this condition, the maximum ICIN(RMS) is given by:
ICIN(RMS) = 15A
0.5 x 0.5 = 7.5A
(3)
Ceramic capacitors feature a very large IRMS rating in a small footprint, making a ceramic capacitor ideal
for this application.
The input capacitors also keep the input stable during load transient conditions. If the input capacitance is
too low, the input can drop below the UVLO threshold and cause the device to disable the output. This
may result in repetitive dropout and re-enable oscillation, or "motorboating". To give the user the ability to
operate with a low VIN voltage, three 100 µF ceramic capacitors were used on the input.
5.2
Inductor: L1
The value of the inductor was selected to allow the device to achieve a 5V to 1.2V conversion at 500kHz
to provide a peak to peak ripple current of 3.2A, which is about 21% of the maximum output current. To
have an optimized design, generally the peak to peak inductor ripple current should be kept to within 20%
to 40% of the rated output current for a given input voltage, output voltage and operating frequency. The
peak to peak inductor ripple current can be calculated by the equation:
'IP-P =
(VIN - VOUT) x D
L x fSW
(4)
Once an inductance value is calculated, an actual inductor needs to be selected based on a trade-off
between physical size, efficiency, and current carrying capability. For the LM21215 evaluation board, a
Vishay IHLP4040DZERR56M01 inductor offers a good balance between efficiency (1.8 mΩ DCR) and
size.
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Component Selection
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Output Capacitors: C3, C4, C5, C9
The value of the output capacitor in a buck regulator influences the voltage ripple that will be present on
the output voltage as well as the large signal output voltage response to a load transient. Given the peakto-peak inductor current ripple (ΔIP-P) the output voltage ripple can be approximated by the equation:
'VOUT = 'IP-P x RESR +
1
8 x fSW x COUT
(5)
The variable RESR above refers to the ESR of the output capacitor. As can be seen in Equation 5, the
ripple voltage on the output can be divided into two parts, one of which is attributed to the AC ripple
current flowing through the ESR of the output capacitor and another due to the AC ripple current actually
charging and discharging the output capacitor. The output capacitor also has an effect on the amount of
droop that is seen on the output voltage in response to a load transient event.
For the evaluation board, three 100µF ceramic capacitors were selected to provide good transient and DC
performance. Ceramic capacitors give the lowest RESR of any standard capacitor chemistries, resulting in
the lowest output ripple for the given ripple current. Ceramic capacitors (especially high capacitance, small
package multi-layer types, or MLCC) lose thier capacitance as the DC voltage is increased. For this
configuration, the actual capacitance value was approximated to be 50 µF per capacitor, or 150 µF total.
This is lower than measured capacitance values for 1.2V, but will allow the user to change the output
voltage up to 3.3V and maintain stability.
5.4
Soft-Start Capacitor: CSS
A soft-start capacitor can be used to control the startup time of the LM21215 voltage regulator. The startup
time of the regulator when using a soft-start capacitor can be estimated by the following equation:
tSS =
0.6V x Css
ISS
(6)
For the LM21215, ISS is nominally 5 µA. For the evaluation board, the soft-start time has been designed to
be roughly 10 ms, resulting in a CSS capacitor value of 33 nF.
5.5
Compensation Components: CC1, CC2, CC3, RC1, RC2
These components are used in conjunction with the error amplifier to create a type 3 voltage-mode
compensation network. The analysis of type 3 compensation is outside the scope of this document, but an
example of the step-by-step procedure to generate compensation component values is given. The
parameters needed for the compensation values are given in the following table.
Parameter
Value
VIN
5.0V
VOUT
1.2V
IOUT
15A
fCROSSOVER
100 kHz
L
0.56 µH
RDCR
1.8 mΩ
CO
150 µF
RESR
1.0 mΩ
ΔVRAMP
0.8V
fSW
500 kHz
where ΔVRAMP is the oscillator peak-to-peak ramp voltage (nominally 0.8 V), fCROSSOVER is the frequency at
which the open-loop gain is a magnitude of 1, RDCR is the effective DC resistance of the inductor, RESR is
the effective resistance of the output capacitor, and CO is the effective output capacitance at the
programmed output voltage. It is recommended that fCROSSOVER not exceed one-fifth of the switching
frequency. The output capacitance, CO, depends on capacitor chemistry and bias voltage. For Multi-Layer
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Ceramic Capacitors (MLCC), the total capacitance will degrade as the DC bias voltage is increased.
Measuring the actual capacitance value for the output capacitors at the output voltage is recommended to
accurately calculate the compensation network. Note that it is more conservative, from a stability
standpoint, to err on the side of a smaller output capacitance value in the compensation calculations
rather than a larger, as this will result in a lower bandwidth but increased phase margin.
First, the value of RFB1 should be chosen. A typical value is 10kΩ. From this, the value of RC1 can be
calculated to set the mid-band gain so that the desired crossover frequency is achieved.
RC1 =
=
fCROSSOVER
'VRAMP
fLC
VIN
RFB1
100 kHz 0.8 V
10 k:
17.4 kHz 5.0 V
= 9.2 k:
(7)
Next, the value of CC1 can be calculated by placing a zero at half of the LC double pole frequency.
1
CC1 =
SfLCRC1
= 1.99 nF
(8)
Now the value of CC2 can be calculated to place a pole at half of the switching frequency.
CC2 =
CC1
SfSWRC1 CC1 -1
= 71 pF
(9)
RC2 can then be calculated to set the second zero at the LC double pole frequency.
RFB1fLC
RC2 =
fESR - fLC
= 166:
(10)
Last, CC3 can be calculated to place a pole at the same frequency as the zero created by the output
capacitor ESR.
CC3 =
1
2SfESRRC2
= 898 pF
(11)
The standard values used for the above calculations are given in the Bill of Materials (Section 7).
5.6
Feedback Resistors: RFB1, RFB2, and RAC
The resistors labeled RFB1 and RFB2 create a voltage divider from VOUT to the feedback pin that is used to
set the output of the voltage regulator. Nominally, the output of the LM21215 evaluation board is set to
1.2V, giving resistor values of RFB1= RFB2 = 10kΩ. If a different output voltage is required, the value of RFB2
can be adjusted according to the equation:
RFB1 =
VOUT
0.6
- 1 x RFB2
(12)
RFB1 does not need to be changed from its value of 10kΩ. Resistor RAC has a value of 49.9Ω and is
provided as an injection point for loop stability measurements, as well as, a way to further tweak the
output voltage accuracy to account for resistor tolerance values differing from ideal calculated values. The
jumper is used to short out RAC when not needed.
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5.7
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Programmable UVLO: REN1 and REN2
The resistors labeled REN1 and REN2 create a voltage divider from VIN to the enable pin that can be used to
enable the device above a programmed VIN, effectively creating a programmable UVLO voltage above the
device's internal UVLO (nominally 2.7V). To allow evaluation of the device down to 2.95V, these
components are not installed. To change the turn-on threshold of the device a 10 kΩ resistor is
recommended for REN1 and the value of REN2 can be calculated using the equation:
REN1 =
VTO
1.35
- 1 x REN2
(13)
where VTO is the desired VIN voltage at which the device will enable.
5.8
Programmable Current Limit: RILIM
The resistor RILIM will set the internal current limit on the LM21215. A 0Ω resistor is used on this board,
allowing the maximum current capability of the device. If a user desires a lower current limit, it should be
programmed such that the peak inductor current (IL) does not trigger the current limit in normal operation.
This requires setting the resistor RILIM to the appropriate value to allow the maximum ripple current plus the
DC output current through the high-side FET during normal operation. The maximum ripple current can be
described as:
ÂILMAX =
ÂILMAX =
FOR D > 0.5
(VINMAX ± VOUTMIN) VOUTMIN
LMIN fSWMIN VINMAX
FOR D < 0.5
(VINMIN ± VOUTMAX) VOUTMAX
LMIN fSWMIN VINMIN
(14)
where VINMAX, VINMIN, VOUTMAX, VOUTMIN, LMIN and FSWMIN are the respective maximum and minimum conditions
of the system as defined by the component tolerance and device variation. From this, the maximum
allowable current through the high-side FET (IHSMAX) of device can be described as:
IHSMAX =
ÂILMAX
+ IDCMAX
2
(15)
where IOUTMAX is the maximum defined DC output current, up to 15 A. Once the IHSMAX value has been
determined, a nominal value of the RILIMresistor can be calculated as follows:
RILIM (kÖ) =
582.4
- 14.2
IHSMAX
(16)
where the RILIMvalue is the nominal resistance necessary for the given IHSMAX value. A conservative design
should also take into account the device variation over VIN and temperature, which can be seen in the
Electrical Characteristics table for the ICLR parameter and the typical performance characteristics in 15A
High Efficiency Point of Load Synchronous Buck Regulator (SNVS625). These variations can cause the
IHSMAX value to increase, depending on the range of the input voltage and junction temperature.
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Performance Characteristics
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6
Performance Characteristics
Figure 2 shows the conversion efficiency versus output current for a 5V input voltage for output voltages of
1.2V and 3.3V. The default output voltage is 1.2V.
100
VIN = 3.3V
VIN = 5.0V
98
EFFICIENCY (%)
96
94
92
90
88
86
84
82
80
0
3
6
9
12
OUTPUT CURRENT (A)
15
Figure 2. Conversion Efficiency Versus Output Current
A soft-start sequence occurs when applying power to the LM21215 evaluation board. Figure 3 shows the
output voltage during a typical start-up sequence.
VOUT (500 mV/Div)
VPGOOD (5V/Div)
VENABLE (5V/Div)
IOUT (10A/Div)
Figure 3. Startup Waveform (2 ms/DIV)
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Figure 4 shows the output voltage ripple. This measurement was taken with the scope probe tip placed on
the output capacitor C9 VOUT connection and the scope probe ground "barrel" wired to the GND
connection of C9. The scope bandwidth is set to 20 MHz.
VOUT (10 mV/Div)
Figure 4. Output Ripple Waveform (2 µs/DIV)
Figure 5 shows the typical SW pin voltage with the output current set to 10A.
VOUT (10 mV/Div)
VSW (2V/Div)
Figure 5. Primary Switch Node Waveform (400 ns/DIV)
8
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Figure 6 shows the VOUT deviation for a 3A to 12A output current transient condition.
VOUT (50 mV/Div)
IOUT (5A/Div)
Figure 6. VOUT Transient Response (50 µs/DIV)
Figure 7 shows the VOUT output response to an output current limit condition.
VOUT (500 mV/Div)
VSW (5V/Div)
IL (10A/Div)
Figure 7. Output Current Limit (10 µs/DIV)
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Figure 8 shows the open loop bode response generated by inserting a stimulus signal across RAC and
using a network analyzer to plot the gain and phase.
80
160
GAIN (dB)
PHASE MARGIN (°)
120
60
80
40
40
20
0
0
-20
100
-40
GAIN
PHASE MARGIN
1k
10k
100k
FREQUENCY (Hz)
-80
1M
Figure 8. Open Loop Bode Response
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Bill of Materials
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7
Bill of Materials
Table 2. Bill of Materials
Item
Description
Vendor
Part Number
Qty
AC INJ
Header, TH, 100mil, 2 × 1, Gold plated,
230 mil above insulator
Samtec Inc.
TSW-102-07-G-S
1
C1
CAP, CERM, 1 uF, 10V, +/-10%, X7R,
0603
MuRata
GRM188R71A105KA61D
1
C3, C4, C5, C6, C7,
C8
CAP, CERM, 100 uF, 6.3V, +/-20%, X5R,
1206
MuRata
GRM31CR60J107ME39L
6
C9
CAP, CERM, 0.1 uF, 50V, +/-10%, X7R,
0603
TDK
C1608X7R1H104K
1
CC1
CAP, CERM, 1800 pF, 50V, +/-5%,
C0G/NP0, 0603
MuRata
C1608C0G1H182J
1
CC2
CAP, CERM, 68 pF, 50V, +/-5%,
C0G/NP0, 0603
MuRata
GRM1885C1H680JA01D
1
CC3
CAP, CERM, 820 pF, 50V, +/-5%,
C0G/NP0, 0603
MuRata
GRM1885C1H821JA01D
1
CSS
CAP, CERM, 0.033 uF, 16V, +/-10%, X7R,
0603
MuRata
GRM188R71C333KA01D
1
GND_FI, GND_FO,
VIN_F, VOUT_F
Standard Banana Jack, Uninsulated, 15A
Johnson
Components
108-0740-001
4
L1
Inductor, Shielded Drum Core, Powdered
Iron, 560nH, 27.5A, 0.0018 ohm, SMD
Vishay-Dale
IHLP4040DZERR56M01
1
R1
RES, 1.0 ohm, 5%, 0.1W, 0603
Vishay-Dale
CRCW06031R00JNEA
1
RAC
RES, 49.9 ohm, 1%, 0.1W, 0603
Vishay-Dale
CRCW060349R9FKEA
1
RC1
RES, 9.31 kohm, 1%, 0.1W, 0603
Vishay-Dale
CRCW06039K31FKEA
1
RC2
RES, 165 ohm, 1%, 0.1W, 0603
Vishay-Dale
CRCW0603165RFKEA
1
RFB1, RFB2, RPG
RES, 10 kohm, 1%, 0.1W, 0603
Vishay-Dale
CRCW060310K0FKEA
3
RILIM
RES, 0 ohm, 1%, 0.1W, 0603
Vishay-Dale
CRCW06030000Z0EA
1
SH-J1
Shunt, 100mil, Gold plated, Black
Samtec Inc.
SNT-100-BK-G
1
U1
15A Buck DC/DC Converter
Texas
Instruments
LM21215
1
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PCB Layout
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PCB Layout
The PCB was manufactured with 2oz. copper outer layers, and 1oz. copper inner layers. Twenty 8 mil.
diameter vias placed underneath the device, along with additional vias placed throughout the ground plane
around the device, help improve the thermal dissipation of the board.
Figure 9. Top Layer (Copper planes outlined in grey)
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Figure 10. Mid Layer1
Figure 11. Mid Layer2
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PCB Layout
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Figure 12. Bottom Layer
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