LM25007EVAL

User's Guide SNVA152A – March 2006 – Revised April 2013 AN-1453 LM25007 Evaluation Board 1 Introduction The LM25007EVAL evaluation board provides the design engineer with a fully functional buck regulator, employing the constant on-time (COT) operating principle. This evaluation board provides a 5V output over an input range of 9V - 42V. The circuit delivers load currents to 450 mA, with current limit at ≊670 mA. The board is populated with all external components except C6 and C9. These components provide options for managing the output ripple as described later in this document. The board’s specification are: • Input Voltage: 9V to 42V • Output Voltage: 5V • Maximum load current: 450 mA • Minimum load current: 0 mA • Current Limit: ≊670 mA • Measured Efficiency: 92.6% (VIN = 9V, IOUT = 150 mA) • Nominal Switching Frequency: 306 kHz • Size: 1.6 in. x 1.0 in. x 0.5 in Figure 1. Evaluation Board - Top Side 2 Theory of Operation Figure 5 contains a simplified block diagram of the LM25007. When the circuit is in regulation, the buck switch is on each cycle for a time determined by R1 and the input voltage according to Equation 1: tON = 1.42 x 10-10 x R1 VIN (1) The nominal switching frequency is calculated from Equation 2: FS = VOUT 1.42 x 10-10 x R1 (2) All trademarks are the property of their respective owners. SNVA152A – March 2006 – Revised April 2013 Submit Documentation Feedback AN-1453 LM25007 Evaluation Board Copyright © 2006–2013, Texas Instruments Incorporated 1 Board Layout and Probing www.ti.com The on-time in this evaluation board ranges from ≊1800 ns at Vin = 9V, to ≊390 ns at Vin = 42V. The ontime varies inversely with VIN to maintain a nearly constant switching frequency, which is nominally 306 kHz in this evaluation board . At the end of each on-time the Minimum Off-Timer ensures the buck switch is off for at least 300 ns. In normal operation the off-time is much longer. During the off-time the output capacitor (C2) is discharged by the load current. When the output voltage falls sufficiently that the voltage at FB is below 2.5V, the regulation comparator initiates a new on-time period. For stable, fixed frequency operation, ≊25 mVp-p of ripple is required at FB to switch the regulation comparator. For a more detailed block diagram and a complete description of the various functional blocks, see the LM25007 42V, 0.5A Step-Down Switching Regulator Data Sheet (SNVS401). 3 Board Layout and Probing Figure 1 shows the placement of the circuit components. The following should be kept in mind when the board is powered: 1) When operating at high input voltage and high load current, forced air flow is recommended. 2) The LM25007 may be hot to the touch when operating at high input voltage and high load current. 3) Use CAUTION when probing the circuit at high input voltages to prevent injury, as well as possible damage to the circuit. 4) Ensure the wires connecting this board to the load are sized appropriately for the load current. Ensure there is not a significant drop in the wires between this evaluation board and the load. 4 Board Connection/Start-up The input connections are made to the J1 connector. The load is normally connected to the V1 and GND terminals of the J3 connector. Ensure the wires are adequately sized for the intended load current. Before start-up a voltmeter should be connected to the input terminals, and to the output terminals. The load current should be monitored with an ammeter or a current probe. It is recommended that the input voltage be increased gradually to 9V, at which time the output voltage should be 5V. If the output voltage is correct with 9V at VIN, then increase the input voltage as desired and proceed with evaluating the circuit. 5 Output Ripple Control The LM25007 requires a minimum of 25 mVp-p ripple at the FB pin, in phase with the switching waveform at the SW pin, for proper operation. In the simplest configuration that ripple is derived from the ripple at VOUT1, generated by the inductor’s ripple current flowing through R4. That ripple voltage is attenuated by the feedback resistors, requiring that the ripple amplitude at VOUT1 be higher than the minimum of 25 mVpp by the gain factor. Options for reducing the output ripple are discussed below, and the results are shown in the graph of Figure 8. 5.1 Minimum Output Ripple This evaluation board is supplied configured for minimum ripple at VOUT1 by setting R4 to zero ohms, and including components R6, C7 and C8. The output ripple that ranges from 2 mVp-p at VIN = 9V to 7 mVp-p at VIN = 42V, is determined primarily by the ESR of output capacitor (C2), and the inductor’s ripple current that ranges from 75 mAp-p to 144 mAp-p over the input voltage range. This performance applies only to continuous conduction mode as the ripple amplitude is higher in discontinuous conduction mode. The ripple voltage required by the FB pin is generated by R6, C7 and C8 since the SW pin switches from -1V to VIN, and the right end of C7 is a virtual ground. The values for R6 and C7 are chosen to generate a 3040 mVp-p triangle waveform at their junction. That triangle wave is then coupled to the FB pin through C8. The following procedure is used to calculate values for R6, C7 and C8: • Calculate the voltage VA: VA = VOUT - (VSW x (1 - (VOUT/VIN))) (3) where, VSW is the absolute value of the voltage at the SW pin during the off-time (typically 1V), and VIN is the minimum input voltage. For this circuit VA calculates to 4.55V. This is the DC voltage at the R6/C7 junction, and is used in Equation 4. 2 AN-1453 LM25007 Evaluation Board SNVA152A – March 2006 – Revised April 2013 Submit Documentation Feedback Copyright © 2006–2013, Texas Instruments Incorporated Output Ripple Control www.ti.com • Calculate the R6 x C7 product: R6 x C7 = (VIN ± VA) x tON 'V (4) where, tON is the maximum on-time (≊1800 ns), VIN is the minimum input voltage, and ΔV is the desired ripple amplitude at the R6/C7 junction, 30 mVp-p for this example. R6 x C7 = (9V ± 4.55V) x 1800 ns = 2.67 x 10-4 0.03V (5) R6 and C7 are then chosen from standard value components to satisfy the above product. For example, C7 can be 2200 pF requiring R6 to be 121 kΩ. C8 is chosen to be 0.01 µF, large compared to C7. This portion of the circuit, as supplied on this EVB, is shown in Figure 2. LM25007 BST 2 C5 0.01PF L1 100 PH C7 R6 SW 1 121k 5V VOUT1 2200 pF D1 R2 3k C8 0.01 PF FB R4 0 VOUT2 5 R3 3k C2 22 PF GND RTN 4 Figure 2. Minimum Ripple Using R6, C7, C8 5.2 Intermediate Ripple Level Configuration This configuration generates more ripple at VOUT1 than the above configuration, but uses one less capacitor. If some ripple can be tolerated in the application, this configuration is slightly more economical, and simpler. R4 and C6 are used instead of R6, C7, and C8, as shown in Figure 3. LM25007 BST 2 C5 0.01 PF L1 SW 100 PH 5V 1 VOUT1 D1 FB C6 1500 pF R2 3k 5 R3 3k 4 R4 0.34: C2 22 PF RTN VOUT2 GND Figure 3. Intermediate Ripple Level Configuration Using C6 and R4 SNVA152A – March 2006 – Revised April 2013 Submit Documentation Feedback AN-1453 LM25007 Evaluation Board Copyright © 2006–2013, Texas Instruments Incorporated 3 Current Limit www.ti.com R4 is chosen to generate ≥25 mV at VOUT1, knowing that the minimum ripple current in this circuit is 75 mAp-p at minimum VIN. C6 couples that ripple to the FB pin without the attenuation of the feedback resistors. C6's minimum value is calculated from: C6 = tON(max) (R2//R3) (6) where, tON(max) is the maximum on-time (at minimum VIN), and R2//R3 is the equivalent parallel value of the feedback resistors. For this evaluation board tON(max) is approximately 1800 ns, and R2//R3 = 1.5 kΩ, and C6 calculates to a minimum of 1200 pF. The resulting ripple at VOUT1 ranges from ≊25 mVp-p to 50 mVp-p over the input voltage range with the circuit in continuous conduction mode. The ripple amplitude is higher if the load current is low enough to force the circuit into discontinuous conduction mode. 5.3 Minimum Cost Configuration This configuration is the same as Section 5.2, but without C6. Since 25 mVp-p are required at the FB pin, R4 is chosen to generate 50 mvp-p at VOUT1, knowing that the minimum ripple current in this circuit is 75 mAp-p at minimum VIN. To allow for tolerances, 0.68Ω is used for R4. The resulting ripple at VOUT1 ranges from ≊50 mVp-p to ≊100 mVp-p over the input voltage range. If the application can accept this ripple level, this is the most economical solution. The circuit is shown in Figure 4. LM25007 BST 2 C5 0.01PF L1 SW 100 PH 5V 1 VOUT1 D1 R2 3k R4 0.68: R3 3k C2 22 PF FB 5 4 VOUT2 GND RTN Figure 4. Minimum Cost Configuration 5.4 Alternate Low Ripple Configuration A low ripple output can be obtained by connecting the load to VOUT2 in the circuits of Section 5.2 or Section 5.3. Since R4 degrades load regulation, this alternative may be viable for applications where the load current is relatively constant. If this method is used, ensure R4’s power rating is appropriate for the load current. 6 Current Limit The LM25007 contains an intelligent current limit off-timer. The current limit threshold is 725 mA, ±25%. If the current in the buck switch (the peak of the inductor’s current waveform) reaches the threshold the present on-time cycle is immediately terminated, and a non-resetable off-time is initiated. The length of the off-time is controlled by an external resistor (R5) and the voltage at the FB pin. If FB = 0V (output is shorted to ground) the off-time is the preset maximum of 17 µs. This off-time ensures safe short circuit operation to the maximum input voltage of 42V. In cases of less severe overload where the output voltage, and the voltage at FB, is above ground the current limit off-time is less than 17 µs. The shorter off-times reduces the amount of foldback, recovery time, and also reduces the startup time. 4 AN-1453 LM25007 Evaluation Board SNVA152A – March 2006 – Revised April 2013 Submit Documentation Feedback Copyright © 2006–2013, Texas Instruments Incorporated Minimum Load Current www.ti.com The current limit off-time is calculated from Equation 7: 10 tOFF = 0.59 + -5 VFB -6 7.22 x 10 x R5 (7) The current limit off-time ranges from 4.3 µs to 17 µs as VFB varies from 2.5V to 0V, with R5 = 200 kΩ. The guideline for selecting R5’s value is that the current limit off-time (at VFB = 2.5V) should be slightly longer than the maximum off-time encountered in normal operation. Setting a shorter off-time could result in inadequate overload protection, and setting a much longer off-time can affect the startup operation. 7 Minimum Load Current The LM25007 requires a minimum load current of ≊500 µA to ensure the boost capacitor (C5) is recharged sufficiently during each off-time. In this evaluation board, the minimum load current is provided by the feedback resistors (R2, R3), allowing the board’s minimum load current to be specified at zero. 9V-42V Input C3 C1 1.0 PF VCC LM25007 VIN 8 Minimum Off Timer On Timer R1 0.1 PF 115k 7 C4 0.1 PF BST V IN 2 0.01 PF L1 100 PH C5 6 SW Logic RON/SD 1 2.5V 4 Current Limit Detect and Off-Timer Regulation Comparator RTN 5 D1 C7 121k 2200 pF C8 0.01 PF RCL 3 R6 C6 R5 200k C9 FB 5V VOUT1 (V1) R2 3k R4 0 VOUT2 (V2) R3 3k C2 22 PF GND Figure 5. Complete Evaluation Board Schematic Table 1. Bill of Materials (BOM) Item Description Mfg., Part Number Package Value C1 C2 Ceramic Capacitor TDK C3225X7R2A105M 1210 1.0 µF, 100V Ceramic Capacitor TDK C3225X7R1C226M 1210 22 µF, 16V C3, 4 Ceramic Capacitor TDK C2012X7R2A104M 0805 0.1 µF, 100V C5,8 Ceramic Capacitor TDK C2012X7R2A103M 0805 0.01 µF, 100V Unpopulated 0805 TDK C2012X7R2A222M 0805 Unpopulated 0805 C6 C7 Ceramic Capacitor C9 2200 pF D1 Schottky Diode Diodes Inc. DFLS160 Power DI 123 60V, 1A L1 Power Inductor TDK SLF7045T-101MR50 7 mm x 7 mm 100 µH R1 Resistor Vishay CRCW08051153F 0805 115 kΩ R2, 3 Resistor Vishay CRCW08053011F 0805 3.01 kΩ R4 Resistor Vishay CRCW2010000Z 2010 0Ω R5 Resistor Vishay CRCW08052003F 0805 200 kΩ R6 Resistor Vishay CRCW08051213F 0805 121 kΩ U1 Switching Regulator LM25007 VSSOP-8 SNVA152A – March 2006 – Revised April 2013 Submit Documentation Feedback AN-1453 LM25007 Evaluation Board Copyright © 2006–2013, Texas Instruments Incorporated 5 Circuit Performance 8 www.ti.com Circuit Performance 100 Vin = 9V 90 EFFICIENCY (%) 15V 80 42V 30V 70 60 50 0 50 100 150 200 250 300 350 400 450 LOAD CURRENT (mA) Figure 6. Efficiency vs Load Current 100 450 mA EFFICIENCY (%) 90 80 150 mA IOUT = 50 mA 70 60 50 5 10 15 20 25 30 35 40 45 INPUT VOLTAGE (V) Figure 7. Efficiency vs Input Voltage 6 AN-1453 LM25007 Evaluation Board SNVA152A – March 2006 – Revised April 2013 Submit Documentation Feedback Copyright © 2006–2013, Texas Instruments Incorporated Circuit Performance www.ti.com 120 OUTPUT RIPPLE (mVp-p) 100 Option C 80 60 Option B 40 20 Options A & D 0 5 10 15 20 25 30 35 40 45 INPUT VOLTAGE (V) Figure 8. Output Voltage Ripple SWITCHING FREQUENCY (kHz) 400 350 300 250 VIN = 15V 200 0 50 100 150 200 250 300 350 400 450 LOAD CURRENT (mA) Figure 9. Switching Frequency vs. Load Current SNVA152A – March 2006 – Revised April 2013 Submit Documentation Feedback AN-1453 LM25007 Evaluation Board Copyright © 2006–2013, Texas Instruments Incorporated 7 PCB Layout 9 www.ti.com PCB Layout Figure 10. Board Silkscreen Figure 11. Board Top Layer 8 AN-1453 LM25007 Evaluation Board SNVA152A – March 2006 – Revised April 2013 Submit Documentation Feedback Copyright © 2006–2013, Texas Instruments Incorporated PCB Layout www.ti.com Figure 12. Board Bottom Layer (viewed from top) SNVA152A – March 2006 – Revised April 2013 Submit Documentation Feedback AN-1453 LM25007 Evaluation Board Copyright © 2006–2013, Texas Instruments Incorporated 9 IMPORTANT NOTICE Texas Instruments Incorporated and its subsidiaries (TI) reserve the right to make corrections, enhancements, improvements and other changes to its semiconductor products and services per JESD46, latest issue, and to discontinue any product or service per JESD48, latest issue. Buyers should obtain the latest relevant information before placing orders and should verify that such information is current and complete. All semiconductor products (also referred to herein as “components”) are sold subject to TI’s terms and conditions of sale supplied at the time of order acknowledgment. TI warrants performance of its components to the specifications applicable at the time of sale, in accordance with the warranty in TI’s terms and conditions of sale of semiconductor products. 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