LM2586T-3.3

LM2586 www.ti.com SNVS121C – MAY 2004 – REVISED JULY 2005 LM2586 SIMPLE SWITCHER® 3A Flyback Regulator with Shutdown Check for Samples: LM2586 FEATURES • 1 • • • • • 234 • • • • Requires few external components Family of standard inductors and transformers NPN output switches 3.0A, can stand off 65V Wide input voltage range: 4V to 40V Adjustable switching frequency: 100 kHz to 200 kHz External shutdown capability Draws less than 60 μA when shut down Frequency synchronization Current-mode operation for improved transient response, line regulation, and current limit • • Internal soft-start function reduces in-rush current during start-up Output transistor protected by current limit, under voltage lockout, and thermal shutdown System output voltage tolerance of ±4% max over line and load conditions TYPICAL APPLICATIONS • • • • Flyback regulator Forward converter Multiple-output regulator Simple boost regulator DESCRIPTION The LM2586 series of regulators are monolithic integrated circuits specifically designed for flyback, step-up (boost), and forward converter applications. The device is available in 4 different output voltage versions: 3.3V, 5.0V, 12V, and adjustable. Requiring a minimum number of external components, these regulators are cost effective, and simple to use. Included in the datasheet are typical circuits of boost and flyback regulators. Also listed are selector guides for diodes and capacitors and a family of standard inductors and flyback transformers designed to work with these switching regulators. The power switch is a 3.0A NPN device that can stand-off 65V. Protecting the power switch are current and thermal limiting circuits, and an undervoltage lockout circuit. This IC contains an adjustable frequency oscillator that can be programmed up to 200 kHz. The oscillator can also be synchronized with other devices, so that multiple devices can operate at the same switching frequency. Other features include soft start mode to reduce in-rush current during start up, and current mode control for improved rejection of input voltage and output load transients and cycle-by-cycle current limiting. The device also has a shutdown pin, so that it can be turned off externally. An output voltage tolerance of ±4%, within specified input voltages and output load conditions, is guaranteed for the power supply system. Connection Diagrams Figure 1. Bent, Staggered Leads 7-Lead TO-220 (T) Top View 1 2 3 4 Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet. SIMPLE SWITCHER is a registered trademark of Texas Instruments. Switchers Made Simple, Simple Switcher are registered trademarks of dcl_owner. All other trademarks are the property of their respective owners. PRODUCTION DATA information is current as of publication date. Products conform to specifications per the terms of the Texas Instruments standard warranty. Production processing does not necessarily include testing of all parameters. Copyright © 2004–2005, Texas Instruments Incorporated LM2586 SNVS121C – MAY 2004 – REVISED JULY 2005 www.ti.com Figure 2. Bent, Staggered Leads 7-Lead TO-220 (T) Side View Figure 3. 7-Lead TO-263 (S) Top View Figure 4. 7-Lead TO-263 (S) Side View These devices have limited built-in ESD protection. The leads should be shorted together or the device placed in conductive foam during storage or handling to prevent electrostatic damage to the MOS gates. Absolute Maximum Ratings (1) −0.4V ≤ VIN ≤ 45V Input Voltage −0.4V ≤ VSW ≤ 65V Switch Voltage Switch Current (2) Internally Limited Compensation Pin Voltage −0.4V ≤ VCOMP ≤ 2.4V Feedback Pin Voltage −0.4V ≤ VFB ≤ 2 VOUT −0.4V ≤ VSH ≤ 6V ON /OFF Pin Voltage −0.4V ≤ VSYNC ≤ 2V Sync Pin Voltage Power Dissipation (3) Internally Limited −65°C to +150°C Storage Temperature Range Lead Temperature (Soldering, 10 sec.) Maximum Junction Temperature 260°C (3) 150°C Minimum ESD Rating (C = 100 pF, R = 1.5 kΩ) (1) (2) (3) 2 kV Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. These ratings apply when the current is limited to less than 1.2 mA for pins 1, 2, 3, and 6. Operating ratings indicate conditions for which the device is intended to be functional, but device parameter specifications may not be guaranteed under these conditions. For guaranteed specifications and test conditions, see the Electrical Characteristics. Note that switch current and output current are not identical in a step-up regulator. Output current cannot be internally limited when the LM2586 is used as a step-up regulator. To prevent damage to the switch, the output current must be externally limited to 3A. However, output current is internally limited when the LM2586 is used as a flyback regulator (see the Application Hints section for more information). The junction temperature of the device (TJ) is a function of the ambient temperature (TA), the junction-to-ambient thermal resistance (θJA), and the power dissipation of the device (PD). A thermal shutdown will occur if the temperature exceeds the maximum junction temperature of the device: PD × θJA + TA(MAX) ≥ TJ(MAX). For a safe thermal design, check that the maximum power dissipated by the device is less than: PD ≤ [TJ(MAX) − TA(MAX)]/θJA. When calculating the maximum allowable power dissipation, derate the maximum junction temperature—this ensures a margin of safety in the thermal design. Operating Ratings 4V ≤ VIN ≤ 40V Supply Voltage Output Switch Voltage 0V ≤ VSW ≤ 60V Output Switch Current ISW ≤ 3.0A 2 Submit Documentation Feedback Copyright © 2004–2005, Texas Instruments Incorporated Product Folder Links: LM2586 LM2586 www.ti.com SNVS121C – MAY 2004 – REVISED JULY 2005 Operating Ratings (continued) −40°C ≤ TJ ≤ +125°C Junction Temp. Range Submit Documentation Feedback Copyright © 2004–2005, Texas Instruments Incorporated Product Folder Links: LM2586 3 LM2586 SNVS121C – MAY 2004 – REVISED JULY 2005 www.ti.com Electrical Characteristics LM2586-3.3 Specifications with standard type face are for TJ = 25°C, and those in bold type face apply over full Operating Temperature Range. Unless otherwise specified, VIN = 5V. Symbol Parameters Conditions SYSTEM PARAMETERS Test Circuit of Figure 5 VOUT Output Voltage Typical Min Max Units 3.3 3.17/3.14 3.43/3.46 V 20 50/100 mV 20 50/100 mV (1) VIN = 4V to 12V ILOAD = 0.3 to 1.2A ΔVOUT/ Line Regulation VIN = 4V to 12V ΔVIN ΔVOUT/ ILOAD = 0.3A Load Regulation VIN = 12V ΔILOAD η ILOAD = 0.3A to 1.2A Efficiency VIN = 5V, ILOAD = 0.3A 76 Output Reference Measured at Feedback Pin 3.3 Voltage VCOMP = 1.0V Reference Voltage VIN = 4V to 40V UNIQUE DEVICE PARAMETERS VREF ΔVREF % (2) 3.242/3.234 3.358/3.366 2.0 V mV Line Regulation GM AVOL (1) (2) (3) 4 Error Amp ICOMP = −30 μA to +30 μA Transconductance VCOMP = 1.0V Error Amp VCOMP = 0.5V to 1.6V Voltage Gain RCOMP = 1.0 MΩ 1.193 0.678 260 151/75 2.259 mmho V/V (3) External components such as the diode, inductor, input and output capacitors can affect switching regulator performance. When the LM2586 is used as shown in Figure 5 Figure 6, system performance will be as specified by the system parameters. All room temperature limits are 100% production tested, and all limits at temperature extremes are guaranteed via correlation using standard Statistical Quality Control (SQC) methods. A 1.0 MΩ resistor is connected to the compensation pin (which is the error amplifier output) to ensure accuracy in measuring AVOL. Submit Documentation Feedback Copyright © 2004–2005, Texas Instruments Incorporated Product Folder Links: LM2586 LM2586 www.ti.com SNVS121C – MAY 2004 – REVISED JULY 2005 LM2586-5.0 Symbol Parameters Conditions SYSTEM PARAMETERS Test Circuit of Figure 5 VOUT Output Voltage Typical Min Max Units 5.0 4.80/4.75 5.20/5.25 V 20 50/100 mV 20 50/100 mV (1) VIN = 4V to 12V ILOAD = 0.3A to 1.1A ΔVOUT/ Line Regulation VIN = 4V to 12V ΔVIN ΔVOUT/ ILOAD = 0.3A Load Regulation VIN = 12V ΔILOAD η ILOAD = 0.3A to 1.1A Efficiency UNIQUE DEVICE PARAMETERS VIN = 12V, ILOAD = 0.6A 80 % (2) VREF Output Reference Voltage Measured at Feedback Pin VCOMP = 1.0V 5.0 ΔVREF Reference Voltage VIN = 4V to 40V 3.3 4.913/4.900 5.088/5.100 V mV Line Regulation GM AVOL Error Amp ICOMP = −30 μA to +30 μA Transconductance VCOMP = 1.0V Error Amp VCOMP = 0.5V to 1.6V Voltage Gain (1) (2) (3) RCOMP = 1.0 MΩ 0.750 0.447 165 99/49 1.491 mmho V/V (3) External components such as the diode, inductor, input and output capacitors can affect switching regulator performance. When the LM2586 is used as shown in Figure 5 Figure 6, system performance will be as specified by the system parameters. All room temperature limits are 100% production tested, and all limits at temperature extremes are guaranteed via correlation using standard Statistical Quality Control (SQC) methods. A 1.0 MΩ resistor is connected to the compensation pin (which is the error amplifier output) to ensure accuracy in measuring AVOL. Submit Documentation Feedback Copyright © 2004–2005, Texas Instruments Incorporated Product Folder Links: LM2586 5 LM2586 SNVS121C – MAY 2004 – REVISED JULY 2005 www.ti.com LM2586-12 Symbol Parameters Conditions SYSTEM PARAMETERS Test Circuit of Figure 6 VOUT Output Voltage Typical Min Max Units 12.0 11.52/11.40 12.48/12.60 V 20 100/200 mV 20 100/200 mV (1) VIN = 4V to 10V ILOAD = 0.2A to 0.8A ΔVOUT/ Line Regulation VIN = 4V to 10V ΔVIN ΔVOUT/ ILOAD = 0.2A Load Regulation VIN = 10V ΔILOAD η ILOAD = 0.2A to 0.8A Efficiency UNIQUE DEVICE PARAMETERS VREF ΔVREF VIN = 10V, ILOAD = 0.6A 93 % (2) Output Reference Measured at Feedback Pin Voltage VCOMP = 1.0V Reference Voltage VIN = 4V to 40V 12.0 11.79/11.76 12.21/12.24 7.8 V mV Line Regulation GM AVOL Error Amp ICOMP = −30 μA to +30 μA Transconductance VCOMP = 1.0V Error Amp VCOMP = 0.5V to 1.6V Voltage Gain (1) (2) (3) 6 RCOMP = 1.0 MΩ 0.328 0.186 70 41/21 0.621 mmho V/V (3) External components such as the diode, inductor, input and output capacitors can affect switching regulator performance. When the LM2586 is used as shown in Figure 5 Figure 6, system performance will be as specified by the system parameters. All room temperature limits are 100% production tested, and all limits at temperature extremes are guaranteed via correlation using standard Statistical Quality Control (SQC) methods. A 1.0 MΩ resistor is connected to the compensation pin (which is the error amplifier output) to ensure accuracy in measuring AVOL. Submit Documentation Feedback Copyright © 2004–2005, Texas Instruments Incorporated Product Folder Links: LM2586 LM2586 www.ti.com SNVS121C – MAY 2004 – REVISED JULY 2005 LM2586-ADJ Symbol Parameters Conditions SYSTEM PARAMETERS Test Circuit of Figure 6 VOUT Output Voltage Typical Min Max Units 12.0 11.52/11.40 12.48/12.60 V 20 100/200 mV 20 100/200 mV (1) VIN = 4V to 10V ILOAD = 0.2A to 0.8A ΔVOUT/ Line Regulation VIN = 4V to 10V ΔVIN ΔVOUT/ ILOAD = 0.2A Load Regulation VIN = 10V ΔILOAD η ILOAD = 0.2A to 0.8A Efficiency UNIQUE DEVICE PARAMETERS VREF ΔVREF VIN = 10V, ILOAD = 0.6A 93 % (2) Output Reference Measured at Feedback Pin Voltage VCOMP = 1.0V Reference Voltage VIN = 4V to 40V 1.230 1.208/1.205 1.252/1.255 V 1.5 mV Line Regulation Error Amp ICOMP = −30 μA to +30 μA Transconductance VCOMP = 1.0V AVOL Error Amp Voltage Gain IB Error Amp GM 3.200 1.800 6.000 mmho VCOMP = 0.5V to 1.6V, RCOMP = 1.0 MΩ (3) 670 400/200 VCOMP = 1.0V 125 425/600 nA V/V Input Bias Current COMMON DEVICE PARAMETERS for all versions IS Input Supply Current IS/D Shutdown Input (2) Switch Off (4) 11 15.5/16.5 mA ISWITCH = 1.8A 50 100/115 mA VSH = 3V 16 100/300 μA Supply Current VUV Input Supply RLOAD = 100Ω 3.30 3.05 3.75 V 100 85/75 115/125 kHz Undervoltage Lockout fO Oscillator Frequency Measured at Switch Pin RLOAD = 100Ω, VCOMP = 1.0V Freq. Adj. Pin Open (Pin 1) RSET = 22 kΩ fSC Short-Circuit Measured at Switch Pin Frequency RLOAD = 100Ω 200 kHz 25 kHz VFEEDBACK = 1.15V VEAO Error Amplifier Output Swing Upper Limit 2.8 2.6/2.4 V (5) Lower Limit 0.25 0.40/0.55 V 260/320 μA (4) IEAO Error Amp (6) Output Current 165 110/70 (Source or Sink) (1) (2) (3) (4) (5) (6) External components such as the diode, inductor, input and output capacitors can affect switching regulator performance. When the LM2586 is used as shown in Figure 5 Figure 6, system performance will be as specified by the system parameters. All room temperature limits are 100% production tested, and all limits at temperature extremes are guaranteed via correlation using standard Statistical Quality Control (SQC) methods. A 1.0 MΩ resistor is connected to the compensation pin (which is the error amplifier output) to ensure accuracy in measuring AVOL. To measure this parameter, the feedback voltage is set to a high value, depending on the output version of the device, to force the error amplifier output low and the switch off. To measure this parameter, the feedback voltage is set to a low value, depending on the output version of the device, to force the error amplifier output high and the switch on. To measure the worst-case error amplifier output current, the LM2586 is tested with the feedback voltage set to its low value () and at its high value (). Submit Documentation Feedback Copyright © 2004–2005, Texas Instruments Incorporated Product Folder Links: LM2586 7 LM2586 SNVS121C – MAY 2004 – REVISED JULY 2005 www.ti.com LM2586-ADJ (continued) Symbol ISS Parameters Soft Start Current Conditions Typical Min Max Units 11.0 8.0/7.0 17.0/19.0 μA 98 93/90 VFEEDBACK = 0.92V VCOMP = 1.0V DMAX Maximum Duty Cycle RLOAD = 100Ω % (5) IL Switch Leakage Switch Off Current VSWITCH = 60V VSUS Switch Sustaining Voltage dV/dT = 1.5V/ns VSAT Switch Saturation Voltage ISWITCH = 3.0A ICL NPN Switch Current Limit VSTH Synchronization FSYNC = 200 kHz Threshold Voltage VCOMP = 1V, VIN = 5V Synchronization VIN = 5V Pin Current VCOMP = 1V, VSYNC = VSTH ON/OFF Pin (Pin 1) VCOMP = 1V ISYNC VSHTH Threshold Voltage ISH 15 65 0.45 μA V 0.65/0.9 V 4.0 3.0 7.0 A 0.75 0.625/0.40 0.875/1.00 V 200 μA 100 1.6 1.0/0.8 2.2/2.4 V 40 15/10 65/75 μA (7) ON/OFF Pin (Pin 1) VCOMP = 1V Current VSH = VSHTH Thermal Resistance T Package, Junction to Ambient (8) 65 θJA T Package, Junction to Ambient (9) 45 θJC T Package, Junction to Case 2 θJA S Package, Junction to Ambient 56 θJA S Package, Junction to Ambient 35 θJA S Package, Junction to Ambient 26 θJC S Package, Junction to Case 2 θJA 300/600 (10) °C/W (11) (12) (7) When testing the minimum value, do not sink current from this pin—isolate it with a diode. If current is drawn from this pin, the frequency adjust circuit will begin operation (see Figure 40). (8) Junction to ambient thermal resistance (no external heat sink) for the 7 lead TO-220 package mounted vertically, with ½ inch leads in a socket, or on a PC board with minimum copper area. (9) Junction to ambient thermal resistance (no external heat sink) for the 7 lead TO-220 package mounted vertically, with ½ inch leads soldered to a PC board containing approximately 4 square inches of (1 oz.) copper area surrounding the leads. (10) Junction to ambient thermal resistance for the 7 lead TO-263 mounted horizontally against a PC board area of 0.136 square inches (the same size as the TO-263 package) of 1 oz. (0.0014 in. thick) copper. (11) Junction to ambient thermal resistance for the 7 lead TO-263 mounted horizontally against a PC board area of 0.4896 square inches (3.6 times the area of the TO-263 package) of 1 oz. (0.0014 in. thick) copper. (12) Junction to ambient thermal resistance for the 7 lead TO-263 mounted horizontally against a PC board copper area of 1.0064 square inches (7.4 times the area of the TO-263 package) of 1 oz. (0.0014 in. thick) copper. Additional copper area will reduce thermal resistance further. See the thermal model in Switchers Made Simple® software. 8 Submit Documentation Feedback Copyright © 2004–2005, Texas Instruments Incorporated Product Folder Links: LM2586 LM2586 www.ti.com SNVS121C – MAY 2004 – REVISED JULY 2005 Typical Performance Characteristics Supply Current vs Temperature Reference Voltage vs Temperature ΔReference Voltage vs Supply Voltage Supply Current vs Switch Current Current Limit vs Temperature Feedback Pin Bias Current vs Temperature Switch Saturation Voltage vs Temperature Switch Transconductance vs Temperature Oscillator Frequency vs Temperature Error Amp Transconductance vs Temperature Submit Documentation Feedback Copyright © 2004–2005, Texas Instruments Incorporated Product Folder Links: LM2586 9 LM2586 SNVS121C – MAY 2004 – REVISED JULY 2005 www.ti.com Typical Performance Characteristics (continued) Error Amp Voltage Gain vs Temperature Short Circuit Frequency vs Temperature Shutdown Supply Current vs Temperature ON/OFF Pin Current vs Voltage Oscillator Frequency vs Resistance Flyback Regulator 10 Submit Documentation Feedback Copyright © 2004–2005, Texas Instruments Incorporated Product Folder Links: LM2586 LM2586 www.ti.com SNVS121C – MAY 2004 – REVISED JULY 2005 Test Circuits CIN1—100 μF, 25V Aluminum Electrolytic CIN2—0.1 μF Ceramic T—22 μH, 1:1 Schott #67141450 D—1N5820 COUT—680 μF, 16V Aluminum Electrolytic CC—0.47 μF Ceramic RC—2k Figure 5. LM2586-3.3 and LM2586-5.0 CIN1—100 μF, 25V Aluminum Electrolytic CIN2—0.1 μF Ceramic L—15 μH, Renco #RL-5472-5 D—1N5820 COUT—680 μF, 16V Aluminum Electrolytic CC—0.47 μF Ceramic RC—2k For 12V Devices: R1 = Short (0Ω) and 2 = Open For ADJ Devices: R1 = 48.75k, ±0.1% and 2 = 5.62k, ±0.1% Figure 6. LM2586-12 and LM2586-ADJ Submit Documentation Feedback Copyright © 2004–2005, Texas Instruments Incorporated Product Folder Links: LM2586 11 LM2586 SNVS121C – MAY 2004 – REVISED JULY 2005 www.ti.com Block Diagram For Fixed Versions 3.3V, R1 = 3.4k, R2 = 2k 5.0V, R1 = 6.15k, R2 = 2k 12V, R1 = 8.73k, R2 = 1k For Adj. Version R1 = Short (0Ω), R2 = Open Flyback Regulator Operation The LM2586 is ideally suited for use in the flyback regulator topology. The flyback regulator can produce a single output voltage, such as the one shown in Figure 7, or multiple output voltages. In Figure 7, the flyback regulator generates an output voltage that is inside the range of the input voltage. This feature is unique to flyback regulators and cannot be duplicated with buck or boost regulators. The operation of a flyback regulator is as follows (refer to Figure 7): when the switch is on, current flows through the primary winding of the transformer, T1, storing energy in the magnetic field of the transformer. Note that the primary and secondary windings are out of phase, so no current flows through the secondary when current flows through the primary. When the switch turns off, the magnetic field collapses, reversing the voltage polarity of the primary and secondary windings. Now rectifier D1 is forward biased and current flows through it, releasing the energy stored in the transformer. This produces voltage at the output. The output voltage is controlled by modulating the peak switch current. This is done by feeding back a portion of the output voltage to the error amp, which amplifies the difference between the feedback voltage and a 1.230V reference. The error amp output voltage is compared to a ramp voltage proportional to the switch current (i.e., inductor current during the switch on time). The comparator terminates the switch on time when the two voltages are equal, thereby controlling the peak switch current to maintain a constant output voltage. 12 Submit Documentation Feedback Copyright © 2004–2005, Texas Instruments Incorporated Product Folder Links: LM2586 LM2586 www.ti.com SNVS121C – MAY 2004 – REVISED JULY 2005 As shown in Figure 7, the LM2586 can be used as a flyback regulator by using a minimum number of external components. The switching waveforms of this regulator are shown in Figure 8. Typical Performance Characteristics observed during the operation of this circuit are shown in Figure 9. Figure 7. 12V Flyback Regulator Design Example Submit Documentation Feedback Copyright © 2004–2005, Texas Instruments Incorporated Product Folder Links: LM2586 13 LM2586 SNVS121C – MAY 2004 – REVISED JULY 2005 www.ti.com Typical Performance Characteristics A: Switch Voltage, 20V/div B: Switch Current, 2A/div C: Output Rectifier Current, 2A/div D: Output Ripple Voltage, 50 mV/div AC-Coupled Figure 8. Switching Waveforms Figure 9. VOUT Response to Load Current Step Typical Flyback Regulator Applications Figure 10 through Figure 15 show six typical flyback applications, varying from single output to triple output. Each drawing contains the part number(s) and manufacturer(s) for every component except the transformer. For the transformer part numbers and manufacturers' names, see the table in Table 1. For applications with different output voltages—requiring the LM2586-ADJ—or different output configurations that do not match the standard configurations, refer to the Switchers Made Simple software. Figure 10. Single-Output Flyback Regulator 14 Submit Documentation Feedback Copyright © 2004–2005, Texas Instruments Incorporated Product Folder Links: LM2586 LM2586 www.ti.com SNVS121C – MAY 2004 – REVISED JULY 2005 Figure 11. Single-Output Flyback Regulator Figure 12. Single-Output Flyback Regulator Submit Documentation Feedback Copyright © 2004–2005, Texas Instruments Incorporated Product Folder Links: LM2586 15 LM2586 SNVS121C – MAY 2004 – REVISED JULY 2005 www.ti.com Figure 13. Dual-Output Flyback Regulator Figure 14. Dual-Output Flyback Regulator 16 Submit Documentation Feedback Copyright © 2004–2005, Texas Instruments Incorporated Product Folder Links: LM2586 LM2586 www.ti.com SNVS121C – MAY 2004 – REVISED JULY 2005 Figure 15. Triple-Output Flyback Regulator TRANSFORMER SELECTION (T) Table 1 lists the standard transformers available for flyback regulator applications. Included in the table are the turns ratio(s) for each transformer, as well as the output voltages, input voltage ranges, and the maximum load currents for each circuit. Table 1. Transformer Selection Table Applications Figure 10 Figure 11 Figure 12 Figure 13 Figure 14 Transformers T7 T7 T7 T6 T6 T5 4V–6V 4V–6V 8V–16V 4V–6V 18V–36V 18V–36V VOUT1 3.3V 5V 12V 12V 12V 5V IOUT1 (Max) 1.4A 1A 0.8A 0.15A 0.6A 1.8A 1 1 1 1.2 1.2 0.5 VOUT2 −12V −12V 12V IOUT2(Max) 0.15A 0.6A 0.25A 1.2 1.2 VIN N1 N2 Figure 15 1.15 VOUT3 −12V IOUT3 (Max) 0.25A N3 1.15 Submit Documentation Feedback Copyright © 2004–2005, Texas Instruments Incorporated Product Folder Links: LM2586 17 LM2586 SNVS121C – MAY 2004 – REVISED JULY 2005 www.ti.com Table 2. Transformer Manufacturer Guide Transformer Type Manufacturers' Part Numbers Coilcraft (1) (2) (3) (4) Coilcraft (1) Surface Mount (1) Pulse (2) Surface Mount Pulse (2) Renco (3) Schott (4) T5 Q4338-B Q4437-B PE-68413 — RL-5532 67140890 T6 Q4339-B Q4438-B PE-68414 — RL-5533 67140900 T7 S6000-A S6057-A — PE-68482 RL-5751 26606 Coilcraft Inc., Phone: (800) 322-26451102 Silver Lake Road, Cary, IL 60013 Fax: (708) 639-1469 European Headquarters, 21 Napier Place Phone: +44 1236 730 595Wardpark North, Cumbernauld, Scotland G68 0LL Fax: +44 1236 730 627 Pulse Engineering Inc., Phone: (619) 674-810012220 World Trade Drive, San Diego, CA 92128 Fax: (619) 674-8262European Headquarters, Dunmore Road Phone: +353 93 24 107Tuam, Co. Galway, Ireland Fax: +353 93 24 459 Renco Electronics Inc., Phone: (800) 645-582860 Jeffryn Blvd. East, Deer Park, NY 11729 Fax: (516) 586-5562 Schott Corp., Phone: (612) 475-11731000 Parkers Lane Road, Wayzata, MN 55391 Fax: (612) 475-1786 TRANSFORMER FOOTPRINTS Figure 16 through Figure 30 show the footprints of each transformer, listed in Table 2. T7 T6 Figure 16. Coilcraft S6000-A (Top View) Figure 17. Coilcraft Q4339-B (Top View) T5 T5 Figure 18. Coilcraft Q4437-B (Surface Mount) (Top View) Figure 19. Coilcraft Q4338-B (Top View) T7 T6 Figure 20. Coilcraft S6057-A (Surface Mount) (Top View) 18 Figure 21. Coilcraft Q4438-B (Surface Mount) (Top View) Submit Documentation Feedback Copyright © 2004–2005, Texas Instruments Incorporated Product Folder Links: LM2586 LM2586 www.ti.com SNVS121C – MAY 2004 – REVISED JULY 2005 T7 T6 Figure 22. Pulse PE-68482 (Top View) Figure 23. Pulse PE-68414 (Surface Mount) (Top View) T5 T7 Figure 24. Pulse PE-68413 (Surface Mount) (Top View) Figure 25. Renco RL-5751 (Top View) T6 T5 Figure 26. Renco RL-5533 (Top View) Figure 27. Renco RL-5532 (Top View) T7 T6 Figure 28. Schott 26606 (Top View) Figure 29. Schott 67140900 (Top View) T5 Figure 30. Schott 67140890 (Top View) Submit Documentation Feedback Copyright © 2004–2005, Texas Instruments Incorporated Product Folder Links: LM2586 19 LM2586 SNVS121C – MAY 2004 – REVISED JULY 2005 www.ti.com Step-Up (Boost) Regulator Operation Figure 31 shows the LM2586 used as a step-up (boost) regulator. This is a switching regulator that produces an output voltage greater than the input supply voltage. A brief explanation of how the LM2586 Boost Regulator works is as follows (refer to Figure 31). When the NPN switch turns on, the inductor current ramps up at the rate of VIN/L, storing energy in the inductor. When the switch turns off, the lower end of the inductor flies above VIN, discharging its current through diode (D) into the output capacitor (COUT) at a rate of (VOUT − VIN)/L. Thus, energy stored in the inductor during the switch on time is transferred to the output during the switch off time. The output voltage is controlled by adjusting the peak switch current, as described in the flyback regulator section. Figure 31. 12V Boost Regulator By adding a small number of external components (as shown in Figure 31), the LM2586 can be used to produce a regulated output voltage that is greater than the applied input voltage. The switching waveforms observed during the operation of this circuit are shown in Figure 32. Typical performance of this regulator is shown in Figure 33. 20 Submit Documentation Feedback Copyright © 2004–2005, Texas Instruments Incorporated Product Folder Links: LM2586 LM2586 www.ti.com SNVS121C – MAY 2004 – REVISED JULY 2005 Typical Performance Characteristics A: Switch Voltage,10V/div B: Switch Current, 2A/div C: Inductor Current, 2A/div D: Output Ripple Voltage,100 mV/div, AC-Coupled Figure 32. Switching Waveforms Figure 33. VOUT Response to Load Current Step Typical Boost Regulator Applications Figure 34 Figure 35 through Figure 37 show four typical boost applications—one fixed and three using the adjustable version of the LM2586. Each drawing contains the part number(s) and manufacturer(s) for every component. For the fixed 12V output application, the part numbers and manufacturers' names for the inductor are listed in a table in Table 3. For applications with different output voltages, refer to the Switchers Made Simple software. Figure 34. +5V to +12V Boost Regulator Table 3 contains a table of standard inductors, by part number and corresponding manufacturer, for the fixed output regulator of Figure 34. Submit Documentation Feedback Copyright © 2004–2005, Texas Instruments Incorporated Product Folder Links: LM2586 21 LM2586 SNVS121C – MAY 2004 – REVISED JULY 2005 www.ti.com Table 3. Inductor Selection Table Coilcraft Pulse (1) Renco (2) Schott (3) (4) Schott (4) (Surface Mount) DO3316-153 (1) (2) (3) (4) PE-53898 RL-5471-7 67146510 67146540 Coilcraft Inc., Phone: (800) 322-26451102 Silver Lake Road, Cary, IL 60013 Fax: (708) 639-1469European Headquarters, 21 Napier Place Phone: +44 1236 730 595Wardpark North, Cumbernauld, Scotland G68 0LL Fax: +44 1236 730 627 Pulse Engineering Inc., Phone: (619) 674-810012220 World Trade Drive, San Diego, CA 92128 Fax: (619) 674-8262European Headquarters, Dunmore Road Phone: +353 93 24 107Tuam, Co. Galway, Ireland Fax: +353 93 24 459 Renco Electronics Inc., Phone: (800) 645-582860 Jeffryn Blvd. East, Deer Park, NY 11729 Fax: (516) 586-5562 Schott Corp., Phone: (612) 475-11731000 Parkers Lane Road, Wayzata, MN 55391 Fax: (612) 475-1786 Figure 35. +12V to +24V Boost Regulator (1) Figure 36. +24V to +36V Boost Regulator The LM2586 will require a heat sink in these applications. The size of the heat sink will depend on the maximum ambient temperature. To calculate the thermal resistance of the IC and the size of the heat sink needed, see the “Heat Sink/Thermal Considerations” section in the Application Hints. Figure 37. +24V to +48V Boost Regulator Application Hints LM2586 SPECIAL FEATURES Figure 38. Shutdown Operation 22 Submit Documentation Feedback Copyright © 2004–2005, Texas Instruments Incorporated Product Folder Links: LM2586 LM2586 www.ti.com SNVS121C – MAY 2004 – REVISED JULY 2005 SHUTDOWN CONTROL A feature of the LM2586 is its ability to be shut down using the ON /OFF pin (pin 1). This feature conserves input power by turning off the device when it is not in use. For proper operation, an isolation diode is required (as shown in Figure 38). The device will shut down when 3V or greater is applied on the ON /OFF pin, sourcing current into pin 1. In shut down mode, the device will draw typically 56 μA of supply current (16 μA to VIN and 40 μA to the ON /OFF pin). To turn the device back on, leave pin 1 floating, using an (isolation) diode, as shown in Figure 38 (for normal operation, do not source or sink current to or from this pin—see the next section). FREQUENCY ADJUSTMENT The switching frequency of the LM2586 can be adjusted with the use of an external resistor. This feature allows the user to optimize the size of the magnetics and the output capacitor(s) by tailoring the operating frequency. A resistor connected from pin 1 (the Freq. Adj. pin) to ground will set the switching frequency from 100 kHz to 200 kHz (maximum). As shown in Figure 38, the pin can be used to adjust the frequency while still providing the shut down function. A curve in the Performance Characteristics Section graphs the resistor value to the corresponding switching frequency. The table in Table 4 shows resistor values corresponding to commonly used frequencies. However, changing the LM2586's operating frequency from its nominal value of 100 kHz will change the magnetics selection and compensation component values. Table 4. Frequency Setting Resistor Guide RSET(kΩ) Frequency (kHz) Open 100 200 125 47 150 33 175 22 200 Figure 39. Frequency Synchronization FREQUENCY SYNCHRONIZATION Another feature of the LM2586 is the ability to synchronize the switching frequency to an external source, using the sync pin (pin 6). This feature allows the user to parallel multiple devices to deliver more output power. A negative falling pulse applied to the sync pin will synchronize the LM2586 to an external oscillator (see Figure 39 Figure 40). Use of this feature enables the LM2586 to be synchronized to an external oscillator, such as a system clock. This operation allows multiple power supplies to operate at the same frequency, thus eliminating frequency-related noise problems. Submit Documentation Feedback Copyright © 2004–2005, Texas Instruments Incorporated Product Folder Links: LM2586 23 LM2586 SNVS121C – MAY 2004 – REVISED JULY 2005 www.ti.com Figure 40. Waveforms of a Synchronized 12V Boost Regulator The scope photo in Figure 40 shows a LM2586 12V Boost Regulator synchronized to a 200 kHz signal. There is a 700 ns delay between the falling edge of the sync signal and the turning on of the switch. Figure 41. Boost Regulator PROGRAMMING OUTPUT VOLTAGE (SELECTING R1 AND R2) Referring to the adjustable regulator in Figure 41, the output voltage is programmed by the resistors R1 and R2 by the following formula: VOUT = VREF (1 + R1/R2) where VREF = 1.23V (1) Resistors R1 and R2 divide the output voltage down so that it can be compared with the 1.23V internal reference. With R2 between 1k and 5k, R1 is: R1 = R2 (VOUT/VREF − 1) where VREF = 1.23V (2) For best temperature coefficient and stability with time, use 1% metal film resistors. 24 Submit Documentation Feedback Copyright © 2004–2005, Texas Instruments Incorporated Product Folder Links: LM2586 LM2586 www.ti.com SNVS121C – MAY 2004 – REVISED JULY 2005 SHORT CIRCUIT CONDITION Due to the inherent nature of boost regulators, when the output is shorted (see Figure 41), current flows directly from the input, through the inductor and the diode, to the output, bypassing the switch. The current limit of the switch does not limit the output current for the entire circuit. To protect the load and prevent damage to the switch, the current must be externally limited, either by the input supply or at the output with an external current limit circuit. The external limit should be set to the maximum switch current of the device, which is 3A. In a flyback regulator application (Figure 42), using the standard transformers, the LM2586 will survive a short circuit to the main output. When the output voltage drops to 80% of its nominal value, the frequency will drop to 25 kHz. With a lower frequency, off times are larger. With the longer off times, the transformer can release all of its stored energy before the switch turns back on. Hence, the switch turns on initially with zero current at its collector. In this condition, the switch current limit will limit the peak current, saving the device. FLYBACK REGULATOR INPUT CAPACITORS A flyback regulator draws discontinuous pulses of current from the input supply. Therefore, there are two input capacitors needed in a flyback regulator—one for energy storage and one for filtering (see Figure 42). Both are required due to the inherent operation of a flyback regulator. To keep a stable or constant voltage supply to the LM2586, a storage capacitor (≥100 μF) is required. If the input source is a rectified DC supply and/or the application has a wide temperature range, the required rms current rating of the capacitor might be very large. This means a larger value of capacitance or a higher voltage rating will be needed for the input capacitor. The storage capacitor will also attenuate noise which may interfere with other circuits connected to the same input supply voltage. Figure 42. Flyback Regulator In addition, a small bypass capacitor is required due to the noise generated by the input current pulses. To eliminate the noise, insert a 1.0 μF ceramic capacitor between VIN and ground as close as possible to the device. SWITCH VOLTAGE LIMITS In a flyback regulator, the maximum steady-state voltage appearing at the switch, when it is off, is set by the transformer turns ratio, N, the output voltage, VOUT, and the maximum input voltage, VIN (Max): VSW(OFF) = VIN (Max) + (VOUT +VF)/N (3) Submit Documentation Feedback Copyright © 2004–2005, Texas Instruments Incorporated Product Folder Links: LM2586 25 LM2586 SNVS121C – MAY 2004 – REVISED JULY 2005 www.ti.com where VF is the forward biased voltage of the output diode, and is typically 0.5V for Schottky diodes and 0.8V for ultra-fast recovery diodes. In certain circuits, there exists a voltage spike, VLL, superimposed on top of the steady-state voltage (see Figure 8, waveform A). Usually, this voltage spike is caused by the transformer leakage inductance and/or the output rectifier recovery time. To “clamp” the voltage at the switch from exceeding its maximum value, a transient suppressor in series with a diode is inserted across the transformer primary (as shown in the circuit in Figure 7 and other flyback regulator circuits throughout the datasheet). The schematic in Figure 42 shows another method of clamping the switch voltage. A single voltage transient suppressor (the SA51A) is inserted at the switch pin. This method clamps the total voltage across the switch, not just the voltage across the primary. If poor circuit layout techniques are used (see the “Circuit Layout Guideline” section), negative voltage transients may appear on the Switch pin (pin 5). Applying a negative voltage (with respect to the IC's ground) to any monolithic IC pin causes erratic and unpredictable operation of that IC. This holds true for the LM2586 IC as well. When used in a flyback regulator, the voltage at the Switch pin (pin 5) can go negative when the switch turns on. The “ringing” voltage at the switch pin is caused by the output diode capacitance and the transformer leakage inductance forming a resonant circuit at the secondary(ies). The resonant circuit generates the “ringing” voltage, which gets reflected back through the transformer to the switch pin. There are two common methods to avoid this problem. One is to add an RC snubber around the output rectifier(s), as in Figure 42. The values of the resistor and the capacitor must be chosen so that the voltage at the Switch pin does not drop below −0.4V. The resistor may range in value between 10Ω and 1 kΩ, and the capacitor will vary from 0.001 μF to 0.1 μF. Adding a snubber will (slightly) reduce the efficiency of the overall circuit. The other method to reduce or eliminate the “ringing” is to insert a Schottky diode clamp between pins 5 and 4 (ground), also shown in Figure 42. This prevents the voltage at pin 5 from dropping below −0.4V. The reverse voltage rating of the diode must be greater than the switch off voltage. Figure 43. Input Line Filter OUTPUT VOLTAGE LIMITATIONS The maximum output voltage of a boost regulator is the maximum switch voltage minus a diode drop. In a flyback regulator, the maximum output voltage is determined by the turns ratio, N, and the duty cycle, D, by the equation: VOUT ≈ N × VIN × D/(1 − D) (4) The duty cycle of a flyback regulator is determined by the following equation: (5) Theoretically, the maximum output voltage can be as large as desired—just keep increasing the turns ratio of the transformer. However, there exists some physical limitations that prevent the turns ratio, and thus the output voltage, from increasing to infinity. The physical limitations are capacitances and inductances in the LM2586 switch, the output diode(s), and the transformer—such as reverse recovery time of the output diode (mentioned above). 26 Submit Documentation Feedback Copyright © 2004–2005, Texas Instruments Incorporated Product Folder Links: LM2586 LM2586 www.ti.com SNVS121C – MAY 2004 – REVISED JULY 2005 NOISY INPUT LINE CONDITION A small, low-pass RC filter should be used at the input pin of the LM2586 if the input voltage has an unusually large amount of transient noise, such as with an input switch that bounces. The circuit in Figure 43 demonstrates the layout of the filter, with the capacitor placed from the input pin to ground and the resistor placed between the input supply and the input pin. Note that the values of RIN and CIN shown in the schematic are good enough for most applications, but some readjusting might be required for a particular application. If efficiency is a major concern, replace the resistor with a small inductor (say 10 μH and rated at 200 mA). STABILITY All current-mode controlled regulators can suffer from an instability, known as subharmonic oscillation, if they operate with a duty cycle above 50%. To eliminate subharmonic oscillations, a minimum value of inductance is required to ensure stability for all boost and flyback regulators. The minimum inductance is given by: (6) where VSAT is the switch saturation voltage and can be found in the Characteristic Curves. Figure 44. Circuit Board Layout CIRCUIT LAYOUT GUIDELINES As in any switching regulator, layout is very important. Rapidly switching currents associated with wiring inductance generate voltage transients which can cause problems. For minimal inductance and ground loops, keep the length of the leads and traces as short as possible. Use single point grounding or ground plane construction for best results. Separate the signal grounds from the power grounds (as indicated in Figure 44). When using the Adjustable version, physically locate the programming resistors as near the regulator IC as possible, to keep the sensitive feedback wiring short. HEAT SINK/THERMAL CONSIDERATIONS In many cases, a heat sink is not required to keep the LM2586 junction temperature within the allowed operating temperature range. For each application, to determine whether or not a heat sink will be required, the following must be identified: 1) Maximum ambient temperature (in the application). 2) Maximum regulator power dissipation (in the application). 3) Maximum allowed junction temperature (125°C for the LM2586). For a safe, conservative design, a temperature approximately 15°C cooler than the maximum junction temperature should be selected (110°C). 4) LM2586 package thermal resistances θJA and θJC (given in the Electrical Characteristics). Total power dissipated (PD) by the LM2586 can be estimated as follows: Submit Documentation Feedback Copyright © 2004–2005, Texas Instruments Incorporated Product Folder Links: LM2586 27 LM2586 SNVS121C – MAY 2004 – REVISED JULY 2005 www.ti.com (7) VIN is the minimum input voltage, VOUT is the output voltage, N is the transformer turns ratio, D is the duty cycle, and ILOAD is the maximum load current (and ∑ILOAD is the sum of the maximum load currents for multiple-output flyback regulators). The duty cycle is given by: (8) where VF is the forward biased voltage of the diode and is typically 0.5V for Schottky diodes and 0.8V for fast recovery diodes. VSAT is the switch saturation voltage and can be found in the Characteristic Curves. When no heat sink is used, the junction temperature rise is: ΔTJ = PD • θJA. (9) Adding the junction temperature rise to the maximum ambient temperature gives the actual operating junction temperature: TJ = ΔTJ + TA. (10) If the operating junction temperature exceeds the maximum junction temperatue in item 3 above, then a heat sink is required. When using a heat sink, the junction temperature rise can be determined by the following: ΔTJ = PD • (θJC + θInterface + θHeat Sink) (11) Again, the operating junction temperature will be: TJ = ΔTJ + TA (12) As before, if the maximum junction temperature is exceeded, a larger heat sink is required (one that has a lower thermal resistance). Included in the Switchers Made Simple® design software is a more precise (non-linear) thermal model that can be used to determine junction temperature with different input-output parameters or different component values. It can also calculate the heat sink thermal resistance required to maintain the regulator junction temperature below the maximum operating temperature. To further simplify the flyback regulator design procedure, National Semiconductor is making available computer design software to be used with the Simple Switcher® line of switching regulators. Switchers Made Simpleis available on a 3½″ diskette for IBM compatible computers from a National Semiconductor sales office in your area or the National Semiconductor Customer Response Center (1-800-272-9959). 28 Submit Documentation Feedback Copyright © 2004–2005, Texas Instruments Incorporated Product Folder Links: LM2586 PACKAGE OPTION ADDENDUM www.ti.com 17-Nov-2012 PACKAGING INFORMATION Orderable Device Status (1) Package Type Package Pins Package Qty Drawing Eco Plan Lead/Ball Finish (2) MSL Peak Temp Samples (3) (Requires Login) LM2586S-12 ACTIVE DDPAK KTW 7 45 TBD CU SNPB Level-3-235C-168 HR LM2586S-12/NOPB ACTIVE DDPAK KTW 7 45 Pb-Free (RoHS Exempt) CU SN Level-3-245C-168 HR LM2586S-3.3 ACTIVE DDPAK KTW 7 45 TBD CU SNPB Level-3-235C-168 HR LM2586S-3.3/NOPB ACTIVE DDPAK KTW 7 45 Pb-Free (RoHS Exempt) CU SN Level-3-245C-168 HR LM2586S-5.0 ACTIVE DDPAK KTW 7 45 TBD CU SNPB Level-3-235C-168 HR LM2586S-5.0/NOPB ACTIVE DDPAK KTW 7 45 Pb-Free (RoHS Exempt) CU SN Level-3-245C-168 HR LM2586S-ADJ ACTIVE DDPAK KTW 7 45 TBD CU SNPB Level-3-235C-168 HR LM2586S-ADJ/NOPB ACTIVE DDPAK KTW 7 45 Pb-Free (RoHS Exempt) CU SN Level-3-245C-168 HR LM2586SX-3.3 ACTIVE DDPAK KTW 7 500 TBD CU SNPB Level-3-235C-168 HR LM2586SX-3.3/NOPB ACTIVE DDPAK KTW 7 500 Pb-Free (RoHS Exempt) CU SN Level-3-245C-168 HR LM2586SX-5.0 ACTIVE DDPAK KTW 7 500 TBD CU SNPB Level-3-235C-168 HR LM2586SX-5.0/NOPB ACTIVE DDPAK KTW 7 500 Pb-Free (RoHS Exempt) CU SN Level-3-245C-168 HR LM2586SX-ADJ ACTIVE DDPAK KTW 7 500 TBD CU SNPB Level-3-235C-168 HR LM2586SX-ADJ/NOPB ACTIVE DDPAK KTW 7 500 Pb-Free (RoHS Exempt) CU SN Level-3-245C-168 HR LM2586T-3.3 ACTIVE TO-220 NDZ 7 45 TBD CU SNPB Level-1-NA-UNLIM LM2586T-3.3/NOPB ACTIVE TO-220 NDZ 7 45 Pb-Free (RoHS Exempt) CU SN Level-1-NA-UNLIM LM2586T-5.0 ACTIVE TO-220 NDZ 7 45 TBD CU SNPB Level-1-NA-UNLIM LM2586T-5.0/NOPB ACTIVE TO-220 NDZ 7 45 Pb-Free (RoHS Exempt) CU SN Level-1-NA-UNLIM LM2586T-ADJ ACTIVE TO-220 NDZ 7 45 TBD CU SNPB Level-1-NA-UNLIM LM2586T-ADJ/NOPB ACTIVE TO-220 NDZ 7 45 Pb-Free (RoHS Exempt) CU SN Level-1-NA-UNLIM (1) The marketing status values are defined as follows: ACTIVE: Product device recommended for new designs. Addendum-Page 1 PACKAGE OPTION ADDENDUM www.ti.com 17-Nov-2012 LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect. NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design. PREVIEW: Device has been announced but is not in production. Samples may or may not be available. OBSOLETE: TI has discontinued the production of the device. (2) Eco Plan - The planned eco-friendly classification: Pb-Free (RoHS), Pb-Free (RoHS Exempt), or Green (RoHS & no Sb/Br) - please check http://www.ti.com/productcontent for the latest availability information and additional product content details. TBD: The Pb-Free/Green conversion plan has not been defined. Pb-Free (RoHS): TI's terms "Lead-Free" or "Pb-Free" mean semiconductor products that are compatible with the current RoHS requirements for all 6 substances, including the requirement that lead not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, TI Pb-Free products are suitable for use in specified lead-free processes. Pb-Free (RoHS Exempt): This component has a RoHS exemption for either 1) lead-based flip-chip solder bumps used between the die and package, or 2) lead-based die adhesive used between the die and leadframe. The component is otherwise considered Pb-Free (RoHS compatible) as defined above. Green (RoHS & no Sb/Br): TI defines "Green" to mean Pb-Free (RoHS compatible), and free of Bromine (Br) and Antimony (Sb) based flame retardants (Br or Sb do not exceed 0.1% by weight in homogeneous material) (3) MSL, Peak Temp. -- The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder temperature. Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is provided. TI bases its knowledge and belief on information provided by third parties, and makes no representation or warranty as to the accuracy of such information. Efforts are underway to better integrate information from third parties. TI has taken and continues to take reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on incoming materials and chemicals. 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Addendum-Page 2 PACKAGE MATERIALS INFORMATION www.ti.com 17-Nov-2012 TAPE AND REEL INFORMATION *All dimensions are nominal Device Package Package Pins Type Drawing SPQ Reel Reel A0 Diameter Width (mm) (mm) W1 (mm) B0 (mm) K0 (mm) P1 (mm) W Pin1 (mm) Quadrant LM2586SX-3.3 DDPAK KTW 7 500 330.0 24.4 10.75 14.85 5.0 16.0 24.0 Q2 LM2586SX-3.3/NOPB DDPAK KTW 7 500 330.0 24.4 10.75 14.85 5.0 16.0 24.0 Q2 LM2586SX-5.0 DDPAK KTW 7 500 330.0 24.4 10.75 14.85 5.0 16.0 24.0 Q2 LM2586SX-5.0/NOPB DDPAK KTW 7 500 330.0 24.4 10.75 14.85 5.0 16.0 24.0 Q2 LM2586SX-ADJ DDPAK KTW 7 500 330.0 24.4 10.75 14.85 5.0 16.0 24.0 Q2 LM2586SX-ADJ/NOPB DDPAK KTW 7 500 330.0 24.4 10.75 14.85 5.0 16.0 24.0 Q2 Pack Materials-Page 1 PACKAGE MATERIALS INFORMATION www.ti.com 17-Nov-2012 *All dimensions are nominal Device Package Type Package Drawing Pins SPQ Length (mm) Width (mm) Height (mm) LM2586SX-3.3 DDPAK KTW 7 500 358.0 343.0 63.0 LM2586SX-3.3/NOPB DDPAK KTW 7 500 358.0 343.0 63.0 LM2586SX-5.0 DDPAK KTW 7 500 358.0 343.0 63.0 LM2586SX-5.0/NOPB DDPAK KTW 7 500 358.0 343.0 63.0 LM2586SX-ADJ DDPAK KTW 7 500 358.0 343.0 63.0 LM2586SX-ADJ/NOPB DDPAK KTW 7 500 358.0 343.0 63.0 Pack Materials-Page 2 MECHANICAL DATA NDZ0007B TA07B (Rev E) www.ti.com MECHANICAL DATA MPSF015 – AUGUST 2001 KTW (R-PSFM-G7) PLASTIC FLANGE-MOUNT 0.410 (10,41) 0.385 (9,78) 0.304 (7,72) –A– 0.006 –B– 0.303 (7,70) 0.297 (7,54) 0.0625 (1,587) H 0.055 (1,40) 0.0585 (1,485) 0.300 (7,62) 0.064 (1,63) 0.045 (1,14) 0.252 (6,40) 0.056 (1,42) 0.187 (4,75) 0.370 (9,40) 0.179 (4,55) 0.330 (8,38) H 0.296 (7,52) A 0.605 (15,37) 0.595 (15,11) 0.012 (0,305) C 0.000 (0,00) 0.019 (0,48) 0.104 (2,64) 0.096 (2,44) H 0.017 (0,43) 0.050 (1,27) C C F 0.034 (0,86) 0.022 (0,57) 0.010 (0,25) M B 0.026 (0,66) 0.014 (0,36) 0°~3° AM C M 0.183 (4,65) 0.170 (4,32) 4201284/A 08/01 NOTES: A. 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