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LM2595
SNVS122C – MAY 1999 – REVISED MAY 2016
LM2595 SIMPLE SWITCHER® Power Converter 150-kHz 1-A Step-Down Voltage Regulator
1 Features
3 Description
•
•
The LM2595 series of regulators are monolithic
integrated circuits that provide all the active functions
for a step-down (buck) switching regulator, capable of
driving a 1-A load with excellent line and load
regulation. These devices are available in fixed output
voltages of 3.3 V, 5 V, 12 V, and an adjustable output
version.
1
•
•
•
•
•
•
•
•
•
•
•
3.3-V, 5-V, 12-V, and Adjustable Output Versions
Adjustable Version Output Voltage Range, 1.2 V
to 37 V ±4% Maximum Over Line and Load
Conditions
Available in TO-220 and TO-263 Surface-Mount
Packages
Ensured 1-A Output Load Current
Input Voltage Range Up to 40 V
Requires Only 4 External Components
Excellent Line and Load Regulation Specifications
150-kHz Fixed-Frequency Internal Oscillator
TTL Shutdown Capability
Low Power Standby Mode, IQ, Typically 85 μA
High Efficiency
Uses Readily Available Standard Inductors
Thermal Shutdown and Current-Limit Protection
Requiring a minimum number of external
components, these regulators are simple to use and
include internal frequency compensation, and a fixedfrequency oscillator.
The LM2595 series operates at a switching frequency
of 150 kHz, thus allowing smaller-sized filter
components than what would be needed with lowerfrequency switching regulators. Available in a
standard 5-pin TO-220 package with several different
lead bend options, and a 5-pin TO-263 surface-mount
package. Typically, for output voltages less than
12 V, and ambient temperatures less than 50°C, no
heat sink is required.
2 Applications
•
•
•
•
Simple High-Efficiency Step-Down (Buck)
Regulator
Efficient Preregulator for Linear Regulators
On-Card Switching Regulators
Positive-to-Negative Converter
Device Information(1)
PART NUMBER
LM2595
PACKAGE
BODY SIZE (NOM)
TO-263 (5)
10.16 mm × 8.42 mm
TO-220 (5)
14.986 mm × 10.16 mm
(1) For all available packages, see the orderable addendum at
the end of the data sheet.
Typical Application
(Fixed Output Voltage Versions)
1
An IMPORTANT NOTICE at the end of this data sheet addresses availability, warranty, changes, use in safety-critical applications,
intellectual property matters and other important disclaimers. PRODUCTION DATA.
LM2595
SNVS122C – MAY 1999 – REVISED MAY 2016
www.ti.com
Table of Contents
1
2
3
4
5
6
7
Features ..................................................................
Applications ...........................................................
Description .............................................................
Revision History.....................................................
Description (continued).........................................
Pin Configuration and Functions .........................
Specifications.........................................................
1
1
1
2
3
3
4
7.1
7.2
7.3
7.4
7.5
7.6
7.7
7.8
7.9
4
4
4
4
5
5
5
6
Absolute Maximum Ratings .....................................
ESD Ratings..............................................................
Recommended Operating Conditions.......................
Thermal Information ..................................................
Electrical Characteristics – 3.3 V ..............................
Electrical Characteristics – 5 V .................................
Electrical Characteristics – 12 V ...............................
Electrical Characteristics – Adjustable......................
Electrical Characteristics – All Output Voltage
Versions .....................................................................
7.10 Typical Characteristics ............................................
8
6
7
Detailed Description ............................................ 10
8.1
8.2
8.3
8.4
9
Overview .................................................................
Functional Block Diagram .......................................
Feature Description.................................................
Device Functional Modes........................................
10
10
10
14
Application and Implementation ........................ 15
9.1 Application Information............................................ 15
9.2 Typical Applications ................................................ 23
10 Power Supply Recommendations ..................... 31
11 Layout................................................................... 31
11.1 Layout Guidelines ................................................. 31
11.2 Layout Examples................................................... 31
11.3 Thermal Considerations ........................................ 32
12 Device and Documentation Support ................. 34
12.1
12.2
12.3
12.4
Community Resources..........................................
Trademarks ...........................................................
Electrostatic Discharge Caution ............................
Glossary ................................................................
34
34
34
34
13 Mechanical, Packaging, and Orderable
Information ........................................................... 34
4 Revision History
NOTE: Page numbers for previous revisions may differ from page numbers in the current version.
Changes from Revision B (April 2013) to Revision C
Page
•
Added ESD Ratings table, Feature Description section, Device Functional Modes, Application and Implementation
section, Power Supply Recommendations section, Layout section, Device and Documentation Support section, and
Mechanical, Packaging, and Orderable Information section. ................................................................................................. 1
•
Removed all references to design software Switchers Made Simple .................................................................................... 1
•
Removed NEB package from data sheet .............................................................................................................................. 4
Changes from Revision A (April 2013) to Revision B
•
2
Page
Changed layout of National Semiconductor Data Sheet to TI format .................................................................................. 32
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5 Description (continued)
A standard series of inductors are available from several different manufacturers optimized for use with the
LM2595 series. This feature greatly simplifies the design of switch-mode power supplies.
Other features include a ±4% tolerance on output voltage under specified input voltage and output load
conditions, and ±15% on the oscillator frequency. External shutdown is included, featuring typically 85-μA standby current. Self protection features include a two stage frequency reducing current limit for the output switch and
an overtemperature shutdown for complete protection under fault conditions.
6 Pin Configuration and Functions
NDH Package
5–Pin TO-220
Top View
KTT Package
5-Pin TO-263
Top View
Pin Functions
PIN
I/O
DESCRIPTION
NO.
NAME
1
Output
O
Internal switch. The voltage at this pin switches between (+VIN − VSAT) and approximately –0.5 V,
with a duty cycle of approximately VOUT/VIN. To minimize coupling to sensitive circuitry, the PCB
copper area connected to this pin must be kept to a minimum.
2
+VIN
I
This is the positive input supply for the IC switching regulator. A suitable input bypass capacitor must
be present at this pin to minimize voltage transients and to supply the switching currents needed by
the regulator.
3
Ground
—
4
Feedback
I
Senses the regulated output voltage to complete the feedback loop.
I
Allows the switching regulator circuit to be shut down using logic level signals, thus dropping the total
input supply current to approximately 85 μA. Pulling this pin below a threshold voltage of
approximately 1.3 V turns the regulator on, and pulling this pin above 1.3 V (up to a maximum of
25 V) shuts the regulator down. If this shutdown feature is not needed, the ON/OFF pin can be wired
to the ground pin or it can be left open, in either case the regulator is in the ON condition.
5
ON/OFF
Circuit ground.
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7 Specifications
7.1 Absolute Maximum Ratings
(1) (2)
MIN
Maximum supply voltage
MAX
UNIT
45
V
ON/OFF pin input voltage
–0.3
25
V
Feedback pin voltage
–0.3
25
V
–1
V
Output voltage to ground (steady-state)
Power dissipation
Lead temperature
Internally limited
KTT package
Vapor phase (60 sec)
215
Infrared (10 sec)
245
NDH package (soldering, 10 sec)
Maximum junction temperature
Storage temperature, Tstg
(1)
(2)
°C
260
–65
150
°C
150
°C
Stresses beyond those listed under Absolute Maximum Ratings may cause permanent damage to the device. These are stress ratings
only, which do not imply functional operation of the device at these or any other conditions beyond those indicated under Recommended
Operating Conditions. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability.
If Military/Aerospace specified devices are required, please contact the Texas Instruments Sales Office/ Distributors for availability and
specifications.
7.2 ESD Ratings
V(ESD)
(1)
Electrostatic discharge
Human-body model (HBM), per ANSI/ESDA/JEDEC JS-001 (1)
VALUE
UNIT
±2000
V
JEDEC document JEP155 states that 500-V HBM allows safe manufacturing with a standard ESD control process.
7.3 Recommended Operating Conditions
MIN
MAX
Supply voltage
4.5
40
UNIT
V
Temperature range, TJ
–40
125
°C
7.4 Thermal Information
LM2595
THERMAL METRIC (1)
Junction-to-ambient
thermal resistance (2) (3)
RθJA
RθJC(top)
(1)
(2)
(3)
4
KTT
(TO-263)
NDH
(TO-220)
5 PINS
5 PINS
Printed-circuit board with 1-oz copper area of approximately 1 in2
—
50
Printed-circuit board with 0.5 in2 of 1-oz copper area
50
—
Printed-circuit board with 2.5 in of 1-oz copper area
30
—
Double-sided, printed-circuit board with 3 in2 of 1-oz copper area
20
—
2
2
°C/W
2
Junction-to-case (top) thermal resistance
UNIT
°C/W
For more information about traditional and new thermal metrics, see the Semiconductor and IC Package Thermal Metrics application
report, SPRA953.
The package thermal impedance is calculated in accordance to JESD 51-7.
Thermal resistances were simulated on a 4-layer, JEDEC board
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7.5 Electrical Characteristics – 3.3 V
Specifications are for TJ = 25°C (unless otherwise noted).
PARAMETER
SYSTEM PARAMETERS
(3)
Output voltage
4.75 V ≤ VIN ≤ 40 V,
0.1 A ≤ ILOAD ≤ 1 A
η
Efficiency
VIN = 12 V, ILOAD = 1 A
(2)
(3)
MIN (1)
TJ = 25°C
3.168
Over full operating temperature range
3.135
TYP (2)
MAX (1)
UNIT
(see Figure 35 for test circuit)
VOUT
(1)
TEST CONDITIONS
3.3
3.432
V
3.465
78%
All limits specified at room temperature and temperature extremes. All room temperature limits are 100% production tested. All limits at
temperature extremes are specified via correlation using standard Statistical Quality Control (SQC) methods. All limits are used to
calculate Average Outgoing Quality Level (AOQL).
Typical numbers are at 25°C and represent the most likely norm.
External components such as the catch diode, inductor, input and output capacitors, and voltage programming resistors can affect
switching regulator system performance. When the LM2595 is used as shown in the Figure 35 test circuit, system performance is shown
in the test conditions column.
7.6 Electrical Characteristics – 5 V
Specifications are for TJ = 25°C (unless otherwise noted).
PARAMETER
TEST CONDITIONS
MIN (1)
TYP (2)
4.8
5
MAX (1)
UNIT
SYSTEM PARAMETERS (3) (see Figure 35 for test circuit)
VOUT
Output voltage
7 V ≤ VIN ≤ 40 V,
0.1 A ≤ ILOAD ≤ 1 A
η
Efficiency
VIN = 12 V, ILOAD = 1 A
(1)
(2)
(3)
TJ = 25°C
Over full operating temperature range
4.75
5.2
V
5.25
82%
All limits specified at room temperature and temperature extremes. All room temperature limits are 100% production tested. All limits at
temperature extremes are specified via correlation using standard Statistical Quality Control (SQC) methods. All limits are used to
calculate Average Outgoing Quality Level (AOQL).
Typical numbers are at 25°C and represent the most likely norm.
External components such as the catch diode, inductor, input and output capacitors, and voltage programming resistors can affect
switching regulator system performance. When the LM2595 is used as shown in the Figure 35 test circuit, system performance is shown
in the test conditions column.
7.7 Electrical Characteristics – 12 V
Specifications are for TJ = 25°C (unless otherwise noted).
PARAMETER
SYSTEM PARAMETERS
TEST CONDITIONS
(3)
Output voltage
15 V ≤ VIN ≤ 40 V,
0.1 A ≤ ILOAD ≤ 1 A
η
Efficiency
VIN = 25 V, ILOAD = 1 A
(2)
(3)
TYP (2)
MAX (1)
11.52
12
12.48
UNIT
(see Figure 35 for test circuit)
VOUT
(1)
MIN (1)
TJ = 25°C
Over full operating temperature range
11.4
12.6
V
90%
All limits specified at room temperature and temperature extremes. All room temperature limits are 100% production tested. All limits at
temperature extremes are specified via correlation using standard Statistical Quality Control (SQC) methods. All limits are used to
calculate Average Outgoing Quality Level (AOQL).
Typical numbers are at 25°C and represent the most likely norm.
External components such as the catch diode, inductor, input and output capacitors, and voltage programming resistors can affect
switching regulator system performance. When the LM2595 is used as shown in the Figure 35 test circuit, system performance is shown
in the test conditions column.
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7.8 Electrical Characteristics – Adjustable
Specifications are for TJ = 25°C (unless otherwise noted).
PARAMETER
SYSTEM PARAMETERS
TEST CONDITIONS
(3)
MIN (1)
Feedback voltage
Efficiency
η
(1)
(2)
(3)
MAX (1)
UNIT
(see Figure 35 for test circuit)
4.5 V ≤ VIN ≤ 40 V, 0.1 A ≤ ILOAD ≤ 1 A
VFB
TYP (2)
1.23
TJ = 25°C
VOUT programmed for 3 V,
circuit of Figure 35
Over full operating temperature range
1.193
1.267
1.18
1.28
VIN = 12 V, VOUT = 3 V, ILOAD = 1 A
V
78%
All limits specified at room temperature and temperature extremes. All room temperature limits are 100% production tested. All limits at
temperature extremes are specified via correlation using standard Statistical Quality Control (SQC) methods. All limits are used to
calculate Average Outgoing Quality Level (AOQL).
Typical numbers are at 25°C and represent the most likely norm.
External components such as the catch diode, inductor, input and output capacitors, and voltage programming resistors can affect
switching regulator system performance. When the LM2595 is used as shown in the Figure 35 test circuit, system performance is shown
in the test conditions column.
7.9 Electrical Characteristics – All Output Voltage Versions
Specifications are for TJ = 25°C, ILOAD = 200 mA, VIN = 12 V for the 3.3-V, 5-V, and adjustable versions, and VIN = 24 V for the
12-V version (unless otherwise noted).
PARAMETER
TEST CONDITIONS
MIN (1)
TYP (2)
MAX (1)
10
50
UNIT
DEVICE PARAMETERS
Ib
Feedback bias current
fO
Oscillator frequency (3)
VSAT
Saturation voltage
DC
Adjustable version only,
VFB = 1.3 V
TJ = 25°C
Over full operating
temperature range
100
TJ = 25°C
127
Over full operating temperature range
110
IOUT = 1 A, TJ = 25°C (4) (5)
1
Over full operating temperature range
100%
0%
TJ = 25°C
IL
Output leakage current
IQ
Quiescent current (6)
Peak current (4) (5)
Over full operating
temperature range
1.2
1.5
1.15
Output = −1 V
V
A
50
μA
15
mA
5
10
mA
85
200
2
ON/OFF pin = 5 V (OFF) (7)
kHz
2.4
2.6
Output = 0 V (4) (6) (7)
TJ = 25°C
Standby quiescent current
1.2
1.3
Min duty cycle (OFF) (6)
Current limit
173
173
Max duty cycle (ON) (5)
ICL
ISTBY
150
nA
Over full operating
temperature range
250
μA
ON/OFF CONTROL (see Figure 35 for test circuit)
ON/OFF pin logic input
1.3
VIH
Threshold voltage, high
Regulator ON, over full operating temperature range
VIL
Threshold voltage, low
Regulator OFF, over full operating temperature range
IH
ON/OFF pin input current, high
VLOGIC = 2.5 V (regulator OFF)
IL
ON/OFF pin input current, low
VLOGIC = 0.5 V (regulator ON)
(1)
(2)
(3)
(4)
(5)
(6)
(7)
6
V
0.6
V
5
15
μA
0.02
5
μA
2
V
All limits specified at room temperature and temperature extremes. All room temperature limits are 100% production tested. All limits at
temperature extremes are specified via correlation using standard Statistical Quality Control (SQC) methods. All limits are used to
calculate Average Outgoing Quality Level (AOQL).
Typical numbers are at 25°C and represent the most likely norm.
The switching frequency is reduced when the second stage current limit is activated. The amount of reduction is determined by the
severity of current overload.
No diode, inductor or capacitor connected to output pin.
Feedback pin removed from output and connected to 0 V to force the output transistor switch ON.
Feedback pin removed from output and connected to 12 V for the 3.3-V, 5-V, and adjustable versions, and 15 V for the 12-V version, to
force the output transistor switch OFF.
VIN = 40 V.
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7.10 Typical Characteristics
Circuit of Figure 35
Figure 1. Normalized Output Voltage
Figure 2. Line Regulation
Figure 3. Efficiency
Figure 4. Switch Saturation Voltage
Figure 5. Switch Current Limit
Figure 6. Dropout Voltage
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Typical Characteristics (continued)
Circuit of Figure 35
8
Figure 7. Operating Quiescent Current
Figure 8. Shutdown Quiescent Current
Figure 9. Minimum Operating Supply Voltage
Figure 10. ON /OFF Threshold Voltage
Figure 11. ON/OFF Pin Current (Sinking)
Figure 12. Switching Frequency
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Typical Characteristics (continued)
Circuit of Figure 35
Figure 13. Feedback Pin Bias Current
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8 Detailed Description
8.1 Overview
The LM2595 SIMPLE SWITCHER® regulator is an easy-to-use, nonsynchronous step-down DC-DC converter
with a wide input voltage range up to 40 V. The regulator is capable of delivering up to 1-A DC load current with
excellent line and load regulation. These devices are available in fixed output voltages of 3.3-V, 5-V, 12-V, and
an adjustable output version. The family requires few external components, and the pin arrangement was
designed for simple, optimum PCB layout.
8.2 Functional Block Diagram
8.3 Feature Description
8.3.1 Delayed Start-Up
The circuit in Figure 14 uses the ON/OFF pin to provide a time delay between the time the input voltage is
applied and the time the output voltage comes up (only the circuitry pertaining to the delayed start up is shown).
As the input voltage rises, the charging of capacitor C1 pulls the ON/OFF pin high, keeping the regulator off.
Once the input voltage reaches its final value and the capacitor stops charging, the resistor R2 pulls the ON/OFF
pin low, thus allowing the circuit to start switching. Resistor R1 is included to limit the maximum voltage applied to
the ON/OFF pin (maximum of 25 V), reduces power supply noise sensitivity, and also limits the capacitor, C1,
discharge current. When high input ripple voltage exists, avoid long delay time, because this ripple can be
coupled into the ON/OFF pin and cause problems.
This delayed start-up feature is useful in situations where the input power source is limited in the amount of
current it can deliver. It allows the input voltage to rise to a higher voltage before the regulator starts operating.
Buck regulators require less input current at higher input voltages.
10
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Feature Description (continued)
Figure 14. Delayed Start-Up
8.3.2 Undervoltage Lockout
Some applications require the regulator to remain off until the input voltage reaches a predetermined voltage.
Figure 15 shows an undervoltage lockout feature applied to a buck regulator, while Figure 16 and Figure 17
apply the same feature to an inverting circuit. The circuit in Figure 16 features a constant threshold voltage for
turnon and turnoff (Zener voltage plus approximately one volt). If hysteresis is required, the circuit in Figure 17
has a turnon voltage which is different than the turnoff voltage. The amount of hysteresis is approximately equal
to the value of the output voltage. If Zener voltages greater than 25 V are used, an additional 47-kΩ resistor is
required from the ON/OFF pin to the ground pin to stay within the 25-V maximum limit of the ON/OFF pin.
Figure 15. Undervoltage Lockout for Buck Regulator
8.3.3 Inverting Regulator
The circuit in Figure 18 converts a positive input voltage to a negative output voltage with a common ground. The
circuit operates by bootstrapping the regulator's ground pin to the negative output voltage, then grounding the
feedback pin, the regulator senses the inverted output voltage and regulates it.
This circuit has an ON/OFF threshold of approximately 13 V.
Figure 16. Undervoltage Lockout for Inverting Regulator
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Feature Description (continued)
This example uses the LM2595 5-V version to generate a −5-V output, but other output voltages are possible by
selecting other output voltage versions, including the adjustable version.
Because this regulator topology can produce an output voltage that is either greater than or less than the input
voltage, the maximum output current greatly depends on both the input and output voltage. Figure 19 provides a
guide as to the amount of output load current possible for the different input and output voltage conditions.
The maximum voltage appearing across the regulator is the absolute sum of the input and output voltage, and
this must be limited to a maximum of 40 V. For example, when converting 20 V to −12 V, the regulator would see
32 V between the input pin and ground pin. The LM2595 has a maximum input voltage spec of 40 V.
Additional diodes are required in this regulator configuration. Diode D1 is used to isolate input voltage ripple or
noise from coupling through the CIN capacitor to the output, under light or no load conditions. Also, this diode
isolation changes the topology to closely resemble a buck configuration thus providing good closed loop stability.
TI recommends a Schottky diode for low input voltages (because of its lower voltage drop), but for higher input
voltages, a fast recovery diode could be used.
Without diode D3, when the input voltage is first applied, the charging current of CIN can pull the output positive
by several volts for a short period of time. Adding D3 prevents the output from going positive by more than a
diode voltage.
This circuit has hysteresis.
Regulator starts switching at VIN = 13 V
Regulator stops switching at VIN = 8 V
Figure 17. Undervoltage Lockout With Hysteresis For Inverting Regulator
CIN – 220-μF, 25-V tantalum Sprague 595D
120-μF, 50-V electrolytic Panasonic HFQ
COUT – 22-μF, 20-V tantalum Sprague 595D
120-μF, 25-V electrolytic Panasonic HFQ
Figure 18. Inverting −5-V Regulator With Delayed Start-Up
12
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Feature Description (continued)
Figure 19. Inverting Regulator Typical Load Current
Because of differences in the operation of the inverting regulator, the standard design procedure is not used to
select the inductor value. In the majority of designs, a 68-μH, 1.5-A inductor is the best choice. Capacitor
selection is narrowed down to just a few values. Using the values shown in Figure 18 will provide good results in
the majority of inverting designs.
This type of inverting regulator can require relatively large amounts of input current when starting up, even with
light loads. Input currents as high as the LM2595 current limit (approximately 1.5 A) are required for at least 2 ms
or more, until the output reaches its nominal output voltage. The actual time depends on the output voltage and
the size of the output capacitor. Input power sources that are current limited or sources that can not deliver these
currents without getting loaded down, may not work correctly. Because of the relatively high start-up currents
required by the inverting topology, the delayed start-up feature (C1, R1 and R2) shown in Figure 18 is
recommended. By delaying the regulator start-up, the input capacitor is allowed to charge up to a higher voltage
before the switcher begins operating. A portion of the high input current required for start-up is now supplied by
the input capacitor (CIN). For severe start up conditions, the input capacitor can be made much larger than
normal.
8.3.4 Inverting Regulator Shutdown Methods
Using the ON/OFF pin in a standard buck configuration is simple. To turn the regulator ON, pull the ON/OFF pin
below 1.3 V (at 25°C referenced to ground). To shut the regulator OFF, pull the ON/OFF pin above 1.3 V. With
the inverting configuration, some level shifting is required, because the ground pin of the regulator is no longer at
ground, but is now setting at the negative output voltage level. Two different shutdown methods for inverting
regulators are shown in Figure 20 and Figure 21.
Figure 20. Inverting Regulator Ground Referenced Shutdown
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Feature Description (continued)
Figure 21. Inverting Regulator Ground Referenced Shutdown Using Opto Device
8.4 Device Functional Modes
8.4.1 Discontinuous Mode Operation
The selection guide chooses inductor values suitable for continuous mode operation, but for low current
applications or high input voltages, a discontinuous mode design may be a better choice. Discontinuous mode
would use an inductor that would be physically smaller, and would need only one half to one third the inductance
value required for a continuous mode design. The peak switch and inductor currents will be higher in a
discontinuous design, but at these low load currents (400 mA and below), the maximum switch current will still be
less than the switch current limit.
Discontinuous operation can have voltage waveforms that are considerably different than a continuous design.
The output pin (switch) waveform can have some damped sinusoidal ringing present (see Typical
Characteristics). This ringing is normal for discontinuous operation, and is not caused by feedback loop
instabilities. In discontinuous operation, there is a period of time where neither the switch nor the diode are
conducting, and the inductor current has dropped to zero. During this time, a small amount of energy can
circulate between the inductor and the switch/diode parasitic capacitance causing this characteristic ringing.
Normally this ringing is not a problem, unless the amplitude becomes great enough to exceed the input voltage,
and even then, there is very little energy present to cause damage.
Different inductor types and/or core materials produce different amounts of this characteristic ringing. Ferrite core
inductors have very little core loss and therefore produce the most ringing. The higher core loss of powdered iron
inductors produce less ringing. If desired, a series RC could be placed in parallel with the inductor to dampen the
ringing.
Before
Ripple
Filter
5 mV/div
Alter
Ripple
Filter
2 µsec/div
Figure 22. Post Ripple Filter Waveform
14
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9 Application and Implementation
NOTE
Information in the following applications sections is not part of the TI component
specification, and TI does not warrant its accuracy or completeness. TI’s customers are
responsible for determining suitability of components for their purposes. Customers should
validate and test their design implementation to confirm system functionality.
9.1 Application Information
9.1.1 Input Capacitor (CIN)
A low ESR aluminum or tantalum bypass capacitor is required between the input pin and ground pin. The
capacitor must be placed near the regulator using short leads. This capacitor prevents large voltage transients
from appearing at the input, and provides the instantaneous current required each time the switch turns on.
The important parameters for the Input capacitor are the voltage rating and the RMS current rating. Because of
the relatively high RMS currents flowing in a buck regulator's input capacitor, this capacitor must be chosen for
its RMS current rating rather than its capacitance or voltage ratings, although the capacitance value and voltage
rating are directly related to the RMS current rating.
The RMS current rating of a capacitor could be viewed as a capacitor's power rating. The RMS current flowing
through the capacitors internal ESR produces power which causes the internal temperature of the capacitor to
rise. The RMS current rating of a capacitor is determined by the amount of current required to raise the internal
temperature approximately 10°C above an ambient temperature of 105°C. The ability of the capacitor to dissipate
this heat to the surrounding air will determine the amount of current the capacitor can safely sustain. Capacitors
that are physically large and have a large surface area will typically have higher RMS current ratings. For a given
capacitor value, a higher voltage electrolytic capacitor will be physically larger than a lower voltage capacitor, and
thus be able to dissipate more heat to the surrounding air, and therefore will have a higher RMS current rating.
The consequences of operating an electrolytic capacitor above the RMS current rating is a shortened operating
life. The higher temperature speeds up the evaporation of the capacitor's electrolyte, resulting in eventual failure.
Selecting an input capacitor requires consulting the manufacturer's data sheet for maximum allowable RMS
ripple current. For a maximum ambient temperature of 40°C, a general guideline would be to select a capacitor
with a ripple current rating of approximately 50% of the DC load current. For ambient temperatures up to 70°C, a
current rating of 75% of the DC load current would be a good choice for a conservative design. The capacitor
voltage rating must be at least 1.25 times greater than the maximum input voltage, and often a much higher
voltage capacitor is required to satisfy the RMS current requirements.
Figure 23 shows the relationship between an electrolytic capacitor value, its voltage rating, and the RMS current
it is rated for. These curves were obtained from the Nichicon PL series of low-ESR, high-reliability electrolytic
capacitors designed for switching regulator applications. Other capacitor manufacturers offer similar types of
capacitors, but always check the capacitor data sheet.
Standard electrolytic capacitors typically have much higher ESR numbers, lower RMS current ratings and
typically have a shorter operating lifetime.
Because of their small size and excellent performance, surface-mount solid tantalum capacitors are often used
for input bypassing, but several precautions must be observed. A small percentage of solid tantalum capacitors
can short if the inrush current rating is exceeded. This can happen at turnon when the input voltage is suddenly
applied, and of course, higher input voltages produce higher inrush currents. Several capacitor manufacturers do
a 100% surge current testing on their products to minimize this potential problem. If high turn on currents are
expected, it may be necessary to limit this current by adding either some resistance or inductance before the
tantalum capacitor, or select a higher voltage capacitor. As with aluminum electrolytic capacitors, the RMS ripple
current rating must be sized to the load current.
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Application Information (continued)
9.1.2 Feedforward Capacitor (CFF) for Adjustable Output Voltage Version Only
A feedforward capacitor, CFF, shown across R2 in Table 1 is used when the output voltage is greater than 10 V
or when COUT has a very low ESR. This capacitor adds lead compensation to the feedback loop and increases
the phase margin for better loop stability.
Figure 23. RMS Current Ratings for Low ESR Electrolytic Capacitors (Typical)
9.1.3 Output Capacitor (COUT)
An output capacitor is required to filter the output and provide regulator loop stability. Low impedance or low ESR
Electrolytic or solid tantalum capacitors designed for switching regulator applications must be used. When
selecting an output capacitor, the important capacitor parameters are the 100-kHz Equivalent Series Resistance
(ESR), the RMS ripple current rating, voltage rating, and capacitance value. For the output capacitor, the ESR
value is the most important parameter.
The output capacitor requires an ESR value that has an upper and lower limit. For low output ripple voltage, a
low ESR value is required. This value is determined by the maximum allowable output ripple voltage, typically 1%
to 2% of the output voltage. But if the selected capacitor's ESR is extremely low, there is a possibility of an
unstable feedback loop, resulting in an oscillation at the output. Using the capacitors listed in the tables, or
similar types, will provide design solutions under all conditions.
If very low output ripple voltage (less than 15 mV) is required, see Output Voltage Ripple and Transients for a
post ripple filter.
An aluminum electrolytic capacitor's ESR value is related to the capacitance value and its voltage rating. In most
cases, higher voltage electrolytic capacitors have lower ESR values (see Figure 24). Often, capacitors with much
higher voltage ratings may be required to provide the low ESR values required for low output ripple voltage.
The output capacitor for many different switcher designs often can be satisfied with only three or four different
capacitor values and several different voltage ratings. See Table 5 and Table 7 for typical capacitor values,
voltage ratings, and manufacturer's capacitor types.
Electrolytic capacitors are not recommended for temperatures below −25°C. The ESR rises dramatically at cold
temperatures and typically rises 3X at −25°C and as much as 10X at −40°C (see Figure 25).
Solid tantalum capacitors have a much better ESR specifications for cold temperatures and are recommended
for temperatures below −25°C.
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Application Information (continued)
Figure 24. Capacitor ESR vs Capacitor Voltage Rating (Typical Low ESR Electrolytic Capacitor)
Table 1. Output Capacitor and Feedforward Capacitor Selection Table
THROUGH-HOLE OUTPUT CAPACITOR
SURFACE-MOUNT OUTPUT CAPACITOR
OUTPUT
VOLTAGE
(V)
PANASONIC HFQ
SERIES (µF/V)
NICHICON PL
SERIES (µF/V)
FEEDFORWARD
CAPACITOR
AVX TPS
SERIES (µF/V)
SPRAGUE 595D
SERIES (µF/V)
FEEDFORWARD
CAPACITOR
9
180/25
180/25
1.5 nF
100/16
180/16
1.5 nF
12
120/25
120/25
1.5 nF
68/20
120/20
1.5 nF
15
120/25
120/25
1.5 nF
68/20
100/20
1.5 nF
24
82/35
82/35
1 nF
33/25
33/35
220 pF
28
82/50
82/50
1 nF
10/35
33/35
220 pF
9.1.4 Catch Diode
Buck regulators require a diode to provide a return path for the inductor current when the switch turns off. This
must be a fast diode and must be placed close to the LM2595 using short leads and short printed circuit traces.
Because of their very fast switching speed and low forward voltage drop, Schottky diodes provide the best
performance, especially in low output voltage applications (5 V and lower). Ultra-fast recovery, or high-efficiency
rectifiers are also a good choice, but some types with an abrupt turnoff characteristic may cause instability or
EMI problems. Ultra-fast recovery diodes typically have reverse recovery times of 50 ns or less. Rectifiers such
as the 1N5400 series are much too slow and must not be used.
Figure 25. Capacitor ESR Change vs Temperature
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Table 2. Diode Selection Table
1-A DIODES
VR
SURFACE MOUNT
SCHOTTKY
ULTRA FAST
RECOVERY
SK12
20 V
SK13
30 V
MBRS130
SK14
40 V
3-A DIODES
THROUGH HOLE
SCHOTTKY
ULTRA FAST
RECOVERY
SURFACE MOUNT
SCHOTTKY
ULTRA FAST
RECOVERY
1N5817
All of
these
diodes
are
rated to
at least
50 V
SR102
1N5818
SR103
11DQ03
THROUGH HOLE
SCHOTTKY
ULTRA FAST
RECOVERY
1N5820
All of
these
diodes
are
rated to
at least
50 V
SK32
SK33
All of
these
diodes
are
rated to
at least
50 V
SR302
MBR320
1N5821
MBR330
31DQ03
1N5822
MBRS140
1N5819
SK34
SR304
10BQ040
SR104
MBRS340
MBR340
MUR120
All of
these
diodes
are
rated to
at least
50 V
10MQ040
MURS120
11DQ04
30WQ04
MURS320
31DQ04
MUR320
50 V
MBRS160
10BF10
SR105
SK35
30WF10
SR305
30WF10
or
10BQ050
MBR150
MBR360
MBR350
More
10MQ060
11DQ05
30WQ05
31DQ05
9.1.5 Inductor Selection
All switching regulators have two basic modes of operation: continuous and discontinuous. The difference
between the two types relates to the inductor current, whether it is flowing continuously, or if it drops to zero for a
period of time in the normal switching cycle. Each mode has distinctively different operating characteristics,
which can affect the regulators performance and requirements. Most switcher designs will operate in the
discontinuous mode when the load current is low.
The LM2595 (or any of the Simple Switcher family) can be used for both continuous or discontinuous modes of
operation.
In many cases the preferred mode of operation is the continuous mode. This mode offers greater output power,
lower peak switch, inductor and diode currents, and can have lower output ripple voltage. However, the
continuous mode requires larger inductor values to keep the inductor current flowing continuously, especially at
low output load currents and/or high input voltages.
To simplify the inductor selection process, an inductor selection guide (nomograph) was designed (see Figure 27
through Figure 30). This guide assumes that the regulator is operating in the continuous mode, and selects an
inductor that will allow a peak-to-peak inductor ripple current to be a certain percentage of the maximum design
load current. This peak-to-peak inductor ripple current percentage is not fixed, but is allowed to change as
different design load currents are selected. (See Figure 26.)
Figure 26. ΔIIND, Peak-to-Peak Inductor Ripple Current
(as a Percentage of the Load Current) vs Load Current
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By allowing the percentage of inductor ripple current to increase for low load currents, the inductor value and size
can be kept relatively low.
When operating in the continuous mode, the inductor current waveform ranges from a triangular to a sawtooth
type of waveform (depending on the input voltage), with the average value of this current waveform equal to the
DC output load current.
Inductors are available in different styles such as pot core, toroid, E-core, bobbin core, and so forth, as well as
different core materials, such as ferrites and powdered iron. The least expensive, the bobbin, rod or stick core,
consists of wire wound on a ferrite bobbin. This type of construction makes for an inexpensive inductor; however,
because the magnetic flux is not completely contained within the core, it generates more Electro-Magnetic
Interference (EMl). This magnetic flux can induce voltages into nearby printed circuit traces, thus causing
problems with both the switching regulator operation and nearby sensitive circuitry, and can give incorrect scope
readings because of induced voltages in the scope probe (see Open Core Inductors).
When multiple switching regulators are placed on the same PCB, open core magnetics can cause interference
between two or more of the regulator circuits, especially at high currents. A toroid or E-core inductor (closed
magnetic structure) must be used in these situations.
The inductors listed in the selection chart include ferrite E-core construction for Schott, ferrite bobbin core for
Renco and Coilcraft, and powdered iron toroid for Pulse Engineering.
Exceeding an inductor's maximum current rating may cause the inductor to overheat because of the copper wire
losses, or the core may saturate. If the inductor begins to saturate, the inductance decreases rapidly and the
inductor begins to look mainly resistive (the DC resistance of the winding). This can cause the switch current to
rise very rapidly and force the switch into a cycle-by-cycle current limit, thus reducing the DC output load current.
This can also result in overheating of the inductor and/or the LM2595. Different inductor types have different
saturation characteristics, and this must be kept in mind when selecting an inductor.
The inductor manufacturer's data sheets include current and energy limits to avoid inductor saturation.
For continuous mode operation, see the inductor selection graphs in Figure 27 through Figure 30
Figure 27. LM2595 3.3-V
Figure 28. LM2595 5-V
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Figure 30. LM2595 Adjustable Voltage
Figure 29. LM2595 12-V
Table 3. Inductor Manufacturer's Part Numbers
RENCO
PULSE ENGINEERING
COILCRAFT
INDUCTANCE
(μH)
CURRENT
(A)
L4
68
0.32
RL-1284-68-43
RL1500-68
PE-53804
PE-53804-S
DO1608-68
L5
47
0.37
RL-1284-47-43
RL1500-47
PE-53805
PE-53805-S
DO1608-473
L6
33
0.44
RL-1284-33-43
RL1500-33
PE-53806
PE-53806-S
DO1608-333
L9
220
0.32
RL-5470-3
RL1500-220
PE-53809
PE-53809-S
DO3308-224
L10
150
0.39
RL-5470-4
RL1500-150
PE-53810
PE-53810-S
DO3308-154
L11
100
0.48
RL-5470-5
RL1500-100
PE-53811
PE-53811-S
DO3308-104
L12
68
0.58
RL-5470-6
RL1500-68
PE-53812
PE-53812-S
DO3308-683
L13
47
0.70
RL-5470-7
RL1500-47
PE-53813
PE-53813-S
DO3308-473
L14
33
0.83
RL-1284-33-43
RL1500-33
PE-53814
PE-53814-S
DO3308-333
L15
22
0.99
RL-1284-22-43
RL1500-22
PE-53815
PE-53815-S
DO3308-223
L16
15
1.24
RL-1284-15-43
RL1500-15
PE-53816
PE-53816-S
DO3308-153
L17
330
0.42
RL-5471-1
RL1500-330
PE-53817
PE-53817-S
DO3316-334
L18
220
0.55
RL-5471-2
RL1500-220
PE-53818
PE-53818-S
DO3316-224
L19
150
0.66
RL-5471-3
RL1500-150
PE-53819
PE-53819-S
DO3316-154
L20
100
0.82
RL-5471-4
RL1500-100
PE-53820
PE-53820-S
DO3316-104
L21
68
0.99
RL-5471-5
RL1500-68
PE-53821
PE-53821-S
DO3316-683
L22
47
1.17
RL-5471-6
—
PE-53822
PE-53822-S
DO3316-473
L23
33
1.40
RL-5471-7
—
PE-53823
PE-53823-S
DO3316-333
L24
22
1.70
RL-1283-22-43
—
PE-53824
PE-53824-S
DO3316-223
L26
330
0.80
RL-5471-1
—
PE-53826
PE-53826-S
DO5022P-334
L27
220
1.00
RL-5471-2
—
PE-53827
PE-53827-S
DO5022P-224
L28
150
1.20
RL-5471-3
—
PE-53828
PE-53828-S
DO5022P-154
L29
100
1.47
RL-5471-4
—
PE-53829
PE-53829-S
DO5022P-104
L30
68
1.78
RL-5471-5
—
PE-53830
PE-53830-S
DO5022P-683
L35
47
2.15
RL-5473-1
—
PE-53935
PE-53935-S
THROUGH HOLE
SURFACE
MOUNT
THROUGH
HOLE
SURFACE
MOUNT
SURFACE
MOUNT
—
9.1.6 Output Voltage Ripple and Transients
The output voltage of a switching power supply operating in the continuous mode will contain a sawtooth ripple
voltage at the switcher frequency, and may also contain short voltage spikes at the peaks of the sawtooth
waveform.
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The output ripple voltage is a function of the inductor sawtooth ripple current and the ESR of the output
capacitor. A typical output ripple voltage can range from approximately 0.5% to 3% of the output voltage. To
obtain low ripple voltage, the ESR of the output capacitor must be low; however, caution must be exercised when
using extremely low ESR capacitors because they can affect the loop stability, resulting in oscillation problems. If
very low output ripple voltage is required (less than 20 mV), TI recommends a post ripple filter (see Figure 32).
The inductance required is typically between 1 μH and 5 μH, with low DC resistance, to maintain good load
regulation. A low ESR output filter capacitor is also required to assure good dynamic load response and ripple
reduction. The ESR of this capacitor may be as low as desired, because it is out of the regulator feedback loop.
Figure 22 shows a typical output ripple voltage, with and without a post ripple filter.
When observing output ripple with a scope, it is essential that a short, low inductance scope probe ground
connection be used. Most scope probe manufacturers provide a special probe terminator which is soldered onto
the regulator board, preferably at the output capacitor. This provides a very short scope ground, thus eliminating
the problems associated with the 3 inch ground lead normally provided with the probe, and provides a much
cleaner and more accurate picture of the ripple voltage waveform.
The voltage spikes are caused by the fast switching action of the output switch and the diode, the parasitic
inductance of the output filter capacitor, and its associated wiring. To minimize these voltage spikes, the output
capacitor must be designed for switching regulator applications, and the lead lengths must be kept very short.
Wiring inductance, stray capacitance, as well as the scope probe used to evaluate these transients, all contribute
to the amplitude of these spikes.
When a switching regulator is operating in the continuous mode, the inductor current waveform ranges from a
triangular to a sawtooth type of waveform (depending on the input voltage). For a given input and output voltage,
the peak-to-peak amplitude of this inductor current waveform remains constant. As the load current increases or
decreases, the entire sawtooth current waveform also rises and falls. The average value (or the center) of this
current waveform is equal to the DC load current.
If the load current drops to a low enough level, the bottom of the sawtooth current waveform will reach zero, and
the switcher will smoothly change from a continuous to a discontinuous mode of operation. Most switcher
designs (regardless how large the inductor value is) will be forced to run discontinuous if the output is lightly
loaded. This is a perfectly acceptable mode of operation.
Figure 31. Peak-to-Peak Inductor
Ripple Current vs Load Current
In a switching regulator design, knowing the value of the peak-to-peak inductor ripple current (ΔIIND) can be
useful for determining a number of other circuit parameters. Parameters such as, peak inductor or peak switch
current, minimum load current before the circuit becomes discontinuous, output ripple voltage and output
capacitor ESR can all be calculated from the peak-to-peak ΔIIND. When the inductor nomographs shown in
Figure 27 through Figure 30 are used to select an inductor value, the peak-to-peak inductor ripple current can
immediately be determined. Figure 31 shows the range of (ΔIIND) that can be expected for different load currents.
Figure 31 also shows how the peak-to-peak inductor ripple current (ΔIIND) changes from the lower border to the
upper border (for a given load current) within an inductance region. The upper border represents a higher input
voltage, while the lower border represents a lower input voltage (see Inductor Selection).
These curves are only correct for continuous mode operation, and only if the inductor selection guides are used
to select the inductor value
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Consider the following example:
VOUT = 5 V, maximum load current of 800 mA
VIN = 12 V (nominal) varying between 10 V and 14 V
The selection guide in Figure 28 shows that the vertical line for a 0.8-A load current and the horizontal line for the
12-V input voltage intersect approximately midway between the upper and lower borders of the 68-μH inductance
region. A 68-μH inductor allows a peak-to-peak inductor current (ΔIIND) to flow as a percentage of the maximum
load current. Referring to Figure 31, follow the 0.8-A line approximately midway into the inductance region, and
read the peak-to-peak inductor ripple current (ΔIIND) on the left hand axis (approximately 300 mAp-p).
As the input voltage increases to 14 V, it approaches the upper border of the inductance region, and the inductor
ripple current increases. Figure 31 shows that for a load current of 0.8 A, the peak-to-peak inductor ripple current
(ΔIIND) is 300 mA with 12-V in, and can range from 340 mA at the upper border (14-V in) to 225 mA at the lower
border (10-V in).
Once the ΔIIND value is known, the following formulas can be used to calculate additional information about the
switching regulator circuit.
1. Peak Inductor or peak switch current
2. Minimum load current before the circuit becomes discontinuous
3. Output Ripple Voltage = (ΔIIND) × (ESR of COUT)
= 0.30 A × 0.16 Ω = 48 mVp-p
4. ESR of COUT
9.1.7 Open Core Inductors
Another possible source of increased output ripple voltage or unstable operation is from an open core inductor.
Ferrite bobbin or stick inductors have magnetic lines of flux flowing through the air from one end of the bobbin to
the other end. These magnetic lines of flux will induce a voltage into any wire or PCB copper trace that comes
within the inductor's magnetic field. The strength of the magnetic field, the orientation and location of the PC
copper trace to the magnetic field, and the distance between the copper trace and the inductor determine the
amount of voltage generated in the copper trace. Another way of looking at this inductive coupling is to consider
the PCB copper trace as one turn of a transformer (secondary) with the inductor winding as the primary. Many
millivolts can be generated in a copper trace placed near an open core inductor, which can cause stability
problems or high output ripple voltage problems.
If unstable operation is seen, and an open core inductor is used, it is possible that the location of the inductor
with respect to other PC traces may be the problem. To determine if this is the problem, temporarily raise the
inductor away from the board by several inches and then check circuit operation. If the circuit now operates
correctly, then the magnetic flux from the open core inductor is causing the problem. Substituting a closed core
inductor such as a torroid or E-core will correct the problem, or re-arranging the PC layout may be necessary.
Magnetic flux cutting the IC device ground trace, feedback trace, or the positive or negative traces of the output
capacitor must be minimized.
Sometimes, placing a trace directly beneath a bobbin inductor will provide good results, provided it is exactly in
the center of the inductor (because the induced voltages cancel themselves out). However, if the trace is off
center, then problems could arise. If flux problems are present, even the direction of the inductor winding can
make a difference in some circuits.
This discussion on open core inductors is not to frighten users, but to alert them on what kind of problems to
watch out for. Open core bobbin or stick inductors are an inexpensive, simple way of making a compact, efficient
inductor, and they are used by the millions in many different applications.
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9.2 Typical Applications
9.2.1 Series Buck Regulator (Fixed Output)
CIN – 120-μF, 50-V, aluminum electrolytic Nichicon, PL Series
COUT – 120-μF, 25-V aluminum electrolytic Nichicon, PL Series
D1 – 3-A, 40-V Schottky rectifier, 1N5822
L1 – 100-μH, L29
Figure 32. Fixed Output Voltage Versions
9.2.1.1 Design Requirements
Table 4 lists the parameters for this design example.
Table 4. Example Parameters
PARAMETER
EXAMPLE VALUE
Regulated output voltage (3.3 V, 5 V or 12 V), VOUT
5V
Maximum DC input voltage, VIN(max)
12 V
Maximum load current, ILOAD(max)
1A
9.2.1.2 Detailed Design Procedure
9.2.1.2.1 Inductor Selection (L1)
1. Select the correct inductor value selection guide from Figure 27, Figure 28, or Figure 29 (output voltages of
3.3 V, 5 V, or 12 V respectively).
Use the inductor selection guide for the 5-V version shown in Figure 28.
2. From the inductor value selection guide, identify the inductance region intersected by the maximum input
voltage line and the maximum load current line. Each region is identified by an inductance value and an
inductor code (LXX).
From the inductor value selection guide shown in Figure 28, the inductance region intersected by the 12-V
horizontal line and the 1-A vertical line is 68 μH, and the inductor code is L30.
3. Select an appropriate inductor from the manufacturer's part numbers listed in Table 3.
The inductance value required is 68 μH. See row L30 of Table 3 and choose an inductor part number from
any of the manufactures (in most instance, both through-hole and surface-mount inductors are available).
9.2.1.2.2 Output Capacitor Selection (COUT)
1. In the majority of applications, low ESR (Equivalent Series Resistance) electrolytic capacitors between 47 μF
and 330 μF and low ESR solid tantalum capacitors between 56 μF and 270 μF provide the best results. This
capacitor must be placed close to the IC using short capacitor leads and short copper traces. Do not use
capacitors larger than 330 μF.
2. To simplify the capacitor selection procedure, see Table 5 for quick design component selection. This table
contains different input voltages, output voltages, and load currents, and lists various inductors and output
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capacitors that will provide the best design solutions.
From Table 5, place the 5-V output voltage section. In the load current column, choose the load current line
that is closest to the current required in the application; for this example, use the 1-A line. In the maximum
input voltage column, select the line that covers the input voltage required in the application; in this example,
use the 15-V line. The rest of this line shows the recommended inductors and capacitors that will provide the
best overall performance.
The capacitor list contains both through-hole electrolytic and surface-mount tantalum capacitors from four
different capacitor manufacturers. TI recommends using both the manufacturers and the manufacturer's
series listed in Table 5.
In this example, aluminum electrolytic capacitors from several different manufacturers are available with the
range of ESR numbers required:
– 220-μF, 25-V Panasonic HFQ Series
– 220-μF, 25-V Nichicon PL Series
3. The capacitor voltage rating for electrolytic capacitors must be at least 1.5 times greater than the output
voltage, and often much higher voltage ratings are required to satisfy the low ESR requirements for low
output ripple voltage.
For a 5-V output, a capacitor voltage rating at least 7.5 V or more is required. But, in this example, even a
low ESR, switching grade, 220-μF, 10-V aluminum electrolytic capacitor would exhibit approximately 225 mΩ
of ESR (see Figure 24 for the ESR versus voltage rating). This amount of ESR would result in relatively high
output ripple voltage. To reduce the ripple to 1% of the output voltage, or less, a capacitor with a higher
voltage rating (lower ESR) must be selected. A 16-V or 25-V capacitor will reduce the ripple voltage by
approximately half.
9.2.1.2.3 Catch Diode Selection (D1)
1. The catch diode current rating must be at least 1.3 times greater than the maximum load current. Also, if the
power supply design must withstand a continuous output short, the diode must have a current rating equal to
the maximum current limit of the LM2595. The most stressful condition for this diode is an overload or
shorted output condition.
See Table 2. In this example, a 3-A, 20-V, 1N5820 Schottky diode will provide the best performance, and will
not be overstressed even for a shorted output.
2. The reverse voltage rating of the diode must be at least 1.25 times the maximum input voltage.
3. This diode must be fast (short reverse recovery time) and must be placed close to the LM2595 using short
leads and short printed circuit traces. Because of their fast switching speed and low forward voltage drop,
Schottky diodes provide the best performance and efficiency, and must be the first choice, especially in low
output voltage applications. Ultra-fast recovery, or high-efficiency rectifiers also provide good results. Ultrafast recovery diodes typically have reverse recovery times of 50 ns or less. Rectifiers such as the 1N5400
series must not be used because they are too slow.
9.2.1.2.4 Input Capacitor (CIN)
A low ESR aluminum or tantalum bypass capacitor is required between the input pin and ground pin to prevent
large voltage transients from appearing at the input. This capacitor must be placed close to the IC using short
leads. In addition, the RMS current rating of the input capacitor must be selected to be at least ½ the DC load
current. The capacitor manufacturer's data sheet must be checked to assure that this current rating is not
exceeded. Figure 23 shows typical RMS current ratings for several different aluminum electrolytic capacitor
values.
The important parameters for the input capacitor are the input voltage rating and the RMS current rating. With a
nominal input voltage of 12 V, an aluminum electrolytic capacitor with a voltage rating greater than 18 V
(1.5 × VIN) is necessary. The next higher capacitor voltage rating is 25 V.
For an aluminum electrolytic, the capacitor voltage rating must be approximately 1.5 times the maximum input
voltage. Exercise caution if solid tantalum capacitors are used (see Input Capacitor (CIN) on input capacitor). The
tantalum capacitor voltage rating must be 2 times the maximum input voltage and TI recommends that they be
surge current tested by the manufacturer.
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The RMS current rating requirement for the input capacitor in a buck regulator is approximately ½ the DC load
current. In this example, with a 1-A load, a capacitor with a RMS current rating of at least 500 mA is required.
Figure 23 can be used to select an appropriate input capacitor. From the curves, place the 25-V line and note
which capacitor values have RMS current ratings greater than 500 mA. Either a 180-μF or 220-μF, 25-V
capacitor could be used.
Use caution when using ceramic capacitors for input bypassing, because it may cause severe ringing at the VIN
pin.
For a through-hole design, a 220-μF, 25-V electrolytic capacitor (Panasonic HFQ series or Nichicon PL series or
equivalent) would be adequate. Other types or other manufacturers' capacitors can be used provided the RMS
ripple current ratings are adequate.
For surface-mount designs, solid tantalum capacitors can be used, but exercise caution with regard to the
capacitor surge current rating (see Input Capacitor (CIN) on input capacitors). The TPS series available from
AVX, and the 593D series from Sprague are both surge current tested.
Table 5. LM2595 Fixed Voltage Quick Design Component Selection Table
OUTPUT CAPACITOR
CONDITIONS
OUTPUT
VOLTAGE
(V)
LOAD
CURREN
T (A)
1
3.3
0.5
1
5
0.5
1
12
0.5
INDUCTOR
MAX INPUT
VOLTAGE
(V)
THROUGH-HOLE
ELECTROLYTIC
INDUCTANCE INDUCTOR
(μH)
(#)
SURFACE-MOUNT TANTALUM
PANASONIC
HFQ SERIES
(μF/V)
NICHICON PL
SERIES
(μF/V)
AVX TPS
SERIES
(μF/V)
SPRAGUE
595D SERIES
(μF/V)
5
22
L24
330/16
330/16
220/10
330/10
7
33
L23
270/25
270/25
220/10
270/10
10
47
L31
220/25
220/35
220/10
220/10
40
68
L30
180/35
220/35
220/10
180/10
6
47
L13
220/25
220/16
220/10
220/10
10
68
L21
150/35
150/25
100/16
150/16
40
100
L20
150/35
82/35
100/16
100/20
8
33
L28
330/16
330/16
220/10
270/10
10
47
L31
220/25
220/25
220/10
220/10
15
68
L30
180/35
180/35
220/10
150/16
40
100
L29
180/35
120/35
100/16
120/16
9
68
L21
180/16
180/16
220/10
150/16
20
150
L19
120/25
1200/25
100/16
100/20
40
150
L19
100/25
100/25
68/20
68/25
15
47
L31
220/25
220/25
68/20
120/20
18
68
L30
180/35
120/25
68/20
120/20
30
150
L36
82/25
82/25
68/20
100/20
40
220
L35
82/25
82/25
68/20
68/25
15
68
L21
180/25
180/25
68/20
120/20
20
150
L19
82/25
82/25
68/20
100/20
40
330
L26
56/25
56/25
68/20
68/25
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9.2.1.3 Application Curves
A
20V
10V
0V
B
1A
0.5A
0A
C
50 mV
AC/
div.
VIN = 20 V, VOUT = 5 V, ILOAD = 1 A
L = 68 μH, COUT = 120 μF, COUT ESR = 100 mΩ
A: Output pin voltage, 10 V/div.
B: Inductor current, 0.5 A/div.
C: Output ripple voltage, 50 mV/div.
Horizontal time base: 2 µs/div.
Figure 33. Continuous Mode Switching Waveforms
VIN = 20 V, VOUT = 5 V, ILOAD = 250 mA to 750 mA
L = 68 μH, COUT = 120 μF, COUT ESR = 100 mΩ
A: Output voltage, 100 mV/div. (AC)
B: 250-mA to 750-mA load pulse
Horizontal time base: 100 µs/div.
Figure 34. Load Transient Response for Continuous Mode
9.2.2 Series Buck Regulator (Adjustable Output)
CIN – 120-μF, 50-V aluminum electrolytic Nichicon, PL Series
COUT – 120-μF, 25-V aluminum electrolytic Nichicon, PL Series
D1 – 3-A, 40-V Schottky rectifier, 1N5822
L1 – 100-μH, L29
R1 – 1-kΩ, 1%
CFF – See Feedforward Capacitor (CFF)
Figure 35. Adjustable Output Voltage Versions
9.2.2.1 Design Requirements
Table 6 lists the parameters for this design example.
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Table 6. Example Parameters
PARAMETER
EXAMPLE VALUE
Regulated output voltage, VOUT
20 V
Maximum input voltage, VIN(max)
28 V
Maximum load current, ILOAD(max)
1A
Switching frequency, F
Fixed at a nominal 150 kHz
9.2.2.2 Detailed Design Procedure
9.2.2.2.1 Programming Output Voltage
Select the R1 and R2.
Use Equation 1 to select the appropriate resistor values.
(1)
Select a value for R1 between 240 Ω and 1.5 kΩ in Equation 2. The lower resistor values minimize noise pickup
in the sensitive feedback pin (for the lowest temperature coefficient and the best stability with time, use 1% metal
film resistors).
(2)
Select R1 to be 1 kΩ, 1%. Solve for R2 in Equation 3.
(3)
R2 = 1k (16.26 − 1) = 15.26k, closest 1% value is 15.4 kΩ.
R2 = 15.4 kΩ.
9.2.2.2.2 Inductor Selection (L1)
1. Calculate the inductor Volt • microsecond constant E • T (V • μs) with Equation 4.
where
•
•
VSAT = internal switch saturation voltage = 1 V
and VD = diode forward voltage drop = 0.5 V
(4)
Calculate the inductor Volt • microsecond constant (E • T) with Equation 5.
(5)
2. Use the E • T value from the previous formula and match it with the E • T number on the vertical axis of the
Inductor Value Selection Guide shown in Figure 30.
E • T = 34.8 (V • μs)
3. On the horizontal axis, select the maximum load current.
ILOAD(max) = 1 A
4. Identify the inductance region intersected by the E • T value and the Maximum Load Current value. Each
region is identified by an inductance value and an inductor code (LXX).
From the inductor value selection guide shown in Figure 30, the inductance region intersected by the 35 (V •
μs) horizontal line and the 1-A vertical line is 100 μH, and the inductor code is L29.
5. Select an appropriate inductor from the manufacturers' part numbers listed in Table 3.
From the table in Table 3, place line L29, and select an inductor part number from the list of manufacturers'
part numbers.
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9.2.2.2.3 Output Capacitor Selection (COUT)
1. In the majority of applications, low ESR electrolytic or solid tantalum capacitors between 47 μF and 330 μF
provide the best results. This capacitor must be placed close to the IC using short capacitor leads and short
copper traces. Do not use capacitors larger than 330 μF. See section on COUT in Output Capacitor Selection
(COUT).
2. To simplify the capacitor selection procedure, refer to the quick design table shown in Table 7. This table
contains different output voltages, and lists various output capacitors that will provide the best design
solutions.
From the quick design table shown in Table 7, place the output voltage column. From that column, place the
output voltage closest to the output voltage in the application. In this example, select the 24-V line. Under the
output capacitor section, select a capacitor from the list of through-hole electrolytic or surface-mount
tantalum types from four different capacitor manufacturers. TI recommends using both the manufacturers
and the manufacturers' series listed in the table.
In this example, through-hole aluminum electrolytic capacitors from several different manufacturers are
available:
–
82-μF, 35-V Panasonic HFQ Series
– 82-μF, 35-V Nichicon PL Series
3. The capacitor voltage rating must be at least 1.5 times greater than the output voltage, and often much
higher voltage ratings are required to satisfy the low ESR requirements needed for low output ripple voltage.
For a 20-V output, a capacitor rating of at least 30 V or more is required. In this example, either a 35-V or 50V capacitor would work. A 35-V rating was chosen, although a 50-V rating could also be used if a lower
output ripple voltage is required.
Other manufacturers or other types of capacitors may also be used, provided the capacitor specifications
(especially the 100-kHz ESR) closely match the types listed in Table 7. Refer to the capacitor manufacturers'
data sheet for this information.
9.2.2.2.4 Feedforward Capacitor (CFF)
For output voltages greater than approximately 10 V, an additional capacitor is required. The compensation
capacitor is typically between 50 pF and 10 nF, and is wired in parallel with the output voltage setting resistor,
R2. It provides additional stability for high output voltages, low input or output voltages, or very low ESR output
capacitors, such as solid tantalum capacitors. Use Equation 6 to calculate CFF.
(6)
This capacitor type can be ceramic, plastic, silver mica, and so forth (because of the unstable characteristics of
ceramic capacitors made with Z5U material, they are not recommended).
The table shown in Table 7 contains feedforward capacitor values for various output voltages. In this example, a
1-nF capacitor is required.
9.2.2.2.5 Catch Diode Selection (D1)
1. The catch diode current rating must be at least 1.3 times greater than the maximum load current. Also, if the
power supply design must withstand a continuous output short, the diode must have a current rating equal to
the maximum current limit of the LM2595. The most stressful condition for this diode is an overload or
shorted output condition. See Table 2.
2. The reverse voltage rating of the diode must be at least 1.25 times the maximum input voltage. Schottky
diodes provide the best performance, and in this example a 3-A, 40-V, 1N5822 Schottky diode is a good
choice.
3. This diode must be fast (short reverse recovery time) and must be placed close to the LM2595 using short
leads and short printed circuit traces. Because of their fast switching speed and low forward voltage drop,
Schottky diodes provide the best performance and efficiency, and must be the first choice, especially in low
output voltage applications. Ultra-fast recovery or high-efficiency rectifiers are also good choices, but some
types with an abrupt turnoff characteristic may cause instability or EMl problems. Ultra-fast recovery diodes
typically have reverse recovery times of 50 ns or less. Rectifiers such as the 1N4001 series must not be
used because they are too slow. The 3-A diode rating is more than adequate and will not be overstressed
even for a shorted output.
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9.2.2.2.6 Input Capacitor (CIN)
A low ESR aluminum or tantalum bypass capacitor is required between the input pin and ground to prevent large
voltage transients from appearing at the input. In addition, the RMS current rating of the input capacitor must be
selected to be at least ½ the DC load current. The capacitor manufacturer's data sheet must be checked to
assure that this current rating is not exceeded. Figure 23 shows typical RMS current ratings for several different
aluminum electrolytic capacitor values.
The important parameters for the input capacitor are the input voltage rating and the RMS current rating. With a
nominal input voltage of 28 V, an aluminum electrolytic aluminum electrolytic capacitor with a voltage rating
greater than 42 V (1.5 × VIN) is required. Because the next higher capacitor voltage rating is 50 V, a 50-V
capacitor must be used. The capacitor voltage rating of (1.5 × VIN) is a conservative guideline, and can be
modified somewhat if desired.
This capacitor must be placed close to the IC using short leads and the voltage rating must be approximately 1.5
times the maximum input voltage.
The RMS current rating requirement for the input capacitor of a buck regulator is approximately ½ the DC load
current. In this example, with a 1-A load, a capacitor with a RMS current rating of at least 500 mA is required.
Figure 23 can be used to select an appropriate input capacitor. From the curves, place the 50-V line and note
which capacitor values have RMS current ratings greater than 500 mA. Either a 100-μF or 120-μF, 50-V
capacitor could be used.
If solid tantalum input capacitors are used, TI recommends that they be surge current tested by the
manufacturer. See caution when using a high dielectric constant ceramic capacitor for input bypassing, because
it may cause severe ringing at the VIN pin.
For a through-hole design, a 120-μF, 50-V electrolytic capacitor (Panasonic HFQ series or Nichicon PL series or
equivalent) would be adequate. Other types or other manufacturers' capacitors can be used provided the RMS
ripple current ratings are adequate.
For surface-mount designs, solid tantalum capacitors can be used, but caution must be exercised with regard to
the capacitor surge current rating (see Input Capacitor (CIN) or input capacitors in this data sheet). The TPS
series available from AVX, and the 593D series from Sprague are both surge current tested.
To further simplify the buck regulator design procedure, TI is making available computer design software to be
used with the SIMPLE SWITCHER line of switching regulators.
Table 7. Output Capacitor and Feedforward Capacitor Selection Table
OUTPUT
VOLTAGE
(V)
THROUGH-HOLE ELECTROLYTIC OUTPUT CAPACITOR
PANASONIC
HFQ SERIES
(μF/V)
NICHICON PL
SERIES
(μF/V)
1.2
330/50
4
220/25
6
9
SURFACE-MOUNT TANTALUM OUTPUT CAPACITOR
FEEDFORWARD
CAPACITOR
AVX TPS
SERIES
(μF/V)
SPRAGUE
595D SERIES
(μF/V)
330/50
0
330/6.3
330/6.3
0
220/25
4.7 nF
220/10
220/10
4.7 nF
220/25
220/25
3.3 nF
220/10
220/10
3.3 nF
180/25
180/25
1.5 nF
100/16
180/16
1.5 nF
12
120/25
120/25
1.5 nF
68/20
120/20
1.5 nF
15
120/25
120/25
1.5 nF
68/20
100/20
1.5 nF
24
82/35
82/35
1 nF
33/25
33/35
220 pF
28
82/50
82/50
1 nF
10/35
33/35
220 pF
FEEDFORWARD
CAPACITOR
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9.2.2.3 Application Curves
VIN = 20 V, VOUT = 5 V, ILOAD = 600 mA
L = 22 μH, COUT = 220 μF, COUT ESR = 50 mΩ
A: Output pin voltage, 10 V/div.
B: Inductor current 0.5 A/div.
C: Output ripple voltage, 50 mV/div.
Horizontal time base: 2 µs/div.
Figure 36. Discontinuous Mode Switching Waveforms
30
A
100 mV
AC/div.
B
1A
0.5A
0A
VIN = 20 V, VOUT = 5 V, ILOAD = 250 mA to 750 mA
L = 22 μH, COUT = 220 μF, COUT ESR = 50 mΩ
A: Output voltage, 100 mV/div. (AC)
B: 250-mA to 750-mA load pulse
Horizontal time base: 200 µs/div.
Figure 37. Load Transient Response
for Discontinuous Mode
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10 Power Supply Recommendations
The LM2595 is designed to operate from an input voltage supply up to 40 V. This input supply must be well
regulated and able to withstand maximum input current and maintain a stable voltage.
11 Layout
11.1 Layout Guidelines
As in any switching regulator, layout is very important. Rapidly switching currents associated with wiring
inductance can generate voltage transients which can cause problems. For minimal inductance and ground
loops, the wires indicated by heavy lines must be wide printed circuit traces and must be kept as short as
possible. For best results, external components must be placed as close to the switcher lC as possible using
ground plane construction or single point grounding.
If open core inductors are used, take special care regarding the location and positioning of this type of inductor.
Allowing the inductor flux to intersect sensitive feedback, lC groundpath and COUT wiring can cause problems.
When using the adjustable version, take special care regarding the location of the feedback resistors and the
associated wiring. Physically place both resistors near the IC, and route the wiring away from the inductor,
especially an open core type of inductor (see Open Core Inductors for more information).
11.2 Layout Examples
CIN – 150-μF, 50-V aluminium electrolytic Nichicon, PL series
COUT – 120-μF, 25-V aluminium electrolytic Nichicon, PL series
D1 – 3-A, 40-V Schottky rectifier, 1N5822
L1 – 68-μH, L30, Schottky, through-hole
Figure 38. Typical Through-Hole PCB Layout, Fixed Output (1X Size)
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Layout Examples (continued)
CIN – 150-μF, 50-V aluminium electrolytic Nichicon, PL series
COUT – 120-μF, 25-V aluminium electrolytic Nichicon, PL series
D1 – 3-A, 40-V Schottky rectifier, 1N5822
L1 – 68-μH, L30, Schottky through-hole
R1 – 1-kΩ, 1%
R2 – Use formula in Detailed Design Procedure
CFF – See Table 7
Figure 39. Typical Through-Hole PCB Layout, Adjustable Output (1X Size)
11.3 Thermal Considerations
The LM2595 is available in two packages: a 5-pin TO-220 (NDH) and a 5-pin surface-mount TO-263 (KTT).
The TO-220 package can be used without a heat sink for ambient temperatures up to approximately 50°C
(depending on the output voltage and load current). Figure 40 shows the LM2595T junction temperature rises
above ambient temperature for different input and output voltages. The data tor these curves was taken with the
LM2595T (TO-220 package) operating as a switching regulator in an ambient temperature of 25°C (still air).
These temperature rise numbers are all approximate and there are many factors that can affect these
temperatures. Higher ambient temperatures require some heat sinking, either to the PCB or a small external heat
sink.
The TO-263 surface-mount package tab is designed to be soldered to the copper on a printed-circuit board
(PCB). The copper and the board are the heat sink for this package and the other heat producing components,
such as the catch diode and inductor. The PCB copper area that the package is soldered to must be at least 0.4
in2, and ideally must have 2 or more square inches of 2 oz (0.0028 in) copper. Additional copper area improves
the thermal characteristics, but with copper areas greater than approximately 3 in2, only small improvements in
heat dissipation are realized. If further thermal improvements are required, TI recommends using double sided or
multilayer PCB with large copper areas.
Figure 41 show the LM2595S (TO-263 package) junction temperature rise above ambient temperature with a 1-A
load for various input and output voltages. This data was taken with the circuit operating as a buck switching
regulator with all components mounted on a PCB to simulate the junction temperature under actual operating
conditions. This curve can be used for a quick check for the approximate junction temperature for various
conditions, but be aware that there are many factors that can affect the junction temperature.
For the best thermal performance, wide copper traces and generous amounts of PCB copper must be used in
the board layout. (One exception to this is the output (switch) pin, which must not have large areas of copper.)
Large areas of copper provide the best transfer of heat (lower thermal resistance) to the surrounding air, and
moving air lowers the thermal resistance even further.
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Thermal Considerations (continued)
Package thermal resistance and junction temperature rise numbers are all approximate, and there are many
factors that will affect these numbers. Some of these factors include board size, shape, thickness, position,
location, and even board temperature. Other factors are, trace width, total printed-circuit copper area, copper
thickness, single- or double-sided multilayer board, and the amount of solder on the board. The effectiveness of
the PCB to dissipate heat also depends on the size, quantity, and spacing of other components on the board, as
well as whether the surrounding air is still or moving. Furthermore, some of these components such as the catch
diode will add heat to the PCB and the heat can vary as the input voltage changes. For the inductor, depending
on the physical size, type of core material, and the DC resistance, it could either act as a heat sink taking heat
away from the board, or it could add heat to the board.
CIRCUIT DATA FOR TEMPERATURE RISE CURVE
TO-220 PACKAGE (NDH)
Capacitors
Through-hole electrolytic
Inductor
Through-hole, 68-μH Schottky
Diode
Through-hole, 3-A, 40-V Schottky
PCB
3 square inches, single-sided 2-oz copper (0.0028″)
Figure 40. Junction Temperature Rise, TO-220
CIRCUIT DATA FOR TEMPERATURE RISE CURVE
TO-263 PACKAGE (KTT)
Capacitors
Surface-mount tantalum, molded D size
Inductor
Surface-mount, 68-μH, Schottky
Diode
Surface-mount, 3-A, 40-V, Schottky
PCB
3 square inches, single-sided 2-oz copper (0.0028″)
Figure 41. Junction Temperature Rise, TO-263
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12 Device and Documentation Support
12.1 Community Resources
The following links connect to TI community resources. Linked contents are provided "AS IS" by the respective
contributors. They do not constitute TI specifications and do not necessarily reflect TI's views; see TI's Terms of
Use.
TI E2E™ Online Community TI's Engineer-to-Engineer (E2E) Community. Created to foster collaboration
among engineers. At e2e.ti.com, you can ask questions, share knowledge, explore ideas and help
solve problems with fellow engineers.
Design Support TI's Design Support Quickly find helpful E2E forums along with design support tools and
contact information for technical support.
12.2 Trademarks
E2E is a trademark of Texas Instruments.
SIMPLE SWITCHER is a registered trademark of Texas Instruments.
All other trademarks are the property of their respective owners.
12.3 Electrostatic Discharge Caution
These devices have limited built-in ESD protection. The leads should be shorted together or the device placed in conductive foam
during storage or handling to prevent electrostatic damage to the MOS gates.
12.4 Glossary
SLYZ022 — TI Glossary.
This glossary lists and explains terms, acronyms, and definitions.
13 Mechanical, Packaging, and Orderable Information
The following pages include mechanical, packaging, and orderable information. This information is the most
current data available for the designated devices. This data is subject to change without notice and revision of
this document. For browser-based versions of this data sheet, refer to the left-hand navigation.
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25-Feb-2022
PACKAGING INFORMATION
Orderable Device
Status
(1)
Package Type Package Pins Package
Drawing
Qty
Eco Plan
(2)
Lead finish/
Ball material
MSL Peak Temp
Op Temp (°C)
Device Marking
(3)
(4/5)
(6)
LM2595S-12
NRND
DDPAK/
TO-263
KTT
5
45
Non-RoHS
& Green
Call TI
Level-3-235C-168 HR
-40 to 125
LM2595S
-12 P+
LM2595S-12/NOPB
ACTIVE
DDPAK/
TO-263
KTT
5
45
RoHS-Exempt
& Green
SN
Level-3-245C-168 HR
-40 to 125
LM2595S
-12 P+
LM2595S-3.3
NRND
DDPAK/
TO-263
KTT
5
45
Non-RoHS
& Green
Call TI
Level-3-235C-168 HR
LM2595S
-3.3 P+
LM2595S-3.3/NOPB
ACTIVE
DDPAK/
TO-263
KTT
5
45
RoHS-Exempt
& Green
SN
Level-3-245C-168 HR
LM2595S
-3.3 P+
LM2595S-5.0
NRND
DDPAK/
TO-263
KTT
5
45
Non-RoHS
& Green
Call TI
Level-3-235C-168 HR
LM2595S
-5.0 P+
LM2595S-5.0/NOPB
ACTIVE
DDPAK/
TO-263
KTT
5
45
RoHS-Exempt
& Green
SN
Level-3-245C-168 HR
LM2595S
-5.0 P+
LM2595S-ADJ
NRND
DDPAK/
TO-263
KTT
5
45
Non-RoHS
& Green
Call TI
Level-3-235C-168 HR
LM2595S
-ADJ P+
LM2595S-ADJ/NOPB
ACTIVE
DDPAK/
TO-263
KTT
5
45
RoHS-Exempt
& Green
SN
Level-3-245C-168 HR
LM2595S
-ADJ P+
LM2595SX-12/NOPB
ACTIVE
DDPAK/
TO-263
KTT
5
500
RoHS-Exempt
& Green
SN
Level-3-245C-168 HR
LM2595SX-3.3/NOPB
ACTIVE
DDPAK/
TO-263
KTT
5
500
RoHS-Exempt
& Green
SN
Level-3-245C-168 HR
LM2595S
-3.3 P+
LM2595SX-5.0/NOPB
ACTIVE
DDPAK/
TO-263
KTT
5
500
RoHS-Exempt
& Green
SN
Level-3-245C-168 HR
LM2595S
-5.0 P+
LM2595SX-ADJ
NRND
DDPAK/
TO-263
KTT
5
500
Non-RoHS
& Green
Call TI
Level-3-235C-168 HR
LM2595S
-ADJ P+
LM2595SX-ADJ/NOPB
ACTIVE
DDPAK/
TO-263
KTT
5
500
RoHS-Exempt
& Green
SN
Level-3-245C-168 HR
LM2595S
-ADJ P+
LM2595T-12/NOPB
ACTIVE
TO-220
NDH
5
45
RoHS & Green
SN
Level-1-NA-UNLIM
LM2595T-3.3/NOPB
ACTIVE
TO-220
NDH
5
45
RoHS & Green
SN
Level-1-NA-UNLIM
LM2595T
-3.3 P+
LM2595T-5.0/NOPB
ACTIVE
TO-220
NDH
5
45
RoHS & Green
SN
Level-1-NA-UNLIM
LM2595T
-5.0 P+
LM2595T-ADJ/NOPB
ACTIVE
TO-220
NDH
5
45
RoHS & Green
SN
Level-1-NA-UNLIM
LM2595T
Addendum-Page 1
-40 to 125
-40 to 125
LM2595S
-12 P+
LM2595T
-12 P+
Samples
PACKAGE OPTION ADDENDUM
www.ti.com
Orderable Device
25-Feb-2022
Status
(1)
Package Type Package Pins Package
Drawing
Qty
Eco Plan
(2)
Lead finish/
Ball material
MSL Peak Temp
Op Temp (°C)
Device Marking
(3)
(4/5)
(6)
-ADJ P+
(1)
The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2)
RoHS: TI defines "RoHS" to mean semiconductor products that are compliant with the current EU RoHS requirements for all 10 RoHS substances, including the requirement that RoHS substance
do not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, "RoHS" products are suitable for use in specified lead-free processes. TI may
reference these types of products as "Pb-Free".
RoHS Exempt: TI defines "RoHS Exempt" to mean products that contain lead but are compliant with EU RoHS pursuant to a specific EU RoHS exemption.
Green: TI defines "Green" to mean the content of Chlorine (Cl) and Bromine (Br) based flame retardants meet JS709B low halogen requirements of
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