LM2695
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SNVS413A – JANUARY 2006 – REVISED APRIL 2013
LM2695 High Voltage (30V, 1.25A) Step Down Switching Regulator
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FEATURES
DESCRIPTION
•
•
•
•
•
•
The LM2695 Step Down Switching Regulator features
all of the functions needed to implement a low cost,
efficient, buck bias regulator capable of supplying
1.25A to the load. This buck regulator contains a 33V
N-Channel Buck Switch, and is available in the
thermally enhanced WSON-10 and HTSSOP-14
packages. The hysteretic regulation scheme requires
no loop compensation, results in fast load transient
response, and simplifies circuit implementation. The
operating frequency remains constant with line and
load variations due to the inverse relationship
between the input voltage and the on-time. The
current limit detection is set at 1.25A. Additional
features include: VCC under-voltage lockout, thermal
shutdown, gate drive under-voltage lockout, and
maximum duty cycle limiter.
1
2
•
•
•
•
•
•
•
Integrated 33V, N-Channel Buck Switch
Integrated Start-Up Regulator
Input Voltage Range: 8V to 30V
No Loop Compensation Required
Ultra-Fast Transient Response
Operating Frequency Remains Constant with
Load Current and Input Voltage
Maximum Duty Cycle Limited During Start-Up
Adjustable Output Voltage
Valley Current Limit At 1.25A
Precision Internal Reference
Low Bias Current
Highly Efficient Operation
Thermal Shutdown
TYPICAL APPLICATIONS
•
•
•
High Efficiency Point-Of-Load (POL) Regulator
Non-Isolated Telecommunication Buck
Regulator
Secondary High Voltage Post Regulator
PACKAGE
•
•
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10-Pin WSON (4 mm x 4 mm)
14-Pin HTSSOP
Exposed Thermal Pad For Improved Heat
Dissipation
Basic Step Down Regulator
8V - 30V
Input
VIN
VCC
C3
C1
LM2695
RON
BST
C4
L1
RON/SD
SHUTDOWN
VOUT
SW
D1
SS
R1
R3
ISEN
C2
C6
FB
RTN
SGND
R2
1
2
Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of
Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet.
All trademarks are the property of their respective owners.
PRODUCTION DATA information is current as of publication date.
Products conform to specifications per the terms of the Texas
Instruments standard warranty. Production processing does not
necessarily include testing of all parameters.
Copyright © 2006–2013, Texas Instruments Incorporated
LM2695
SNVS413A – JANUARY 2006 – REVISED APRIL 2013
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Connection Diagram
1
2
3
4
5
6
7
NC
NC
SW
VIN
BST
VCC
ISEN
RON/SD
SGND
SS
RTN
FB
NC
NC
14
1
13
2
12
3
11
4
10
5
SW
VIN
BST
VCC
ISEN
RON/SD
SGND
SS
RTN
FB
10
9
8
7
6
9
8
Figure 1. 14-Lead HTSSOP (Top View)
See PWP0014A Package
Figure 2. 10-Lead WSON (Top View)
See DPR0010A Package
PIN DESCRIPTIONS
Pin Number
Name
Description
Application Information
WSON-10
HTSSOP-14
1
2
SW
Switching Node
Internally connected to the buck switch source.
Connect to the inductor, free-wheeling diode, and
bootstrap capacitor.
2
3
BST
Boost pin for bootstrap capacitor
Connect a 0.022 µF capacitor from SW to this pin.
The capacitor is charged from VCC via an internal
diode during each off-time.
3
4
ISEN
Current sense
The re-circulating current flows through the internal
sense resistor, and out of this pin to the free-wheeling
diode. Current limit is nominally set at 1.25A.
4
5
SGND
Sense Ground
Re-circulating current flows into this pin to the current
sense resistor.
5
6
RTN
Circuit Ground
Ground for all internal circuitry other than the current
limit detection.
6
9
FB
Feedback input from the regulated
output
Internally connected to the regulation and overvoltage comparators. The regulation level is 2.5V.
7
10
SS
Softstart
An internal 12.3 µA current source charges an
external capacitor to 2.5V, providing the softstart
function.
8
11
RON/SD
On-time control and shutdown
An external resistor from VIN to this pin sets the buck
switch on-time. Grounding this pin shuts down the
regulator.
9
12
VCC
Output from the startup regulator
Nominally regulates at 7.0V. An external voltage (8V14V) can be applied to this pin to reduce internal
dissipation. An internal diode connects VCC to VIN.
13
VIN
Input supply voltage
Nominal input range is 8.0V to 30V.
1,7,8,14
NC
No connection.
No internal connection.
EP
Exposed Pad
Exposed metal pad on the underside of the device. It
is recommended to connect this pad to the PC board
ground plane to aid in heat dissipation.
10
These devices have limited built-in ESD protection. The leads should be shorted together or the device placed in conductive foam
during storage or handling to prevent electrostatic damage to the MOS gates.
2
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Absolute Maximum Ratings (1) (2) (3)
VIN to RTN
33V
BST to RTN
47V
SW to RTN (Steady State)
ESD Rating (4)
-1.5V
Human Body Model
2kV
BST to VCC
33V
VIN to SW
33V
BST to SW
14V
VCC to RTN
14V
SGND to RTN
-0.3V to +0.3V
Current out of ISEN
See Text
SS to RTN
-0.3V to 4V
All Other Inputs to RTN
-0.3 to 7V
Storage Temperature Range
-65°C to +150°C
Junction Temperature
(1)
(2)
(3)
(4)
150°C
Absolute Maximum Ratings are limits beyond which damage to the device may occur. Operating Ratings are conditions under which
operation of the device is intended to be functional. For ensured specifications and test conditions, see the Electrical Characteristics.
For detailed information on soldering plastic WSON-10 packages, refer to the Packaging Data Book available from TI.
If Military/Aerospace specified devices are required, please contact the TI Sales Office/Distributors for availability and specifications.
The human body model is a 100pF capacitor discharged through a 1.5kΩ resistor into each pin.
Operating Ratings (1)
VIN
8.0V to 30V
−40°C to + 125°C
Junction Temperature
(1)
Absolute Maximum Ratings are limits beyond which damage to the device may occur. Operating Ratings are conditions under which
operation of the device is intended to be functional. For ensured specifications and test conditions, see the Electrical Characteristics.
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Electrical Characteristics
Specifications with standard type are for TJ = 25°C only; limits in boldface type apply over the full Operating Junction
Temperature (TJ) range. Minimum and Maximum limits are ensured through test, design, or statistical correlation. Typical
values represent the most likely parametric norm at TJ = 25°C, and are provided for reference purposes only. Unless
otherwise stated the following conditions apply: VIN = 24V, RON = 200kΩ (1).
Symbol
Parameter
Conditions
Min
Typ
Max
Units
6.6
7
7.4
V
Start-Up Regulator, VCC
VCCReg
UVLOVCC
VCC regulated output
VIN-VCC dropout voltage
ICC = 0 mA,
VCC = UVLOVCC + 250 mV
1.3
V
VCC output impedance
0 mA ≤ ICC ≤ 5 mA
140
Ω
VCC current limit (2)
VCC = 0V
9.7
mA
VCC under-voltage lockout
threshold
VCC increasing
5.7
UVLOVCC hysteresis
VCC decreasing
150
mV
UVLOVCC filter delay
100 mV overdrive
3
µs
IIN operating current
Non-switching, FB = 3V
0.5
0.8
mA
IIN shutdown current
RON/SD = 0V
95
200
µA
0.33
0.7
Ω
4.4
5.5
V
Switch Characteristics
Rds(on)
Buck Switch Rds(on)
ITEST = 200 mA
UVLOGD
Gate Drive UVLO
VBST - VSW Increasing
3.0
UVLOGD hysteresis
480
V
mV
Softstart Pin
Pull-up voltage
2.5
V
Internal current source
12.3
µA
Current Limit
ILIM
Threshold
Current out of ISEN
1
1.25
1.5
A
Resistance from ISEN to SGND
130
mΩ
Response time
150
ns
On Timer
tON - 1
On-time
VIN = 10V, RON = 200 kΩ
tON - 2
On-time
VIN = 30V, RON = 200 kΩ
Shutdown threshold
Voltage at RON/SD rising
Threshold hysteresis
Voltage at RON/SD falling
2.1
2.8
3.6
950
0.45
0.8
µs
ns
1.2
V
37
mV
250
ns
Off Timer
tOFF
Minimum Off-time
Regulation and Over-Voltage Comparators (FB Pin)
VREF
FB regulation threshold
SS pin = steady state
FB over-voltage threshold
2.440
2.5
2.550
V
2.9
V
1
nA
Thermal shutdown temperature
175
°C
Thermal shutdown hysteresis
20
°C
FB bias current
Thermal Shutdown
TSD
Thermal Resistance
(1)
(2)
4
θJA
Junction to Ambient
0 LFPM Air Flow
Both Packages
37
θJC
Junction to Case
Both Packages
6.6
°C/W
°C/W
Typical specifications represent the most likely parametric norm at 25°C operation.
VCC provides self bias for the internal gate drive and control circuits. Device thermal limitations limit external loading
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Typical Performance Characteristics
7.0
7.5
RON = 400k
6.0
FS = 150 kHz
ON-TIME (Ps)
VCC (V)
7.0
FS = 45 kHz
6.5
FS = 750 kHz
6.0
5.0
4.0
RON = 200k
3.0
RON = 100k
2.0
5.5
1.0 RON = 44.2k
0
5.0
6.5
7.0
7.5
8.0
8.5
9.0
10
0
20
30
VIN (V)
VIN (V)
Figure 3. VCC vs VIN
Figure 4. ON-Time vs VIN and RON
Typical Application Circuit and Block Diagram
7V SERIES
REGULATOR
8V-30V
Input
LM2695
VIN
VCC
C3
VCC
UVLO
THERMAL
SHUTDOWN
C5
C1
RON
RON
/SD
ON TIMER
RON
START
COMPLETE
250 ns
OFF TIMER
+
0.8V
START
COMPLETE
BST
GATE DRIVE
UVLO
C4
VIN
2.5V
12.3 PA
SS
C6
DRIVER
FB +
REGULATION
COMPARATOR
+
OVER2.9V VOLTAGE
COMPARATOR
RTN
DRIVER
LOGIC
L1
LEVEL
SHIFT
SW
VOUT1
D1
CURRENT LIMIT
COMPARATOR
+
62.5 mV
+
ISEN
R1
RSENSE
50 m:
SGND
R2
R3
VOUT2
C2
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Functional Description
The LM2695 Step Down Switching Regulator features all the functions needed to implement a low cost, efficient
buck bias power converter capable of supplying 1.25A to the load. This high voltage regulator contains a 33V NChannel buck switch, is easy to implement, and is available in the thermally enhanced WSON-10 and HTSSOP14 packages. The regulator’s operation is based on a hysteretic control scheme, and uses an on-time control
which varies inversely with VIN. This feature allows the operating frequency to remain relatively constant with
load and input voltage variations. The hysteretic control requires no loop compensation resulting in very fast load
transient response. The valley current limit detection circuit, internally set at 1.25A, holds the buck switch off until
the high current level subsides. The functional block diagram is shown in Typical Application Circuit and Block
Diagram.
The LM2695 can be applied in numerous applications to efficiently regulate down higher voltages. Additional
features include: Thermal shutdown, VCC under-voltage lockout, gate drive under-voltage lockout, and maximum
duty cycle limiter.
Hysteretic Control Circuit Overview
The LM2695 buck DC-DC regulator employs a control scheme based on a comparator and a one-shot on-timer,
with the output voltage feedback (FB) compared to an internal reference (2.5V). If the FB voltage is below the
reference the buck switch is turned on for a time period determined by the input voltage and a programming
resistor (RON). Following the on-time the switch remains off for a minimum of 250 ns, and until the FB voltage
falls below the reference. The buck switch then turns on for another on-time period. Typically, during start-up, or
when the load current increases suddenly, the off-times are at the minimum of 250 ns. Once regulation is
established, the off-times are longer.
When in regulation, the LM2695 operates in continuous conduction mode at heavy load currents and
discontinuous conduction mode at light load currents. In continuous conduction mode current always flows
through the inductor, never reaching zero during the off-time. In this mode the operating frequency remains
relatively constant with load and line variations. The minimum load current for continuous conduction mode is
one-half the inductor’s ripple current amplitude. The operating frequency is approximately:
VOUT
FS =
1.3 x 10-10 x RON
(1)
The buck switch duty cycle is equal to:
VOUT
tON
DC =
tON + tOFF
=
VIN
(2)
In discontinuous conduction mode current through the inductor ramps up from zero to a peak during the on-time,
then ramps back to zero before the end of the off-time. The next on-time period starts when the voltage at FB
falls below the reference - until then the inductor current remains zero, and the load current is supplied by the
output capacitor (C2). In this mode the operating frequency is lower than in continuous conduction mode, and
varies with load current. Conversion efficiency is maintained at light loads since the switching losses reduce with
the reduction in load and frequency. The approximate discontinuous operating frequency can be calculated as
follows:
VOUT2 x L1 x 1.18 x 1020
FS =
RL x (RON)2
where
•
RL = the load resistance
(3)
The output voltage is set by two external resistors (R1, R2). The regulated output voltage is calculated as
follows:
VOUT = 2.5 x (R1 + R2) / R2
6
(4)
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Output voltage regulation is based on ripple voltage at the feedback input, requiring a minimum amount of ESR
for the output capacitor C2. The LM2695 requires a minimum of 25 mV of ripple voltage at the FB pin. In cases
where the capacitor’s ESR is insufficient additional series resistance may be required (R3 in Typical Application
Circuit and Block Diagram).
For applications where lower output voltage ripple is required the output can be taken directly from a low ESR
output capacitor as shown in Figure 5. However, R3 slightly degrades the load regulation.
L1
SW
LM2695
R1
R3
FB
VOUT2
R2
C2
Figure 5. Low Ripple Output Configuration
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Start-Up Regulator, VCC
The start-up regulator is integral to the LM2695. The input pin (VIN) can be connected directly to line voltage up
to 30V, with transient capability to 33V. The VCC output regulates at 7.0V, and is current limited at 9.7 mA. Upon
power up, the regulator sources current into the external capacitor at VCC (C3). When the voltage on the VCC
pin reaches the under-voltage lockout threshold of 5.7V, the buck switch is enabled and the Softstart pin is
released to allow the Softstart capacitor (C6) to charge up.
The minimum input voltage is determined by the regulator’s dropout voltage, the VCC UVLO falling threshold
(≊5.5V), and the frequency. When VCC falls below the falling threshold the VCC UVLO activates to shut off the
output. If VCC is externally loaded, the minimum input voltage increases since the output impedance at VCC is
≊140Ω.
To reduce power dissipation in the start-up regulator, an auxiliary voltage can be diode connected to the VCC pin.
Setting the auxiliary voltage to between 8V and 14V shuts off the internal regulator, reducing internal power
dissipation. The sum of the auxiliary voltage and the input voltage (VCC + VIN) cannot exceed 47V. Internally, a
diode connects VCC to VIN. See Figure 6.
VCC
C3
BST
C4
L1
LM2695
D2
SW
VOUT1
D1
ISEN
R3
R1
SGND
R2
C2
FB
Figure 6. Self Biased Configuration
Regulation Comparator
The feedback voltage at FB is compared to the voltage at the Softstart pin (2.5V). In normal operation (the output
voltage is regulated), an on-time period is initiated when the voltage at FB falls below 2.5V. The buck switch
stays on for the programmed on-time, causing the FB voltage to rise above 2.5V. After the on-time period, the
buck switch stays off until the FB voltage falls below 2.5V. Input bias current at the FB pin is less than 100 nA
over temperature.
Over-Voltage Comparator
The voltage at FB is compared to an internal 2.9V reference. If the voltage at FB rises above 2.9V the on-time
pulse is immediately terminated. This condition can occur if the input voltage or the output load changes
suddenly, or if the inductor (L1) saturates. The buck switch remains off until the voltage at FB falls below 2.5V.
ON-Time Timer, and Shutdown
The on-time for the LM2695 is determined by the RON resistor and the input voltage (VIN), and is calculated from:
1.3 x 10-10 x RON
tON =
8
VIN
(5)
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See Figure 4. The inverse relationship with VIN results in a nearly constant frequency as VIN is varied. To set a
specific continuous conduction mode switching frequency (FS), the RON resistor is determined from the following:
RON =
VOUT
FS x 1.3 x 10-10
(6)
In high frequency applicatons the minimum value for tON is limited by the maximum duty cycle required for
regulation and the minimum off-time of (250 ns, ±15%). The minimum off-time limits the maximum duty cycle
achievable with a low voltage at VIN. The minimum allowed on-time to regulate the desired VOUT at the minimum
VIN is determined from the following:
VOUT x 288 ns
tON(min) =
(VIN(min) - VOUT)
(7)
The LM2695 can be remotely shut down by taking the RON/SD pin below 0.8V. See Figure 7. In this mode the
SS pin is internally grounded, the on-timer is disabled, and bias currents are reduced. Releasing the RON/SD pin
allows normal operation to resume. The voltage at the RON/SD pin is between 1.5V and 3.0V, depending on VIN
and the RON resistor.
VIN
Input
Voltage
RON
LM2695
RON/SD
STOP
RUN
Figure 7. Shutdown Implementation
Current Limit
Current limit detection occurs during the off-time by monitoring the recirculating current through the free-wheeling
diode (D1). Referring to Typical Application Circuit and Block Diagram, when the buck switch is turned off the
inductor current flows through the load, into SGND, through the sense resistor, out of ISEN and through D1. If
that current exceeds 1.25A the current limit comparator output switches to delay the start of the next on-time
period if the voltage at FB is below 2.5V. The next on-time starts when the current out of ISEN is below 1.25A
and the voltage at FB is below 2.5V. If the overload condition persists causing the inductor current to exceed
1.25A during each on-time, that is detected at the beginning of each off-time. The operating frequency is lower
due to longer-than-normal off-times.
Figure 8 illustrates the inductor current waveform. During normal operation the load current is Io, the average of
the ripple waveform. When the load resistance decreases the current ratchets up until the lower peak reaches
1.25A. During the Current Limited portion of Figure 8, the current ramps down to 1.25A during each off-time,
initiating the next on-time (assuming the voltage at FB is