LM3102EVAL

User's Guide SNVA248A – October 2007 – Revised April 2013 AN-1646 LM3102 Demonstration Board Reference Design 1 Introduction The LM3102 Step Down Switching Regulator features all required functions to implement a cost effective, efficient buck power converter capable of supplying 2.5A to loads. The Constant On-Time (COT) regulation scheme requires no loop compensation, results in a fast load transient response and simple circuit implementation that allows a low component count, and consequently very small overall board space is required for a typical application. The regulator can function properly even with an all ceramic output capacitor network, and does not rely on the output capacitor’s ESR for stability. The operating frequency remains constant with line variations due to the inverse relationship between the input voltage and the on-time. Protection features include output over-voltage protection, thermal shutdown, VCC undervoltage lock-out, gate drive under-voltage lock-out. The LM3102 is available in the thermally enhanced HTSSOP-20 package. This user's guide details the design of a demonstration board which provides a 3.3V output voltage with 2.5A load capability for a wide input voltage range from 8V to 42V. The demonstration board schematic, PCB layout, Bill of Materials, and circuit design descriptions are shown. Typical performance and operating waveforms are also provided for reference. 2 Demonstration Board Schematic Figure 1. LM3102 Demonstration Board Schematic All trademarks are the property of their respective owners. SNVA248A – October 2007 – Revised April 2013 Submit Documentation Feedback AN-1646 LM3102 Demonstration Board Reference Design Copyright © 2007–2013, Texas Instruments Incorporated 1 Quick Setup Procedures 3 www.ti.com Quick Setup Procedures Table 1. Demonstration Board Quick Setup Procedures Step 4 Description Notes 1 Connect a power supply to VIN terminals 2 Connect a load to VOUT terminals VIN range: 8V to 42V 3 SD (JP1) should be left open for normal operation. Short this jumper to shutdown 4 Set VIN = 18V, with 0A load applied, check VOUT with a voltmeter 5 Apply 2.5A load and check VOUT Nominal 3.3V 6 Short output terminals and check the short circuit current with an ammeter Nominal 2.95A 7 Short SD (JP1) to check the shutdown function IOUT range: 0A to 2.5A Nominal 3.3V Performance Characteristics Table 2. Demonstration Board Performance Characteristics Description Symbol Min Typ Max Unit Input Voltage VIN 8 18 42 V Output Voltage VOUT 3.2 3.3 3.4 V Output Current IOUT 0 - 2.5 A Output Voltage Ripple VOUT(Ripple) - - 50 mVp-p Output Voltage Regulation ΔVOUT Efficiency Output Short Current Limit 5 Condition ALL VIN and IOUT Conditions -3 3 % VIN = 8V 84 92 % VIN = 24V 73 85 VIN = 42V (IOUT = 0.1A to 2.5A) 62 79 ILIM-SC 2.95 A Design Procedure The LM3102 is easy to use compared with other devices available on the market because it integrates all key components, including both the main and synchronous power MOSFETs, in a single package and requires no loop compensation owing to the use of the Constant On-Time (COT) hysteretic control scheme. The design of the demonstration board is detailed below. Design Parameters: VIN = 8V to 42V, typical 18V VOUT = 3.3V IOUT = 2.5A 2 AN-1646 LM3102 Demonstration Board Reference Design SNVA248A – October 2007 – Revised April 2013 Submit Documentation Feedback Copyright © 2007–2013, Texas Instruments Incorporated Design Procedure www.ti.com Step 1: Calculate the feedback resistors The ratio of the feedback resistors can be calculated from the following equation: R3 VOUT -1 = R4 0.8 (1) As a general practice, R3 and R4 should be chosen from standard 1% resistor values in the range of 1.0 kΩ to 10 kΩ satisfying the above ratio. Now, select R4 = 2.21 kΩ, with VOUT = 3.3V, R3 = 2.21 k: VOUT 0.8 - 1 = 6.91 k: (2) Step 2: Calculate the on-time setting resistor The switching frequency fSW of the demonstration board is affected by the on-time ton of the LM3102, which is determined by R1. If fSW and VOUT are determined, R1 can be calculated as follows: R1 = VOUT 1.3 x 10-10 x fSW (3) For this demonstration board design, VOUT = 3.3V and fSW = 500 kHz are chosen. As a result, R1 = 50.8 kΩ. To ensure that the on-time is larger than the minimum limit, which is 150 ns, the value of R1 must satisfy the following equation: R1 t VIN(MAX) x 150 ns 1.3 x 10-10 (4) Now the maximum VIN is 42V, the calculated R1 satisfies Equation 4. Step 3: Determine the inductance The main parameter affected by the inductor is the amplitude of the inductor current ripple ILR. Once ILR is selected, L can be determined by: L= VOUT x (VIN - VOUT) ILR x fSW x VIN (5) For this demonstration board design, ILR = 0.5A is selected. Now VIN = 18V, VOUT = 3.3V, and fSW = 500 kHz. As a result, L = 10.78 µH. Figure 2. Inductor Selection for VOUT = 3.3V SNVA248A – October 2007 – Revised April 2013 Submit Documentation Feedback AN-1646 LM3102 Demonstration Board Reference Design Copyright © 2007–2013, Texas Instruments Incorporated 3 Design Procedure www.ti.com Step 4: Determine the value of other components C1 and C2: The function of the input capacitor is to supply most of the main MOSFET current during the on-time, and limit the voltage ripple at the VIN pin, assuming that the voltage source feeding to the VIN pin has finite output impedance. If the voltage source’s dynamic impedance is high (effectively a current source), the input capacitor supplies the average input current, but not the ripple current. At maximum load current, when the main MOSFET turns on, the current to the VIN pin suddenly increases from zero to the lower peak of the inductor’s ripple current and ramps up to the higher peak value. It then drops to zero at turn-off. The average current during the on-time is the load current. For a worst case calculation, the input capacitor must be capable of supplying this average load current during the maximum on-time. The input capacitor is calculated from: CIN = IOUT x ton 'VIN where: • • • • CIN = C1 + C2 is the input capacitor IOUT is the load current ton is the maximum on-time ΔVIN is the allowable ripple voltage at VIN (6) In this demonstration board, two 10 µF capacitors connecting in parallel are used. C3: C3’s purpose is to help avoid transients and ringing due to long lead inductance at the VIN pin. A low ESR 0.1 µF ceramic chip capacitor located close to the LM3102 is used in this demonstration board. C4: A 33 nF high quality ceramic capacitor with low ESR is used for C4 since it supplies a surge current to charge the main MOSFET gate driver at turn-on. Low ESR also helps ensure a complete recharge during each off-time. C5: The capacitor at the SS pin determines the soft-start time, that is, the time for the reference voltage at the regulation comparator and the output voltage to reach their final value. The time is determined from the following equation: tSS = C5 x 0.8V 8 PA (7) In this demonstration board, a 10 nF capacitor is used, and the corresponding soft-start time is about 1 ms. C8: The capacitor on the VCC output provides not only noise filtering and stability, but also prevents false triggering of the VCC UVLO at the main MOSFET on/off transitions. C8 should be no smaller than 680 nF for stability, and should be a good quality, low ESR, ceramic capacitor. In this demonstration board, a 1 µF capacitor is used. C9: If the output voltage is higher than 1.6V, C9 is needed in the Discontinuous Conduction Mode to reduce the output ripple. In this demonstration board, a 10 nF capacitor is used. C10 and C11: The output capacitor should generally be no smaller than 10 µF. Experimentation is usually necessary to determine the minimum value for the output capacitor, as the nature of the load may require a larger value. A load which creates significant transients requires a larger output capacitor than a fixed load. In this demonstration board, two 47 µF capacitors are connected in parallel to provide a low output ripple. C12: C12 is a small value ceramic capacitor located close to the LM3102 to further suppress high frequency noise at VOUT. A 100 nF capacitor is used in this demonstration board. 4 AN-1646 LM3102 Demonstration Board Reference Design SNVA248A – October 2007 – Revised April 2013 Submit Documentation Feedback Copyright © 2007–2013, Texas Instruments Incorporated PC Board Layout www.ti.com 6 PC Board Layout The LM3102 regulation, over-voltage, and current limit comparators are very fast so they will respond to short duration noise pulses. Layout is therefore critical for optimum performance. It must be as neat and compact as possible, and all external components must be as close to their associated pins of the LM3102 as possible. The loop formed by the input capacitors (C1 and C2), the main and synchronous MOSFET internal to the LM3102, and the PGND pin should be as small as possible. The connection from the PGND pin to the input capacitors should be as short and direct as possible. Vias should be added to connect the ground of the input capacitors to a ground plane, located as close to the capacitor as possible. The bootstrap capacitor C4 should be connected as close to the SW and BST pins as possible, and the connecting traces should be thick. The feedback resistors and capacitor R3, R4, and C9 should be close to the FB pin. A long trace running from VOUT to R3 is generally acceptable since this is a low impedance node. Ground R4 directly to the AGND pin (pin 7). The output capacitor C10, C11 should be connected close to the load and tied directly to the ground plane. The inductor L1 should be connected close to the SW pin with as short a trace as possible to reduce the potential for EMI (electromagnetic interference) generation. If it is expected that the internal dissipation of the LM3102 will produce excessive junction temperature during normal operation, making good use of the PC board’s ground plane can help considerably to dissipate heat. The exposed pad on the bottom of the LM3102 IC package can be soldered to the ground plane, which should extend out from beneath the LM3102 to help dissipate heat. The exposed pad is internally connected to the LM3102 IC substrate. Additionally the use of thick traces, where possible, can help conduct heat away from the LM3102. Using numerous vias to connect the die attached pad to the ground plane is a good practice. Judicious positioning of the PC board within the end product, along with the use of any available air flow (forced or natural convection) can help reduce the junction temperature. Figure 3. LM3102 Demonstration Board PCB Top Overlay SNVA248A – October 2007 – Revised April 2013 Submit Documentation Feedback AN-1646 LM3102 Demonstration Board Reference Design Copyright © 2007–2013, Texas Instruments Incorporated 5 PC Board Layout www.ti.com Figure 4. LM3102 Demonstration Board PCB Top View Figure 5. LM3102 Demonstration Board PCB Bottom View 6 AN-1646 LM3102 Demonstration Board Reference Design SNVA248A – October 2007 – Revised April 2013 Submit Documentation Feedback Copyright © 2007–2013, Texas Instruments Incorporated Bill of Materials www.ti.com 7 Bill of Materials Designation Description Size Manufacturer Part # Vendor C1, C2 Cap 10µF 50V Y5V 1210 GRM32DF51H106ZA01L muRata C3 Cap MLCC 0.1µF 50V X7R 0603 ECJ1VB1H104K Panasonic C4 0603/X7R/33000pF/25V 0603 GRM188R71E333KA01B muRata C5, C9 0603/X7R/10000pF/50V 0603 GRM188R71H103KA01B muRata C8 0603/X5R/1µF/10V 0603 GRM188R61A105KA61B muRata C10, C11 Cap MLCC 47µF 6.3V X5R 1210 ECJ4YB0J476M Panasonic C12 0603/X7R/0.1µF/25V 0603 GRM188R71E104KA01B muRata R1 Resistor Chip 51.1kΩ F 0603 CRCW06035112F Vishay R3 Resistor Chip 6.81kΩ F 0603 CRCW06036811F Vishay R4 Resistor Chip 2.21kΩ F 0603 CRCW06032211F Vishay L1 Inductor 10µH 4.40A POWER-CHOKE 10.3 × 10.5 × 4 CDRH104RNP-100NC Sumida SMD-Power Choke WE-TPC 3.6A Type XLH 10 × 10 × 3.8 744066100 Wurth U1 IC LM3102 HTSSOP-20 LM3102 Texas Instruments PCB LM3102 demo board SNVA248A – October 2007 – Revised April 2013 Submit Documentation Feedback Texas Instruments AN-1646 LM3102 Demonstration Board Reference Design Copyright © 2007–2013, Texas Instruments Incorporated 7 Typical Performance and Waveforms 8 www.ti.com Typical Performance and Waveforms All curves and waveforms are taken at VIN = 18V with the demonstration board and TA = 25°C unless otherwise specified. 8 Efficiency vs Load Current (VOUT = 3.3V) VOUT Regulation vs Load Current (VOUT = 3.3V) Continuous Mode Operation (VOUT = 3.3V, 2.5A Loaded) Discontinuous Mode Operation (VOUT = 3.3V, 0.1A Loaded) DCM to CCM Transition (VOUT = 3.3V, 0.1A - 2.5A Load) Load Transient (VOUT = 3.3V, 0.25A - 2.5A Load, Current slew-rate: 2.5A/µs) AN-1646 LM3102 Demonstration Board Reference Design SNVA248A – October 2007 – Revised April 2013 Submit Documentation Feedback Copyright © 2007–2013, Texas Instruments Incorporated Typical Performance and Waveforms www.ti.com Power Up (VOUT = 3.3V, 2.5A Loaded) Enable Transient (VOUT = 3.3V, 2.5A Loaded) Shutdown Transient (VOUT = 3.3V, 2.5A Loaded) SNVA248A – October 2007 – Revised April 2013 Submit Documentation Feedback AN-1646 LM3102 Demonstration Board Reference Design Copyright © 2007–2013, Texas Instruments Incorporated 9 IMPORTANT NOTICE Texas Instruments Incorporated and its subsidiaries (TI) reserve the right to make corrections, enhancements, improvements and other changes to its semiconductor products and services per JESD46, latest issue, and to discontinue any product or service per JESD48, latest issue. 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