User's Guide
SNVA482A – May 2011 – Revised April 2013
AN-2147 LM34923 Evaluation Board
1
Introduction
The LM34923 EVAL evaluation board provides the design engineer with a fully functional buck regulator,
employing the constant on-time (COT) operating principle. This evaluation board provides a 5V output
over an input range of 6V to 75V. The circuit delivers load currents to 500 mA, with current limit set at a
nominal 1 Amp.
The board’s specification are:
• Input Voltage: 6V to 75V
• Output Voltage: 5V
• Maximum load current: 500 mA
• Minimum load current: 0A
• Current Limit: 1 Amp (nominal)
• Measured Efficiency: 94.75% (VIN = 6V, IOUT = 100 mA)
• Nominal Switching Frequency: 200 kHz
• Size: 2.6 in. x 1.6 in.
Figure 1. Evaluation Board - Top Side
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1
Theory of Operation
2
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Theory of Operation
Figure 6 shows the evaluation board schematic. When the circuit is in regulation, the buck switch is on
each cycle for a time determined by R1 and VIN according to Equation 1:
-10
ton =
1.25 x 10 x (R1 + 500:)
+ 30 ns
VIN - 0.5V
(1)
The on-time of this evaluation board ranges from ≊4.38 µs at VIN = 6V, to ≊351 ns at VIN = 75V. The ontime varies inversely with VIN to maintain a nearly constant switching frequency. At the end of each ontime the minimum Off-Timer ensures the buck switch is off for at least 260 ns. In normal operation, the offtime is much longer. During the off-time, the load current is supplied by the output capacitor (C2). When
the output voltage falls sufficiently that the voltage at FB is below 2.5V, the regulation comparator initiates
a new on-time period. For stable, fixed frequency operation, a minimum of 25 mV of ripple is required at
FB to switch the regulation comparator. For a more detailed block diagram, and a complete description of
the various functional blocks, see the LM34923 80-V 600-mA Constant On-Time Buck Switching
Regulator Data Sheet (SNVS695).
3
Board Layout and Probing
The pictorial in Figure 1 shows the placement of the circuit components. The following should be kept in
mind when the board is powered:
• When operating at high input voltage and high load current, forced air flow may be necessary.
• The LM34923 may be hot to the touch when operating at high input voltage and high load current.
• Use CAUTION when probing the circuit at high input voltages to prevent injury, as well as possible
damage to the circuit.
• At maximum load current, the wire size and length used to connect the load becomes important.
Ensure there is not a significant drop in the wires between this evaluation board and the load.
4
Board Connection/Start-up
The input connections are made to the J1 connector. The load is connected to the J2 (OUT) and J3
(GND) terminals. Ensure the wires are adequately sized for the intended load current. Before start-up a
voltmeter should be connected to the input terminals, and to the output terminals. The load current should
be monitored with an ammeter or a current probe. It is recommended that the input voltage be increased
gradually to 6V, at which time the output voltage should be 5V. If the output voltage is correct with 6V at
VIN, then increase the input voltage as desired and proceed with evaluating the circuit. DO NOT EXCEED
75V AT VIN.
5
Output Ripple Control
The LM34923 requires a minimum of 25 mVp-p ripple at the FB pin, in phase with the switching waveform
at the SW pin, for proper operation. The required ripple can be supplied from ripple at VOUT, through the
feedback resistors as described in Section 5.1. Section 5.2 and Section 5.3 provide lower output ripple
with one or two additional components.
5.1
Option A) Lowest Cost Configuration
In this configuration R7 is installed in series with the output capacitance (C2). Since ≥25 mVp-p are
required at the FB pin, R7 must be chosen to generate ≥50 mVp-p at VOUT, knowing that the minimum
ripple current in this circuit is ≊51 mAp-p at minimum VIN. Using 1Ω for R7, the ripple at VOUT ranges from
≊51 mVp-p to ≊280 mVp-p over the input voltage range. If the application can accept this ripple level, this
is the most economical solution. The circuit is shown in Figure 2, see Figure 8. R8, C6, C7, and C8 are
not used in this configuration.
2
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Output Ripple Control
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VCC
C3
1 PF
LM34923
BST
0.01 PF
C4
L1 82 PH
VOUT
5V
SW
D1
R7
1:
R5
3.01 k:
C2
15 PF
FB
GND
R6
3.01 k:
RTN
Figure 2. Lowest Cost Configuration
5.2
Option B) Reduced Ripple Configuration
This configuration generates less ripple at VOUT than Section 5.1 by the addition of one capacitor (C8)
across R5, as shown in Figure 3.
VCC
LM34923
C3
1 PF
BST
0.01 PF
C4
L1 82 PH
VOUT
SW
5V
D1
C8
0.01 PF
R7
0.56:
R5
3.01k:
C2
15 PF
FB
GND
RTN
R6
3.01 k:
Figure 3. Reduced Ripple Configuration
Since the output ripple is passed by C8 to the FB pin with little or no attenuation, R7 can be reduced so
the minimum ripple at VOUT is ≊25 mVp-p. The minimum value for Cff is calculated from:
C8 !
3 x tON (max)
(R5//R6)
(2)
where tON(max) is the maximum on-time (at minimum VIN), and R5//R6 is the parallel equivalent of the
feedback resistors. The ripple at VOUT ranges from 28 mVp-p to 159 mVp-p over the input voltage range,
see Figure 8.
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3
Output Ripple Control
5.3
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Option C) Minimum Ripple Configuration
To obtain minimum ripple at VOUT, R7 is set to 0Ω, and R8, C6, and C7 are added to generate the required
ripple for the FB pin. In this configuration, the output ripple is determined primarily by the characteristics of
the output capacitance and the inductor’s ripple current, see Figure 8.
The ripple voltage required by the FB pin is generated by R8, and C6 since the SW pin switches from
–0.1V to VIN, and the right end of C6 is a virtual ground. The values for R8 and C6 are chosen to generate
a 30-100 mVp-p triangle waveform at their junction. That triangle wave is then coupled to the FB pin
through C7. The following procedure is used to calculate values for R8, C6 and C7:
1) Calculate the voltage VA:
VA = VOUT – (VSW x (1 – (VOUT/VIN)))
(3)
where VSW is the absolute value of the voltage at the SW pin during the off-time, and VIN is the minimum
input voltage. For this circuit, VA calculates to 4.98V. This is the approximate DC voltage at the R8/C6
junction, and is used in Equation 4.
2) Calculate the R8 x C6 product:
R8 x C6 =
(VIN ± VA) x tON
ÂV
(4)
where, tON is the maximum on-time, VIN is the minimum input voltage, and ΔV is the desired ripple
amplitude at the R8/C6 junction, 40 mVp-p for this example.
R8 x C6 =
(6V - 4.98V) x 4.38 Ps
-4
= 1.12 x 10
0.04
(5)
R8 and C6 are then chosen from standard value components to satisfy the above product. Typically, C6 is
3000 to 10000 pF, and R8 is 10 kΩ to 300 kΩ. C7 is chosen large compared to C6, typically 0.1 µF. The
ripple at VOUT is typically less than 10 mVp-p, see Figure 4 and Figure 8.
VCC
C3
1 PF
LM34923
BST
0.01 PF
C4
SW
L1 82 PH
VOUT
5V
R8
D1
36.5 k:
C7
0.1 PF
C6
3300 pF
R5
3.01 k:
FB
R7
0:
C2
15 PF
GND
RTN
R6
3.01 k:
Figure 4. Minimum Output Ripple Configuration
4
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Under-Voltage Detector
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Figure 5. Efficiency at 200 kHz
6
Under-Voltage Detector
The under voltage detector can be used to monitor the input voltage, or any other system voltage as long
as the voltage at the UV pin does not exceed its maximum rating. On this evaluation board, the input
voltage is monitored via resistors R2 and R3.
An appropriate pull-up voltage less than 10 volts must be connected to test point TP2-UVO on this
evaluation board. R4 is the pull-up resistor for the UVO output. The under-voltage status can then be
monitored at the TP3-Status test point.
On this evaluation board the UVO output switches low when the input voltage exceeds 12V, and it
switches high when the input voltage is less than 11V. If it is desired to change the thresholds, the
equations for determining the resistor values are:
R2 =
VUVH - VUVL
5 µA
VUV(HYS)
=
5 µA
(6)
R2 x 2.5V
R3 =
VUVL ± 2.5V
(7)
where, VUVH is the upper threshold at VIN, and VUVL is the lower threshold. The threshold at the UV pin is
2.5V.
The UVO output is high when the VCC voltage is below its UVLO threshold, or when the LM34923 is
shutdown by grounding the TP1-SD test point, regardless of the voltage at the UV pin.
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5
Monitor the Inductor Current
6V to 75V
Input
VIN
C1
2.2 PF
GND
C5
0.1
PF
R1
191 k:
TP1
SD
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VIN
VCC
LM34923
BST
RT/SD
R2
200 k:
TP2
UVO
R4
100 k:
TP3
STATUS
C9
1000 pF
C3
1 PF
0.01
PF
C4
SW
R3
59 k:
FB
UVO
L1 82 PH
VOUT
5V
R9 0:
R8
D1
UV
SW
Scope TP4
36.5 k:
3300
C6 pF
C7
0.1 PF
RTN
C8
R5
3.01 k:
R7
0:
C2
15 PF
VOUT
Scope
TP5
R6
3.01 k:
GND
Figure 6. Complete Evaluation Board Schematic (As Supplied)
7
Monitor the Inductor Current
The inductor’s current can be monitored or viewed on a scope with a current probe. Remove R9, and
install an appropriate current loop across the two large pads where R9 was located. In this way the
inductor’s ripple current and peak current can be accurately determined.
8
Scope Probe Adapters
Scope probe adapters are provided on this evaluation board for monitoring the waveform at the SW pin,
and at the circuit’s output (VOUT), without using the probe’s ground lead that can pick up noise from the
switching waveforms.
6
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Scope Probe Adapters
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8.1
Bill of Materials (BOM)
Table 1. Bill of Materials (BOM)
Item
Description
Mfg., Part Number
Package
Value
C1
C2
Ceramic Capacitor
TDK C3225X7R2A225M
1210
2.2 µF, 100V
Ceramic Capacitor
TDK C3225X7R1C156M
1210
15 µF, 16V
C3
Ceramic Capacitor
TDK C1608X7R1C105K
0603
1 µF, 16V
C4
Ceramic Capacitor
TDK C1608X7R2A103K
0603
0.01 µF, 100V
C5
Ceramic Capacitor
TDK C2012X7R2A104M
0805
0.1 µF, 100V
C6
Ceramic Capacitor
TDK C1608X7R2A332K
0603
3300 pF, 100V
C7
Ceramic Capacitor
TDK C2012X7R2A104M
0805
0.1 µF, 100V
C8
Unpopulated
C9
Ceramic Capacitor
TDK C1608X7R2A102K
0805
1000 pF, 100V
L1
Inductor
Coiltronics DR74-820-R or Wurth Electronics 744771182
D1
Schottky Rectifier
Diodes Inc DFLS1100
Power DI123
100V, 1.0A
R1
Resistor
Vishay CRCW0603191KF
0603
191kΩ
R2
Resistor
Vishay CRCW0603200KF
0603
200kΩ
R3
Resistor
Vishay CRCW060359KOF
0603
59 kΩ
R4
Resistor
Vishay CRCW0603100KF
0603
100 kΩ
R5
Resistor
Vishay CRCW06033KO1F
0603
3.01 kΩ
R6
Resistor
Vishay CRCW06033KO1F
0603
3.01 kΩ
R7
Resistor
Vishay CRCW06030000Z
0603
0Ω jumper
R8
Resistor
Vishay CRCW060336K5F
0603
36.5 kΩ
R9
Resistor
Vishay CRCW06030000Z
0603
0Ω jumper
U1
Switching Regulator
LM34923
VSSOP-10
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7
Circuit Performance
9
8
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Circuit Performance
Figure 7. Output Voltage Ripple
Figure 8. Switching Frequency vs. Input Voltage
Figure 9. Current Limit vs. Input Voltage
Figure 10. Line Regulation
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Typical Waveforms
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Figure 11. Load Regulation
10
Typical Waveforms
Trace 1 = SW Pin
Trace 2 = VOUT
Trace 4 = Inductor Current
Vin = 12V, Iout = 200 mA
Figure 12. Typical Waveforms
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9
PC Board Layout
11
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PC Board Layout
Figure 13. Board Silkscreen
Figure 14. Board Top Layer
10
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PC Board Layout
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Figure 15. Board Bottom Layer (Viewed from Top)
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