LMC6001
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SNOS694F – MAY 2004 – REVISED NOVEMBER 2009
LMC6001 Ultra Ultra-Low Input Current Amplifier
Check for Samples: LMC6001
FEATURES
DESCRIPTION
•
•
•
•
•
•
Featuring 100% tested input currents of 25 fA max.,
low operating power, and ESD protection of 2000V,
the LMC6001 achieves a new industry benchmark for
low input current operational amplifiers. By tightly
controlling the molding compound, Texas Instruments
is able to offer this ultra-low input current in a lower
cost molded package.
1
2
(Max limit, 25°C unless otherwise noted)
Input Current (100% tested): 25 fA
Input Current over Temp.: 2 pA
Low Power: 750 μA
Low VOS: 350 μV
Low Noise: 22 nV/√Hz @1 kHz Typ.
APPLICATIONS
•
•
•
•
Electrometer Amplifier
Photodiode Preamplifier
Ion Detector
A.T.E. Leakage Testing
To avoid long turn-on settling times common in other
low input current opamps, the LMC6001A is tested 3
times in the first minute of operation. Even units that
meet the 25 fA limit are rejected if they drift.
Because of the ultra-low input current noise of 0.13
fA/√Hz, the LMC6001 can provide almost noiseless
amplification of high resistance signal sources.
Adding only 1 dB at 100 kΩ, 0.1 dB at 1 MΩ and 0.01
dB or less from 10 MΩ to 2,000 MΩ, the LMC6001 is
an almost noiseless amplifier.
The LMC6001 is ideally suited for electrometer
applications requiring ultra-low input leakage such as
sensitive photodetection transimpedance amplifiers
and sensor amplifiers. Since input referred noise is
only 22 nV/√Hz, the LMC6001 can achieve higher
signal to noise ratio than JFET input type
electrometer amplifiers. Other applications of the
LMC6001 include long interval integrators, ultra-high
input impedance instrumentation amplifiers, and
sensitive electrical-field measurement circuits.
Connection Diagram
Figure 1. 8-Pin PDIP (Top View)
See P Package
Figure 2. 8-Pin TO-99 (Top View)
See LMC Package
These devices have limited built-in ESD protection. The leads should be shorted together or the device placed in conductive foam
during storage or handling to prevent electrostatic damage to the MOS gates.
1
2
Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of
Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet.
All trademarks are the property of their respective owners.
PRODUCTION DATA information is current as of publication date.
Products conform to specifications per the terms of the Texas
Instruments standard warranty. Production processing does not
necessarily include testing of all parameters.
Copyright © 2004–2009, Texas Instruments Incorporated
LMC6001
SNOS694F – MAY 2004 – REVISED NOVEMBER 2009
www.ti.com
Absolute Maximum Ratings (1) (2)
Differential Input Voltage
±Supply Voltage
(V+) + 0.3V, (V−) − 0.3V
Voltage at Input/Output Pin
Supply Voltage (V+ − V−)
−0.3V to +16V
Output Short Circuit to V+
See (3) (4)
−
See (3)
Output Short Circuit to V
(Soldering, 10 Sec.) Lead Temperature
260°C
−65°C to +150°C
Storage Temperature
Junction Temperature
150°C
Current at Input Pin
±10 mA
Current at Output Pin
±30 mA
Current at Power Supply Pin
40 mA
Power Dissipation
See (5)
(5)
2 kV
ESD Tolerance
(1)
(2)
(3)
(4)
(5)
Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for
which the device is intended to be functional but do not guarantee specific performance limits. For guaranteed specifications and test
conditions, see the Electrical Characteristics. The guaranteed specifications apply only for the test conditions listed.
If Military/Aerospace specified devices are required, please contact the Texas Instruments Sales Office/ Distributors for availability and
specifications.
Applies to both single supply and split supply operation. Continuous short circuit operation at elevated ambient temperature can result in
exceeding the maximum allowed junction temperature of 150°C. Output currents in excess of ±30 mA over long term may adversely
affect reliability.
Do not connect the output to V+, when V+ is greater than 13V or reliability will be adversely affected.
Human body model, 1.5 kΩ in series with 100 pF.
Operating Ratings (1)
−40°C ≤ TJ ≤ +85°C
Temperature Range (LMC6001AI, LMC6001BI, LMC6001CI)
4.5V ≤ V+ ≤ 15.5V
Supply Voltage
Thermal Resistance
(2)
θJA, P Package
100°C/W
θJA, LMC Package
145°C/W
θJC, LMC Package
45°C/W
See (3)
Power Dissipation
(1)
(2)
(3)
2
Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for
which the device is intended to be functional but do not guarantee specific performance limits. For guaranteed specifications and test
conditions, see the Electrical Characteristics. The guaranteed specifications apply only for the test conditions listed.
All numbers apply for packages soldered directly into a printed circuit board.
For operating at elevated temperatures the device must be derated based on the thermal resistance θJA with PD = (TJ − TA)/θJA.
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DC Electrical Characteristics
Limits in standard typeface guaranteed for TJ = 25°C and limits in boldface type apply at the temperature extremes. Unless
otherwise specified, V+ = 5V, V− = 0V, VCM = 1.5V, and RL > 1M.
Symbol
IB
Conditions
Parameter
Input Current
IOS
Input Offset Current
VOS
Input Offset Voltage
Either Input, VCM = 0V, VS =
±5V
Typical (1)
Limits (2)
LMC6001AI
10
5
VS = ±5V, VCM = 0V
TCVOS
Input Offset Voltage Drift
2.5
RIN
Input Resistance
>1
CMRR
Common Mode
+PSRR
0V ≤ VCM ≤ 7.5V
83
V = 10V
Positive Power Supply
5V ≤ V+ ≤ 15V
Negative Power
Large Signal Voltage
Gain
Sourcing, RL = 2 kΩ (3)
Sinking, RL = 2 kΩ
VCM
VO
Input Common-Mode
Voltage
Output Swing
(3)
V+ = 5V and 15V For CMRR
≥ 60 dB
V+ = 5V
RL = 2 kΩ to 2.5V
Output Current
Sourcing, V+ = 5V, VO = 0V
(1)
(2)
(3)
(4)
0.35
1.0
1.0
1.0
1.7
2.0
0.7
1.35
1.35
1.35
2.0
10
10
66
63
63
94
80
74
74
77
71
71
1400
400
300
300
300
200
200
350
180
90
90
100
60
60
−0.4
−0.1
−0.1
−0.1
0
0
0
V+ − 1.9
V+ − 2.3
V+ − 2.3
V+ − 2.3
V+ − 2.5
V+ − 2.5
V+ − 2.5
4.80
4.75
4.75
4.73
4.67
4.67
0.14
0.20
0.20
0.17
0.24
0.24
14.50
14.37
14.37
14.34
14.25
14.25
0.35
0.44
0.44
0.45
0.56
0.56
16
13
13
10
8
8
16
13
13
13
10
10
28
23
23
22
18
18
28
23
23
22
18
18
14.63
22
Sourcing, V+ = 15V, VO = 0V
30
34
fA
mV
μV/°C
70
4.87
Units
Tera Ω
63
21
Sinking, V = 15V, VO =
13V (4)
2000
66
Sinking, V+ = 5V, VO = 5V
+
2000
68
0.26
IO
4000
1000
73
0.10
V+ = 15V
RL = 2 kΩ to 7.5V
1000
72
Supply Rejection Ratio
AV
100
4000
66
83
0V ≥ V− ≥ −10V
25
2000
72
Rejection Ratio
−PSRR
LMC6001CI
75
+
Rejection Ratio
LMC6001BI
dB
min
V/mV
min
V
max
V
min
V
min
V
max
V
min
V
max
mA
min
Typical values represent the most likely parametric norm.
All limits are guaranteed by testing or statistical analysis.
V+ = 15V, VCM = 7.5V and RL connected to 7.5V. For Sourcing tests, 7.5V ≤ VO ≤ 11.5V. For Sinking tests, 2.5V ≤ VO ≤ 7.5V.
Do not connect the output to V+, when V+ is greater than 13V or reliability will be adversely affected.
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DC Electrical Characteristics (continued)
Limits in standard typeface guaranteed for TJ = 25°C and limits in boldface type apply at the temperature extremes. Unless
otherwise specified, V+ = 5V, V− = 0V, VCM = 1.5V, and RL > 1M.
Symbol
IS
Conditions
Parameter
Supply Current
V+ = 5V, VO = 1.5V
V+ = 15V, VO = 7.5V
Typical (1)
Limits (2)
LMC6001AI
LMC6001BI
LMC6001CI
750
750
750
900
900
900
850
850
850
950
950
950
450
550
Units
μA
max
AC Electrical Characteristics
Limits in standard typeface guaranteed for TJ = 25°C and limits in boldface type apply at the temperature extremes. Unless
otherwise specified, V+ = 5V, V− = 0V, VCM = 1.5V and RL > 1M.
Symbol
Parameter
Conditions
See (3)
Typical (1)
LM6001AI
LM6001BI
LM6001CI
0.8
0.8
0.8
0.6
0.6
0.6
Units
SR
Slew Rate
GBW
Gain-Bandwidth Product
1.3
MHz
φfm
Phase Margin
50
Deg
GM
Gain Margin
17
dB
en
Input-Referred Voltage Noise
F = 1 kHz
22
nV/√Hz
in
Input-Referred Current Noise
F = 1 kHz
0.13
fA/√Hz
THD
Total Harmonic Distortion
F = 10 kHz, AV = −10,
RL = 100 kΩ,
VO = 8 VPP
0.01
(1)
(2)
(3)
4
1.5
Limits (2)
V/μs
min
%
Typical values represent the most likely parametric norm.
All limits are guaranteed by testing or statistical analysis.
V+ = 15V. Connected as Voltage Follower with 10V step input. Limit specified is the lower of the positive and negative slew rates.
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Typical Performance Characteristics
VS = ±7.5V, TA = 25°C, unless otherwise specified
Input Current
vs.
Temperature
Input Current
vs.
VCM VS = ±5V
INPUT BIAS CURRENT
100 pA
10 pA
1 pA
100 fA
10 fA
1 fA
0
25
50
75
100
TEMPERATURE (°C)
125
Figure 3.
Figure 4.
Supply Current
vs.
Supply Voltage
Input Voltage vs.Output Voltage
Figure 5.
Figure 6.
Common Mode Rejection Ratio
vs.
Frequency
Power Supply Rejection Ratio
vs.
Frequency
Figure 7.
Figure 8.
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Typical Performance Characteristics (continued)
VS = ±7.5V, TA = 25°C, unless otherwise specified
6
Input Voltage Noise
vs.
Frequency
Noise Figure
vs.
Source Resistance
Figure 9.
Figure 10.
Output Characteristics Sourcing Current
Output Characteristics Sinking Current
Figure 11.
Figure 12.
Gain and Phase Response
vs.
Temperature
(−55°C to +125°C)
Gain and Phase Response
vs.
Capacitive Load
with RL = 500 kΩ
Figure 13.
Figure 14.
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Typical Performance Characteristics (continued)
VS = ±7.5V, TA = 25°C, unless otherwise specified
Open Loop Frequency Response
Inverting Small Signal Pulse Response
Figure 15.
Figure 16.
Inverting Large Signal Pulse Response
Non-Inverting Small Signal Pulse Response
Figure 17.
Figure 18.
Non-Inverting Large Signal Pulse Response
Stability
vs.
Capacitive Load
Figure 19.
Figure 20.
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APPLICATIONS HINTS
AMPLIFIER TOPOLOGY
The LMC6001 incorporates a novel op-amp design topology that enables it to maintain rail-to-rail output swing
even when driving a large load. Instead of relying on a push-pull unity gain output buffer stage, the output stage
is taken directly from the internal integrator, which provides both low output impedance and large gain. Special
feed-forward compensation design techniques are incorporated to maintain stability over a wider range of
operating conditions than traditional op-amps. These features make the LMC6001 both easier to design with, and
provide higher speed than products typically found in this low power class.
COMPENSATING FOR INPUT CAPACITANCE
It is quite common to use large values of feedback resistance for amplifiers with ultra-low input current, like the
LMC6001.
Although the LMC6001 is highly stable over a wide range of operating conditions, certain precautions must be
met to achieve the desired pulse response when a large feedback resistor is used. Large feedback resistors with
even small values of input capacitance, due to transducers, photodiodes, and circuit board parasitics, reduce
phase margins.
When high input impedances are demanded, guarding of the LMC6001 is suggested. Guarding input lines will
not only reduce leakage, but lowers stray input capacitance as well. See PRINTED-CIRCUIT-BOARD LAYOUT
FOR HIGH-IMPEDANCE WORK.
The effect of input capacitance can be compensated for by adding a capacitor, Cf, around the feedback resistors
(as in Figure 21) such that:
(1)
or
R1 CIN ≤ R2 Cf
(2)
Since it is often difficult to know the exact value of CIN, Cf can be experimentally adjusted so that the desired
pulse response is achieved. Refer to the LMC660 and LMC662 for a more detailed discussion on compensating
for input capacitance.
Figure 21. Cancelling the Effect of Input Capacitance
CAPACITIVE LOAD TOLERANCE
All rail-to-rail output swing operational amplifiers have voltage gain in the output stage. A compensation capacitor
is normally included in this integrator stage. The frequency location of the dominant pole is affected by the
resistive load on the amplifier. Capacitive load driving capability can be optimized by using an appropriate
resistive load in parallel with the capacitive load. See Typical Performance Characteristics.
Direct capacitive loading will reduce the phase margin of many op-amps. A pole in the feedback loop is created
by the combination of the op-amp's output impedance and the capacitive load. This pole induces phase lag at the
unity-gain crossover frequency of the amplifier resulting in either an oscillatory or underdamped pulse response.
With a few external components, op amps can easily indirectly drive capacitive loads, as shown in Figure 22.
8
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Figure 22. LMC6001 Noninverting Gain of 10 Amplifier, Compensated to Handle Capacitive Loads
In the circuit of Figure 22, R1 and C1 serve to counteract the loss of phase margin by feeding the high frequency
component of the output signal back to the amplifier's inverting input, thereby preserving phase margin in the
overall feedback loop.
Capacitive load driving capability is enhanced by using a pullup resistor to V+ (Figure 23). Typically a pullup
resistor conducting 500 μA or more will significantly improve capacitive load responses. The value of the pullup
resistor must be determined based on the current sinking capability of the amplifier with respect to the desired
output swing. Open loop gain of the amplifier can also be affected by the pullup resistor. See DC Electrical
Characteristics.
Figure 23. Compensating for Large Capacitive Loads with a Pullup Resistor
PRINTED-CIRCUIT-BOARD LAYOUT FOR HIGH-IMPEDANCE WORK
It is generally recognized that any circuit which must operate with less than 1000 pA of leakage current requires
special layout of the PC board. When one wishes to take advantage of the ultra-low bias current of the
LMC6001, typically less than 10 fA, it is essential to have an excellent layout. Fortunately, the techniques of
obtaining low leakages are quite simple. First, the user must not ignore the surface leakage of the PC board,
even though it may sometimes appear acceptably low, because under conditions of high humidity or dust or
contamination, the surface leakage will be appreciable.
To minimize the effect of any surface leakage, lay out a ring of foil completely surrounding the LMC6001's inputs
and the terminals of capacitors, diodes, conductors, resistors, relay terminals, etc., connected to the op-amp's
inputs, as in Figure 24. To have a significant effect, guard rings should be placed on both the top and bottom of
the PC board. This PC foil must then be connected to a voltage which is at the same voltage as the amplifier
inputs, since no leakage current can flow between two points at the same potential. For example, a PC board
trace-to-pad resistance of 1012Ω, which is normally considered a very large resistance, could leak 5 pA if the
trace were a 5V bus adjacent to the pad of the input.
This would cause a 500 times degradation from the LMC6001's actual performance. If a guard ring is used and
held within 1 mV of the inputs, then the same resistance of 1012Ω will only cause 10 fA of leakage current. Even
this small amount of leakage will degrade the extremely low input current performance of the LMC6001. See
Figure 27 for typical connections of guard rings for standard op-amp configurations.
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Figure 24. Examples of Guard
Ring in PC Board Layout
Figure 25. Inverting Amplifier
Figure 26. Non-Inverting Amplifier
Figure 27. Typical Connections of Guard Rings
The designer should be aware that when it is inappropriate to lay out a PC board for the sake of just a few
circuits, there is another technique which is even better than a guard ring on a PC board: Don't insert the
amplifier's input pin into the board at all, but bend it up in the air and use only air as an insulator. Air is an
excellent insulator. In this case you may have to forego some of the advantages of PC board construction, but
the advantages are sometimes well worth the effort of using point-to-point up-in-the-air wiring. See Figure 28.
10
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(Input pins are lifted out of PC board and soldered directly to components. All other pins connected to PC board).
Figure 28. Air Wiring
Another potential source of leakage that might be overlooked is the device package. When the LMC6001 is
manufactured, the device is always handled with conductive finger cots. This is to assure that salts and skin oils
do not cause leakage paths on the surface of the package. We recommend that these same precautions be
adhered to, during all phases of inspection, test and assembly.
LATCHUP
CMOS devices tend to be susceptible to latchup due to their internal parasitic SCR effects. The (I/O) input and
output pins look similar to the gate of the SCR. There is a minimum current required to trigger the SCR gate
lead. The LMC6001 is designed to withstand 100 mA surge current on the I/O pins. Some resistive method
should be used to isolate any capacitance from supplying excess current to the I/O pins. In addition, like an SCR,
there is a minimum holding current for any latchup mode. Limiting current to the supply pins will also inhibit
latchup susceptibility.
Typical Applications
The extremely high input resistance, and low power consumption, of the LMC6001 make it ideal for applications
that require battery-powered instrumentation amplifiers. Examples of these types of applications are hand-held
pH probes, analytic medical instruments, electrostatic field detectors and gas chromotographs.
TWO OPAMP, TEMPERATURE COMPENSATED pH PROBE AMPLIFIER
The signal from a pH probe has a typical resistance between 10 MΩ and 1000 MΩ. Because of this high value, it
is very important that the amplifier input currents be as small as possible. The LMC6001 with less than 25 fA
input current is an ideal choice for this application.
The theoretical output of the standard Ag/AgCl pH probe is 59.16 mV/pH at 25°C with 0V out at a pH of 7.00.
This output is proportional to absolute temperature. To compensate for this, a temperature compensating
resistor, R1, is placed in the feedback loop. This cancels the temperature dependence of the probe. This resistor
must be mounted where it will be at the same temperature as the liquid being measured.
The LMC6001 amplifies the probe output providing a scaled voltage of ±100 mV/pH from a pH of 7. The second
opamp, a micropower LMC6041 provides phase inversion and offset so that the output is directly proportional to
pH, over the full range of the probe. The pH reading can now be directly displayed on a low cost, low power
digital panel meter. Total current consumption will be about 1 mA for the whole system.
The micropower dual operational amplifier, LMC6042, would optimize power consumption but not offer these
advantages:
1. The LMC6001A guarantees a 25 fA limit on input current at 25°C.
2. The input ESD protection diodes in the LMC6042 are only rated at 500V while the LMC6001 has much more
robust protection that is rated at 2000V.
The setup and calibration is simple with no interactions to cause problems.
1. Disconnect the pH probe and with R3 set to about mid-range and the noninverting input of the LMC6001
grounded, adjust R8 until the output is 700 mV.
2. Apply −414.1 mV to the noninverting input of the LMC6001. Adjust R3 for and output of 1400 mV. This
completes the calibration. As real pH probes may not perform exactly to theory, minor gain and offset
adjustments should be made by trimming while measuring a precision buffer solution.
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R1 100k + 3500 ppm/°C
R2 68.1k
R3, 8 5k
R4, 9 100k
R5 36.5k
R6 619k
R7 97.6k
D1 LM4040D1Z-2.5
C1 2.2 μF
(1)
Micro-ohm style 137 or similar
Figure 29. pH Probe Amplifier
ULTRA-LOW INPUT CURRENT INSTRUMENTATION AMPLIFIER
Figure 30 shows an instrumentation amplifier that features high differential and common mode input resistance
(>1014Ω), 0.01% gain accuracy at AV = 1000, excellent CMRR with 1 MΩ imbalance in source resistance. Input
current is less than 20 fA and offset drift is less than 2.5 μV/°C. R2 provides a simple means of adjusting gain
over a wide range without degrading CMRR. R7 is an initial trim used to maximize CMRR without using super
precision matched resistors. For good CMRR over temperature, low drift resistors should be used.
If R1 = R5, R3 = R6, and R4 = R7; then
∴AV ≈ 100 for circuit shown (R2 = 9.85k).
Figure 30. Instrumentation Amplifier
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PACKAGE OPTION ADDENDUM
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9-Mar-2013
PACKAGING INFORMATION
Orderable Device
Status
(1)
Package Type Package Pins Package Qty
Drawing
Eco Plan
Lead/Ball Finish
(2)
MSL Peak Temp
Op Temp (°C)
Top-Side Markings
(3)
(4)
LMC6001AIN
ACTIVE
PDIP
P
8
40
TBD
Call TI
Call TI
-40 to 85
LMC6001
AIN
LMC6001AIN/NOPB
ACTIVE
PDIP
P
8
40
Green (RoHS
& no Sb/Br)
SN
Level-1-NA-UNLIM
-40 to 85
LMC6001
AIN
LMC6001BIN
ACTIVE
PDIP
P
8
40
TBD
Call TI
Call TI
-40 to 85
LMC6001
BIN
LMC6001BIN/NOPB
ACTIVE
PDIP
P
8
40
Green (RoHS
& no Sb/Br)
SN
Level-1-NA-UNLIM
-40 to 85
LMC6001
BIN
(1)
The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2)
Eco Plan - The planned eco-friendly classification: Pb-Free (RoHS), Pb-Free (RoHS Exempt), or Green (RoHS & no Sb/Br) - please check http://www.ti.com/productcontent for the latest availability
information and additional product content details.
TBD: The Pb-Free/Green conversion plan has not been defined.
Pb-Free (RoHS): TI's terms "Lead-Free" or "Pb-Free" mean semiconductor products that are compatible with the current RoHS requirements for all 6 substances, including the requirement that
lead not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, TI Pb-Free products are suitable for use in specified lead-free processes.
Pb-Free (RoHS Exempt): This component has a RoHS exemption for either 1) lead-based flip-chip solder bumps used between the die and package, or 2) lead-based die adhesive used between
the die and leadframe. The component is otherwise considered Pb-Free (RoHS compatible) as defined above.
Green (RoHS & no Sb/Br): TI defines "Green" to mean Pb-Free (RoHS compatible), and free of Bromine (Br) and Antimony (Sb) based flame retardants (Br or Sb do not exceed 0.1% by weight
in homogeneous material)
(3)
MSL, Peak Temp. -- The Moisture Sensitivity Level rating according to the JEDEC industry standard classifications, and peak solder temperature.
(4)
Only one of markings shown within the brackets will appear on the physical device.
Important Information and Disclaimer:The information provided on this page represents TI's knowledge and belief as of the date that it is provided. TI bases its knowledge and belief on information
provided by third parties, and makes no representation or warranty as to the accuracy of such information. Efforts are underway to better integrate information from third parties. TI has taken and
continues to take reasonable steps to provide representative and accurate information but may not have conducted destructive testing or chemical analysis on incoming materials and chemicals.
TI and TI suppliers consider certain information to be proprietary, and thus CAS numbers and other limited information may not be available for release.
In no event shall TI's liability arising out of such information exceed the total purchase price of the TI part(s) at issue in this document sold by TI to Customer on an annual basis.
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9-Mar-2013
Addendum-Page 2
IMPORTANT NOTICE
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Products
Applications
Audio
www.ti.com/audio
Automotive and Transportation
www.ti.com/automotive
Amplifiers
amplifier.ti.com
Communications and Telecom
www.ti.com/communications
Data Converters
dataconverter.ti.com
Computers and Peripherals
www.ti.com/computers
DLP® Products
www.dlp.com
Consumer Electronics
www.ti.com/consumer-apps
DSP
dsp.ti.com
Energy and Lighting
www.ti.com/energy
Clocks and Timers
www.ti.com/clocks
Industrial
www.ti.com/industrial
Interface
interface.ti.com
Medical
www.ti.com/medical
Logic
logic.ti.com
Security
www.ti.com/security
Power Mgmt
power.ti.com
Space, Avionics and Defense
www.ti.com/space-avionics-defense
Microcontrollers
microcontroller.ti.com
Video and Imaging
www.ti.com/video
RFID
www.ti-rfid.com
OMAP Applications Processors
www.ti.com/omap
TI E2E Community
e2e.ti.com
Wireless Connectivity
www.ti.com/wirelessconnectivity
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