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LMC6035/LMC6035-Q1/LMC6036 Low Power 2.7V Single Supply CMOS Operational
Amplifiers
Check for Samples: LMC6035, LMC6036
FEATURES
APPLICATIONS
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2
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(Typical Unless Otherwise Noted)
LMC6035 in DSBGA Package
Ensured 2.7V, 3V, 5V and 15V Performance
Specified for 2 kΩ and 600Ω Loads
Wide Operating Range: 2.0V to 15.5V
Ultra Low Input Current: 20fA
Rail-to-Rail Output Swing
– @ 600Ω: 200mV from Either Rail at 2.7V
– @ 100kΩ: 5mV from Either Rail at 2.7V
High Voltage Gain: 126dB
Wide Input Common-Mode Voltage Range
–
-0.1V to 2.3V at VS = 2.7V
Low Distortion: 0.01% at 10kHz
LMC6035 Dual LMC6036 Quad
See AN-1112 (Literature Number SNVA009) for
DSBGA Considerations
AEC-Q100 Grade 3 Qualified (LMC6035-Q1)
Filters
High Impedance Buffer or Preamplifier
Battery Powered Electronics
Medical Instrumentation
Automotive Applications
DESCRIPTION
The LMC6035/6 is an economical, low voltage op
amp capable of rail-to-rail output swing into loads of
600Ω. LMC6035 is available in a chip sized package
(8-Bump DSBGA) using micro SMD package
technology. Both allow for single supply operation
and are ensured for 2.7V, 3V, 5V and 15V supply
voltage. The 2.7 supply voltage corresponds to the
End-of-Life voltage (0.9V/cell) for three NiCd or NiMH
batteries in series, making the LMC6035/6 well suited
for portable and rechargeable systems. It also
features a well behaved decrease in its specifications
at supply voltages below its ensured 2.7V operation.
This provides a “comfort zone” for adequate operation
at voltages significantly below 2.7V. Its ultra low input
currents (IIN) makes it well suited for low power active
filter application, because it allows the use of higher
resistor values and lower capacitor values. In
addition, the drive capability of the LMC6035/6 gives
these op amps a broad range of applications for low
voltage systems.
Connection Diagram
Top View
Figure 1. 8-Bump DSBGA Package
(Bump Side Down)
See Package Number YZR0008
1
2
Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of
Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet.
All trademarks are the property of their respective owners.
PRODUCTION DATA information is current as of publication date.
Products conform to specifications per the terms of the Texas
Instruments standard warranty. Production processing does not
necessarily include testing of all parameters.
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Table 1. DSBGA Connection Table
LM6035IBP
LMC6035IBPX
Bump Number
A1
OUTPUT A
B1
LMC6035ITL
LMC6035ITLX
OUTPUT B
−
V+
+
IN A
C1
IN A
OUTPUT A
C2
V−
IN A−
C3
+
IN A+
−
IN B
B3
IN B
V−
A3
OUTPUT B
IN B+
A2
V+
IN B−
These devices have limited built-in ESD protection. The leads should be shorted together or the device placed in conductive foam
during storage or handling to prevent electrostatic damage to the MOS gates.
Absolute Maximum Ratings (1) (2)
ESD Tolerance (3)
Human Body Model (LMC6035, LMC6036)
3000V
Human Body Model (LMC6035-Q1)
2000V
Machine Model
300V
Differential Input Voltage
± Supply Voltage
Supply Voltage (V+ − V−)
16V
Output Short Circuit to V
+
See (4)
Output Short Circuit to V
−
See (5)
Lead Temperature (soldering, 10 sec.)
260°C
Current at Output Pin
±18mA
Current at Input Pin
±5mA
Current at Power Supply Pin
35mA
Storage Temperature Range
−65°C to +150°C
Junction Temperature (6)
(1)
(2)
(3)
(4)
(5)
(6)
150°C
Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for
which the device is intended to be functional, but specific performance is not ensured. For ensured specifications and the test
conditions, see the Electrical Characteristics.
If Military/Aerospace specified devices are required, please contact the TI Sales Office/ Distributors for availability and specifications.
Human body model, 1.5kΩ in series with 100pF.
Do not short circuit output to V+ when V+ is greater than 13V or reliability will be adversely affected.
Applies to both single-supply and split-supply operation. Continuous short circuit operation at elevated ambient temperature can result in
exceeding the maximum allowed junction temperature of 150°C. Output currents in excess of 30mA over long term may adversely affect
reliability.
The maximum power dissipation is a function of TJ(MAX), θJA, and TA. The maximum allowable power dissipation at any ambient
temperature is PD = (TJ(MAX) −TA)/θ JA. All numbers apply for packages soldered directly onto a PC board with no air flow.
Operating Ratings (1)
Supply Voltage
2.0V to 15.5V
−40°C ≤ T J ≤ +85°C
Temperature Range
LMC6035I and LMC6036I
Thermal Resistance (θJA)
8-pin VSSOP
230°C/W
8-pin SOIC
175°C/W
14-pin SOIC
127°C/W
14-pin TSSOP
137°C/W
8-Bump (6 mil) DSBGA
220°C/W
8-Bump (12 mil) Thin DSBGA
220°C/W
(1)
2
Absolute Maximum Ratings indicate limits beyond which damage to the device may occur. Operating Ratings indicate conditions for
which the device is intended to be functional, but specific performance is not ensured. For ensured specifications and the test
conditions, see the Electrical Characteristics.
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DC Electrical Characteristics
Unless otherwise specified, all limits ensured for TJ = 25°C, V+ = 2.7V, V− = 0V, VCM = 1.0V, VO = 1.35V and RL > 1MΩ.
Boldface limits apply at the temperature extremes.
Parameter
LMC6035I/LMC6036I
Test Conditions
Min (1)
Typ (2)
Max (1)
5
6
Units
VOS
Input Offset Voltage
0.5
TCVOS
Input Offset Voltage
Average Drift
2.3
IIN
Input Current
See (3)
0.02
90
pA
IOS
Input Offset Current
See (3)
0.01
45
PA
RIN
Input Resistance
CMRR
Common Mode Rejection Ratio
0.7V ≤ VCM ≤ 12.7V,
V+ = 15V
+PSRR
Positive Power Supply
Rejection Ratio
−PSRR
VCM
Tera Ω
63
60
96
dB
5V ≤ V+ ≤ 15V,
VO = 2.5V
63
60
93
dB
Negative Power Supply
Rejection Ratio
0V ≤ V− ≤ −10V,
VO = 2.5V, V+ = 5V
74
70
97
dB
Input Common-Mode Voltage
Range
V+ = 2.7V
For CMRR ≥ 40dB
−0.1
V+ = 3V
For CMRR ≥ 40dB
V+ = 5V
For CMRR ≥ 50dB
V+ = 15V
For CMRR ≥ 50dB
Large Signal Voltage Gain (4)
RL = 600Ω
RL = 2kΩ
V
0.1
0.3
V
2.6
−0.5
4.2
3.9
0.3
0.5
2.3
−0.3
2.3
2.0
(1)
(2)
(3)
(4)
μV/°C
> 10
2.0
1.7
AV
mV
−0.2
0.0
V
4.5
−0.5
−0.2
0.0
V
14.0
13.7
14.4
Sourcing
100
75
1000
V/mV
Sinking
25
20
250
V/mV
Sourcing
2000
V/mV
Sinking
500
V/mV
All limits are specified by testing or statistical analysis.
Typical Values represent the most likely parametric norm or one sigma value.
Ensured by design.
V+ = 15V, VCM = 7.5V and R L connected to 7.5V. For Sourcing tests, 7.5V ≤ VO ≤ 11.5V. For Sinking tests, 3.5V ≤ VO ≤ 7.5V.
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DC Electrical Characteristics (continued)
Unless otherwise specified, all limits ensured for TJ = 25°C, V+ = 2.7V, V− = 0V, VCM = 1.0V, VO = 1.35V and RL > 1MΩ.
Boldface limits apply at the temperature extremes.
Parameter
VO
LMC6035I/LMC6036I
Test Conditions
V + = 2.7V
RL = 600Ω to 1.35V
Output Swing
Min (1)
Typ (2)
2.0
1.8
2.5
0.2
V + = 2.7V
RL = 2kΩ to 1.35V
2.4
2.2
13.5
13.0
14.2
13.5
Output Current
IS
Supply Current
V
0.2
0.4
V
1.25
1.50
14.8
0.12
IO
V
0.5
0.7
14.5
0.36
V + = 15V,
RL = 2 kΩ to 7.5V
Units
2.62
0.07
V + = 15V
RL = 600Ω to 7.5V
Max (1)
V O = 0V
Sourcing
4
3
8
V O = 2.7V
Sinking
3
2
5
V
0.4
0.5
mA
LMC6035 for Both Amplifiers
V O = 1.35V
0.65
1.6
1.9
LMC6036 for All Four Amplifiers
V O = 1.35V
1.3
2.7
3.0
mA
AC Electrical Characteristics
Unless otherwise specified, all limits ensured for TJ = 25°C, V+ = 2.7V, V− = 0V, VCM = 1.0V, V O = 1.35V and RL > 1 MΩ.
Boldface limits apply at the temperature extremes.
Parameter
Test Conditions
Typ (1)
Units
(2)
1.5
V/μs
1.4
MHz
SR
Slew Rate
See
GBW
Gain Bandwidth Product
V + = 15V
θm
Phase Margin
48
°
Gm
Gain Margin
17
dB
Amp-to-Amp Isolation
See (3)
130
dB
en
Input-Referred Voltage Noise
f = 1kHz
V CM = 1V
27
nV/√Hz
in
Input Referred Current Noise
f = 1kHz
0.2
fA/√Hz
THD
Total Harmonic Distortion
f = 10kHz, AV = −10
R L = 2kΩ, VO = 8 VPP
V + = 10V
0.01
%
(1)
(2)
(3)
4
Typical Values represent the most likely parametric norm or one sigma value.
V+ = 15V. Connected as voltage follower with 10V step input. Number specified is the slower of the positive and negative slew rates.
Input referred, V + = 15V and RL = 100kΩ connected to 7.5V. Each amp excited in turn with 1kHz to produce VO = 12 VPP.
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Typical Performance Characteristics
Unless otherwise specified, VS = 2.7V, single supply, TA = 25°C
Supply Current
vs.
Supply Voltage (Per Amplifier)
Input Current
vs.
Temperature
Figure 2.
Figure 3.
Sourcing Current
vs.
Output Voltage
Sourcing Current
vs.
Output Voltage
Figure 4.
Figure 5.
Sinking Current
vs.
Output Voltage
Sinking Current
vs.
Output Voltage
Figure 6.
Figure 7.
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Typical Performance Characteristics (continued)
Unless otherwise specified, VS = 2.7V, single supply, TA = 25°C
6
Output Voltage Swing
vs.
Supply Voltage
Input Noise
vs.
Frequency
Figure 8.
Figure 9.
Input Noise
vs.
Frequency
Amp to Amp Isolation
vs.
Frequency
Figure 10.
Figure 11.
Amp to Amp Isolation
vs.
Frequency
+PSRR
vs.
Frequency
Figure 12.
Figure 13.
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Typical Performance Characteristics (continued)
Unless otherwise specified, VS = 2.7V, single supply, TA = 25°C
−PSRR
vs.
Frequency
CMRR
vs.
Frequency
Figure 14.
Figure 15.
CMRR
vs.
Input Voltage
CMRR
vs.
Input Voltage
Figure 16.
Figure 17.
Input Voltage
vs.
Output Voltage
Input Voltage
vs.
Output Voltage
Figure 18.
Figure 19.
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Typical Performance Characteristics (continued)
Unless otherwise specified, VS = 2.7V, single supply, TA = 25°C
8
Frequency Response
vs.
Temperature
Frequency Response
vs.
Temperature
Figure 20.
Figure 21.
Gain and Phase
vs.
Capacitive Load
Gain and Phase
vs.
Capacitive Load
Figure 22.
Figure 23.
Slew Rate
vs.
Supply Voltage
Non-Inverting Large Signal Response
Figure 24.
Figure 25.
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Typical Performance Characteristics (continued)
Unless otherwise specified, VS = 2.7V, single supply, TA = 25°C
Non-Inverting Large Signal Response
Non-Inverting Large Signal Response
Figure 26.
Figure 27.
Non-Inverting Small Signal Response
Non-Inverting Small Signal Response
Figure 28.
Figure 29.
Non-Inverting Large Signal Response
Inverting Large Signal Response
Figure 30.
Figure 31.
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Typical Performance Characteristics (continued)
Unless otherwise specified, VS = 2.7V, single supply, TA = 25°C
10
Inverting Large Signal Response
Inverting Large Signal Response
Figure 32.
Figure 33.
Inverting Small Signal Response
Inverting Small Signal Response
Figure 34.
Figure 35.
Inverting Small Signal Response
Stability
vs.
Capacitive Load
Figure 36.
Figure 37.
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Typical Performance Characteristics (continued)
Unless otherwise specified, VS = 2.7V, single supply, TA = 25°C
Stability
vs.
Capacitive Load
Stability
vs.
Capacitive Load
Figure 38.
Figure 39.
Stability
vs.
Capacitive Load
Stability
vs.
Capacitive Load
Figure 40.
Figure 41.
Stability
vs.
Capacitive Load
Figure 42.
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APPLICATION NOTES
Background
The LMC6035/6 is exceptionally well suited for low voltage applications. A desirable feature that the LMC6035/6
brings to low voltage applications is its output drive capability—a hallmark for TI's CMOS amplifiers. The circuit of
Figure 43 illustrates the drive capability of the LMC6035/6 at 3V of supply. It is a differential output driver for a
one-to-one audio transformer, like those used for isolating ground from the telephone lines. The transformer (T1)
loads the op amps with about 600Ω of AC load, at 1 kHz. Capacitor C1 functions to block DC from the low
winding resistance of T1. Although the value of C1 is relatively high, its load reactance (Xc) is negligible
compared to inductive reactance (XI) of T1.
Figure 43. Differential Driver
The circuit in Figure 43 consists of one input signal and two output signals. U1A amplifies the input with an
inverting gain of −2, while the U1B amplifies the input with a non-inverting gain of +2. Since the two outputs are
180° out of phase with each other, the gain across the differential output is 4. As the differential output swings
between the supply rails, one of the op amps sources the current to the load, while the other op amp sinks the
current.
How good a CMOS op amp can sink or source a current is an important factor in determining its output swing
capability. The output stage of the LMC6035/6—like many op amps—sources and sinks output current through
two complementary transistors in series. This “totem pole” arrangement translates to a channel resistance (Rdson)
at each supply rail which acts to limit the output swing. Most CMOS op amps are able to swing the outputs very
close to the rails—except, however, under the difficult conditions of low supply voltage and heavy load. The
LMC6035/6 exhibits exceptional output swing capability under these conditions.
The scope photos of Figure 44 and Figure 45 represent measurements taken directly at the output (relative to
GND) of U1A, in Figure 43. Figure 44 illustrates the output swing capability of the LMC6035, while Figure 45
provides a benchmark comparison. (The benchmark op amp is another low voltage (3V) op amp manufactured
by one of our reputable competitors.)
12
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Figure 44. Output Swing Performance of
the LMC6035 per the Circuit of Figure 43
Figure 45. Output Swing Performance of Benchmark
Op Amp per the Circuit of Figure 43
Notice the superior drive capability of LMC6035 when compared with the benchmark measurement—even
though the benchmark op amp uses twice the supply current.
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Not only does the LMC6035/6 provide excellent output swing capability at low supply voltages, it also maintains
high open loop gain (A VOL) with heavy loads. To illustrate this, the LMC6035 and the benchmark op amp were
compared for their distortion performance in the circuit of Figure 43. The graph of Figure 46 shows this
comparison. The y-axis represents percent Total Harmonic Distortion (THD plus noise) across the loaded
secondary of T1. The x-axis represents the input amplitude of a 1 kHz sine wave. (Note that T1 loses about 20%
of the voltage to the voltage divider of RL (600Ω) and T1's winding resistances—a performance deficiency of the
transformer.)
Figure 46. THD+Noise Performance of LMC6035 and “Benchmark” per Circuit of Figure 43
Figure 46 shows the superior distortion performance of LMC6035/6 over that of the benchmark op amp. The
heavy loading of the circuit causes the AVOL of the benchmark part to drop significantly which causes increased
distortion.
APPLICATION CIRCUITS
Low-Pass Active Filter
A common application for low voltage systems would be active filters, in cordless and cellular phones for
example. The ultra low input currents (IIN) of the LMC6035/6 makes it well suited for low power active filter
applications, because it allows the use of higher resistor values and lower capacitor values. This reduces power
consumption and space.
Figure 47 shows a low pass, active filter with a Butterworth (maximally flat) frequency response. Its topology is a
Sallen and Key filter with unity gain. Note the normalized component values in parenthesis which are obtainable
from standard filter design handbooks. These values provide a 1Hz cutoff frequency, but they can be easily
scaled for a desired cutoff frequency (fc). The bold component values of Figure 47 provide a cutoff frequency of
3kHz. An example of the scaling procedure follows Figure 47.
Figure 47. 2-Pole, 3kHz, Active, Sallen and Key, Lowpass Filter with Butterworth Response
14
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Low-Pass Frequency Scaling Procedure
The actual component values represented in bold of Figure 47 were obtained with the following scaling
procedure:
1. First determine the frequency scaling factor (FSF) for the desired cutoff frequency. Choosing fc at 3kHz,
provides the following FSF computation:
– FSF = 2π x 3kHz (desired cutoff freq.) = 18.84 x 10 3
2. Then divide all of the normalized capacitor values by the FSF as follows:
C1' = C(Normalized)/FSF
C1' =
0.707/18.84 x 103 = 37.93 x 10−6
C2' = 1.414/18.84 x 103 = 75.05 x 10−6
(C1' and C2': prior to
impedance scaling)
3. Last, choose an impedance scaling factor (Z). This Z factor can be calculated from a standard value for C2.
Then Z can be used to determine the remaining component values as follows:
Z = C2'/C2(chosen) = 75.05 x 10 −6/6.8nF = 8.4k
C1 = C1'/Z = 37.93 x 10−6 /8.4k = 4.52nF
(Standard capacitor value chosen for C1 is 4.7nF )
R2(normalized) x Z = 1Ω x 8.4k = 8.4kΩ
R1 = R1(normalized) x Z = 1Ω x 8.4k = 8.4kΩ
R2 =
(Standard value chosen for R1 and R2 is 8.45kΩ )
High Pass Active Filter
The previous low-pass filter circuit of Figure 47 converts to a high-pass active filter per Figure 48.
Figure 48. 2 Pole, 300Hz, Sallen and Key, High-Pass Filter
High-Pass Frequency Scaling Procedure
Choose a standard capacitor value and scale the impedances in the circuit according to the desired cutoff
frequency (300Hz) as follows: C = C1 = C2 Z = 1 Farad/C(chosen) x 2π x (desired cutoff freq.)
= 1
Farad/6.8nF x 2π x 300 Hz = 78.05k
R1 = Z x R1(normalized) = 78.05k x (1/0.707) = 110.4kΩ
(Standard value chosen for R1 is 110kΩ )
R2 = Z x R2(normalized) = 78.05k x (1/1.414) = 55.2kΩ
(Standard value chosen for R1 is 54.9kΩ )
Dual Amplifier Bandpass Filter
The dual amplifier bandpass (DABP) filter features the ability to independently adjust fc and Q. In most other
bandpass topologies, the fc and Q adjustments interact with each other. The DABP filter also offers both low
sensitivity to component values and high Qs. The following application of Figure 49, provides a 1kHz center
frequency and a Q of 100.
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Figure 49. 2 Pole, 1kHz Active, Bandpass Filter
DABP Component Selection Procedure
Component selection for the DABP filter is performed as follows:
1. First choose a center frequency (fc). Figure 49 represents component values that were obtained from the
following computation for a center frequency of 1kHz.
R2 = R3 = 1/(2 πf cC)
Given: fc = 1kHz and C
R2 = R3 = 1/(2π x 3kHz x 6.8nF) = 23.4kΩ
(chosen) = 6.8nF
– (Chosen standard value is 23.7kΩ )
2. Then compute R1 for a desired Q (fc/BW) as follows:
R1 = Q x R2.
Choosing a Q of 100,
R1 = 100
x 23.7kΩ = 2.37MΩ.
PRINTED-CIRCUIT-BOARD LAYOUT FOR HIGH-IMPEDANCE WORK
It is generally recognized that any circuit which must operate with < 1000pA of leakage current requires special
layout of the PC board. If one wishes to take advantage of the ultra-low bias current of the LMC6035/6, typically
< 0.04pA, it is essential to have an excellent layout. Fortunately, the techniques for obtaining low leakages are
quite simple. First, the user must not ignore the surface leakage of the PC board, even though it may at times
appear acceptably low. Under conditions of high humidity, dust or contamination, the surface leakage will be
appreciable.
To minimize the effect of any surface leakage, lay out a ring of foil completely surrounding the LMC6035 or
LMC6036 inputs and the terminals of capacitors, diodes, conductors, resistors, relay terminals, etc. connected to
the op amp's inputs. See Figure 50. To have a significant effect, guard rings should be placed on both the top
and bottom of the PC board. This PC foil must then be connected to a voltage which is at the same voltage as
the amplifier inputs, since no leakage current can flow between two points at the same potential. For example, a
PC board trace-to-pad resistance of 1012Ω, which is normally considered a very large resistance, could leak 5pA
if the trace were a 5V bus adjacent to the pad of an input. This would cause a 100 times degradation from the
amplifiers actual performance. However, if a guard ring is held within 5mV of the inputs, then even a resistance
of 1011Ω would cause only 0.05pA of leakage current, or perhaps a minor (2:1) degradation of the amplifier's
performance. See Figure 51(a) through Figure 51(c) for typical connections of guard rings for standard op amp
configurations. If both inputs are active and at high impedance, the guard can be tied to ground and still provide
some protection; see Figure 51(d).
16
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Product Folder Links: LMC6035 LMC6035-Q1 LMC6036
LMC6035, LMC6035-Q1, LMC6036
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SNOS875G – JANUARY 2000 – REVISED APRIL 2013
Figure 50. Example, using the LMC6036 of Guard Ring in PC Board Layout
(a) Inverting Amplifier (Guard Ring Connections)
(b) Non-Inverting Amplifier (Guard Ring Connections)
(c) Follower (Guard Ring Connections)
(d) Howland Current Pump
Figure 51. Guard Ring Connections
CAPACITIVE LOAD TOLERANCE
Like many other op amps, the LMC6035/6 may oscillate when its applied load appears capacitive. The threshold
of oscillation varies both with load and circuit gain. The configuration most sensitive to oscillation is a unity-gain
follower. See the Typical Performance Characteristics.
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Product Folder Links: LMC6035 LMC6035-Q1 LMC6036
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LMC6035, LMC6035-Q1, LMC6036
SNOS875G – JANUARY 2000 – REVISED APRIL 2013
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The load capacitance interacts with the op amp's output resistance to create an additional pole. If this pole
frequency is sufficiently low, it will degrade the op amp's phase margin so that the amplifier is no longer stable at
low gains. As shown in Figure 52, the addition of a small resistor (50Ω–100Ω) in series with the op amp's output,
and a capacitor (5pF–10pF) from inverting input to output pins, returns the phase margin to a safe value without
interfering with lower-frequency circuit operation. Thus, larger values of capacitance can be tolerated without
oscillation. Note that in all cases, the output will ring heavily when the load capacitance is near the threshold for
oscillation.
DSBGA Considerations
Contrary to what might be guessed, the DSBGA package does not follow the trend of smaller packages having
higher thermal resistance. LMC6035 in DSBGA has thermal resistance of 220°C/W compared to 230°C/W in
VSSOP. Even when driving a 600Ω load and operating from ±7.5V supplies, the maximum temperature rise will
be under 4.5°C. For application information specific to DSBGA, see Application note AN-1112 (Literature Number
SNVA009).
Figure 52. Rx, Cx Improve Capacitive Load Tolerance
Capacitive load driving capability is enhanced by using a pull up resistor to V+ (Figure 53). Typically a pull up
resistor conducting 500μA or more will significantly improve capacitive load responses. The value of the pull up
resistor must be determined based on the current sinking capability of the amplifier with respect to the desired
output swing. Open loop gain of the amplifier can also be affected by the pull up resistor (see Electrical
Characteristics).
Figure 53. Compensating for Large Capacitive Loads with a Pull Up Resistor
Connection Diagrams
Top View
Figure 54. 8-Pin SOIC or VSSOP Package
See Package Number D0008A or DGK0008A
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Top View
Figure 55. 14-Pin SOIC or TSSOP Package
See Package Number D0014A or PW0014A
Copyright © 2000–2013, Texas Instruments Incorporated
Product Folder Links: LMC6035 LMC6035-Q1 LMC6036
PACKAGE OPTION ADDENDUM
www.ti.com
10-Dec-2020
PACKAGING INFORMATION
Orderable Device
Status
(1)
Package Type Package Pins Package
Drawing
Qty
Eco Plan
(2)
Lead finish/
Ball material
MSL Peak Temp
Op Temp (°C)
Device Marking
(3)
(4/5)
(6)
LMC6035IM/NOPB
ACTIVE
SOIC
D
8
95
RoHS & Green
SN
Level-1-260C-UNLIM
-40 to 85
LMC60
35IM
LMC6035IMM/NOPB
ACTIVE
VSSOP
DGK
8
1000
RoHS & Green
SN
Level-1-260C-UNLIM
-40 to 85
A06B
LMC6035IMMX/NOPB
ACTIVE
VSSOP
DGK
8
3500
RoHS & Green
SN
Level-1-260C-UNLIM
-40 to 85
A06B
LMC6035IMQ1
ACTIVE
SOIC
D
8
95
RoHS & Green
SN
Level-1-260C-UNLIM
-40 to 85
LMC60
35IMQ
LMC6035IMX/NOPB
ACTIVE
SOIC
D
8
2500
RoHS & Green
SN
Level-1-260C-UNLIM
-40 to 85
LMC60
35IM
LMC6035IMXQ1
ACTIVE
SOIC
D
8
2500
RoHS & Green
SN
Level-1-260C-UNLIM
-40 to 85
LMC60
35IMQ
LMC6035ITL/NOPB
ACTIVE
DSBGA
YZR
8
250
RoHS & Green
SNAGCU
Level-1-260C-UNLIM
-40 to 85
A
80
LMC6035ITLX/NOPB
ACTIVE
DSBGA
YZR
8
3000
RoHS & Green
SNAGCU
Level-1-260C-UNLIM
-40 to 85
A
80
LMC6036IM/NOPB
ACTIVE
SOIC
D
14
55
RoHS & Green
SN
Level-1-260C-UNLIM
-40 to 85
LMC6036IM
LMC6036IMT/NOPB
ACTIVE
TSSOP
PW
14
94
RoHS & Green
SN
Level-1-260C-UNLIM
-40 to 85
LMC603
6IMT
LMC6036IMTX/NOPB
ACTIVE
TSSOP
PW
14
2500
RoHS & Green
SN
Level-1-260C-UNLIM
-40 to 85
LMC603
6IMT
LMC6036IMX/NOPB
ACTIVE
SOIC
D
14
2500
RoHS & Green
SN
Level-1-260C-UNLIM
-40 to 85
LMC6036IM
(1)
The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2)
RoHS: TI defines "RoHS" to mean semiconductor products that are compliant with the current EU RoHS requirements for all 10 RoHS substances, including the requirement that RoHS substance
do not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, "RoHS" products are suitable for use in specified lead-free processes. TI may
reference these types of products as "Pb-Free".
RoHS Exempt: TI defines "RoHS Exempt" to mean products that contain lead but are compliant with EU RoHS pursuant to a specific EU RoHS exemption.
Addendum-Page 1
Samples
PACKAGE OPTION ADDENDUM
www.ti.com
10-Dec-2020
Green: TI defines "Green" to mean the content of Chlorine (Cl) and Bromine (Br) based flame retardants meet JS709B low halogen requirements of
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