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OPA348-Q1, OPA2348-Q1, OPA4348-Q1
SBOS465C – JANUARY 2009 – REVISED JANUARY 2016
OPAx348-Q1 1-MHz 45-µA CMOS Rail-to-Rail Operational Amplifier
1 Features
3 Description
•
•
The OPAx348-Q1 series of devices are single-supply,
low-power CMOS operational amplifiers. Featuring an
extended bandwidth of 1 MHz and a supply current of
45 µA, the OPAx348-Q1 family of devices is useful
for low-power applications on single supplies of 2.1 V
to 5.5 V.
1
•
•
•
•
•
•
Qualified for Automotive Applications
AEC-Q100 Qualified With the Following Results:
– Device Temperature Grade 1: –40°C to
+125°C Ambient Operating Temperature
Range
– Device HBM ESD Classification Level 2
– Device CDM ESD Classification Level C4B
Low Quiescent Current (IQ): 45 µA (Typ)
Low Cost
Rail-to-Rail Input and Output
Single Supply: 2.1 V to 5.5 V
Input Bias Current: 0.5 pA (Typ)
High Speed: Power With Bandwidth: 1 MHz
Low supply current of 45 µA and an input bias current
of 0.5 pA make the OPAx348-Q1 family of devices an
optimal candidate for low-power, high-impedance
applications such as smoke detectors and other
sensors.
The OPA348-Q1 device is available in both the
SOT23-5 (DBV) and the SOIC (D) packages. The
OPA2348-Q1 device is available in the SOIC-8 (D)
package. The OPA4348-Q1 device is available in the
TSSOP-14
(PW)
package.
The
automotive
temperature range of –40°C to +125°C over all
supply voltages offers additional design flexibility.
2 Applications
•
•
•
•
•
•
•
Portable Equipment
Battery-Powered Equipment
Smoke Alarms
CO Detectors
HEV/EV and Power Train
Infotainment and Cluster
Medical Instrumentation
Device Information(1)
PART NUMBER
PACKAGE
BODY SIZE (NOM)
SOT-23 (5)
2.90 mm × 1.60 mm
SOIC (8)
4.90 mm × 3.91 mm
OPA2348-Q1
SOIC (8)
4.90 mm × 3.91 mm
OPA4348-Q1
TSSOP (14)
5.00 mm × 4.40 mm
OPA348-Q1
(1) For all available packages, see the orderable addendum at
the end of the datasheet.
Noninverting Configuration Driving ADS7822
5V
0.1 µF
8 V+
1/2
OPA2348-Q1
500 Ω
0.1 µF
1 VREF
DCLOCK
+IN
ADS7822
12-Bit A/D
2
VIN
3300 pF
–IN
3
DOUT
CS/SHDN
7
6
5
Serial
Interface
GND 4
VIN = 0 V to 5 V for
0-V to 5-V output.
RC network filters high-frequency noise.
1
An IMPORTANT NOTICE at the end of this data sheet addresses availability, warranty, changes, use in safety-critical applications,
intellectual property matters and other important disclaimers. PRODUCTION DATA.
OPA348-Q1, OPA2348-Q1, OPA4348-Q1
SBOS465C – JANUARY 2009 – REVISED JANUARY 2016
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Table of Contents
1
2
3
4
5
6
7
Features ..................................................................
Applications ...........................................................
Description .............................................................
Revision History.....................................................
Pin Configuration and Functions .........................
Specifications.........................................................
1
1
1
2
3
5
6.1
6.2
6.3
6.4
6.5
6.6
6.7
5
5
5
6
6
7
8
Absolute Maximum Ratings ......................................
ESD Ratings..............................................................
Recommended Operating Conditions.......................
Thermal Information: OPA348-Q1 ............................
Thermal Information: OPA2348-Q1, OPA4348-Q1...
Electrical Characteristics...........................................
Typical Characteristics ..............................................
Detailed Description ............................................ 11
7.1 Overview ................................................................. 11
7.2 Functional Block Diagram ....................................... 11
7.3 Feature Description................................................. 12
7.4 Device Functional Modes........................................ 15
8
Application and Implementation ........................ 16
8.1 Application Information............................................ 16
8.2 Typical Application ................................................. 17
9 Power Supply Recommendations...................... 19
10 Layout................................................................... 20
10.1 Layout Guidelines ................................................. 20
10.2 Layout Example .................................................... 20
11 Device and Documentation Support ................. 21
11.1
11.2
11.3
11.4
11.5
11.6
Documentation Support ........................................
Related Links ........................................................
Community Resource............................................
Trademarks ...........................................................
Electrostatic Discharge Caution ............................
Glossary ................................................................
21
21
21
21
21
21
12 Mechanical, Packaging, and Orderable
Information ........................................................... 21
4 Revision History
NOTE: Page numbers for previous revisions may differ from page numbers in the current version.
Changes from Revision B (December 2014) to Revision C
•
Page
Added the OPA348-Q1 SOIC (D) package option to document ............................................................................................ 1
Changes from Revision A (January 2009) to Revision B
Page
•
Added two new applications to the Applications section ....................................................................................................... 1
•
Added the ESD Ratings table, Feature Description section, Device Functional Modes section, Application and
Implementation section, Power Supply Recommendations section, Layout section, Device and Documentation
Support section, and Mechanical, Packaging, and Orderable Information section ............................................................... 1
•
Added the OPA348-Q1 device to the data sheet .................................................................................................................. 1
•
Changed the name for pin 3 in the PW (TSSOP) package drawing ...................................................................................... 4
2
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SBOS465C – JANUARY 2009 – REVISED JANUARY 2016
5 Pin Configuration and Functions
DBV Package: OPA348-Q1
5-Pin SOT-23
Top View
Out
1
V–
2
+In
3
5
4
D Package: OPA348-Q1
8-Pin SOIC
Top View
V+
–In
NC
1
-In
2
+In
3
V-
4
8
NC
–
7
V+
+
6
OUT
5
nc
Pin Functions: OPA348-Q1
PIN
NO.
NAME
I/O
DESCRIPTION
SOT-23
SOIC
+IN
3
3
I
Noninverting input
–IN
4
2
I
Inverting input
OUT
1
6
O
Output
V+
5
7
—
Positive (highest) supply
V–
2
4
—
Negative (lowest) supply
—
Do not connect
1
NC
—
5
8
D Package: OPA2348-Q1
8-Pin SOIC
Top View
Out A 1
-In A 2
A
+In A 3
V-
B
4
8
V+
7
Out B
6
-In B
5
+In B
Pin Functions: OPA2348-Q1
PIN
I/O
DESCRIPTION
NAME
NO
+IN A
3
I
Noninverting input, Channel A
–IN A
2
I
Inverting input, Channel A
+IN B
5
I
Noninverting input, Channel B
–IN B
6
I
Inverting input, Channel B
OUT A
1
O
Output, Channel A
OUT B
7
O
Output, Channel B
V+
8
—
Positive (highest) supply
V–
4
—
Negative (lowest) supply
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SBOS465C – JANUARY 2009 – REVISED JANUARY 2016
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PW Package: OPA4348-Q1
14-Pin TSSOP
Top View
14
Out D
13
-In D
3
12
+In D
V+
4
11
V-
+In B
5
10
+In C
Out A
1
-In A
2
+In A
A
B
D
C
-In B
6
9
-In C
Out B
7
8
Out C
Pin Functions: OPA4348-Q1
PIN
I/O
DESCRIPTION
NAME
NO.
+IN A
3
I
Noninverting input, Channel A
–IN A
2
I
Inverting input, Channel A
+IN B
5
I
Noninverting input, Channel B
–IN B
6
I
Inverting input, Channel B
+IN C
10
I
Noninverting input, Channel C
–IN C
9
I
Inverting input, Channel C
+IN D
12
I
Noninverting input, Channel D
–IN D
13
I
Inverting input, Channel D
OUT A
1
O
Output, Channel A
OUT B
7
O
Output, Channel B
OUT C
8
O
Output, Channel C
OUT D
14
O
Output, Channel D
V+
4
—
Positive (highest) supply
V–
11
—
Negative (lowest) supply
4
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SBOS465C – JANUARY 2009 – REVISED JANUARY 2016
6 Specifications
6.1 Absolute Maximum Ratings
over operating free-air temperature range (unless otherwise noted) (1)
MIN
Supply voltage, VS
V– to V+
Input voltage, VIN
Signal input terminals (2)
Input current, IIN
Signal input terminals (2)
(V–) – 0.5 V
Output short-circuit duration (3)
V
10
mA
150
°C
150
°C
150
°C
–40
Storage temperature, Tstg
(3)
V
(V+) + 0.5 V
Operating virtual-junction temperature, TJ
(2)
UNIT
7.5
Continuous
Operating free-air temperature, TA
(1)
MAX
–65
Stresses beyond those listed under absolute maximum ratings may cause permanent damage to the device. These are stress ratings
only, and functional operation of the device at these or any other conditions beyond those indicated under recommended operating
conditions is not implied. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability.
Input terminals are diode-clamped to the power-supply rails. Input signals that can swing more than 0.5 V beyond the supply rails should
be current-limited to 10 mA or less.
Short-circuit to ground, one amplifier per package.
6.2 ESD Ratings
VALUE
Human-body model (HBM), per AEC Q100-002 (1)
V(ESD)
(1)
Electrostatic
discharge
Charged-device model (CDM), per AEC
Q100-011
UNIT
±2000
All pins
±500
Corner pins (1, 7, 8, and 14)
±750
V
AEC Q100-002 indicates that HBM stressing shall be in accordance with the ANSI/ESDA/JEDEC JS-001 specification.
6.3 Recommended Operating Conditions
over operating free-air temperature range (unless otherwise noted)
MIN
MAX
UNIT
VS
Supply voltage, V– to V+
2.1
5.5
V
TA
Operating free-air temperature
–40
125
°C
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SBOS465C – JANUARY 2009 – REVISED JANUARY 2016
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6.4 Thermal Information: OPA348-Q1
OPA348-Q1
THERMAL METRIC (1)
DBV (SOT-23)
D (SOIC)
5 PINS
8 PINS
UNIT
RθJA
Junction-to-ambient thermal resistance
228.5
142.0
°C/W
RθJC(top)
Junction-to-case (top) thermal resistance
99.1
90.2
°C/W
RθJB
Junction-to-board thermal resistance
54.6
82.5
°C/W
ψJT
Junction-to-top characterization parameter
7.7
39.4
°C/W
ψJB
Junction-to-board characterization parameter
53.8
82.0
°C/W
RθJC(bottom)
Junction-to-case (bottom) thermal resistance
n/a
n/a
°C/W
(1)
For more information about traditional and new thermal metrics, see the Semiconductor and IC Package Thermal Metrics application
report, SPRA953.
6.5 Thermal Information: OPA2348-Q1, OPA4348-Q1
THERMAL METRIC (1)
OPA2348-Q1
OPA4348-Q1
D (SOIC)
PW (TSSOP)
8 PINS
14 PINS
UNIT
RθJA
Junction-to-ambient thermal resistance
138.4
121
°C/W
RθJC(top)
Junction-to-case (top) thermal resistance
89.5
49.4
°C/W
RθJB
Junction-to-board thermal resistance
78.6
62.8
°C/W
ψJT
Junction-to-top characterization parameter
29.9
5.9
°C/W
ψJB
Junction-to-board characterization parameter
78.1
62.2
°C/W
RθJC(bottom)
Junction-to-case (bottom) thermal resistance
n/a
n/a
°C/W
(1)
6
For more information about traditional and new thermal metrics, see the Semiconductor and IC Package Thermal Metrics application
report, SPRA953.
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SBOS465C – JANUARY 2009 – REVISED JANUARY 2016
6.6 Electrical Characteristics
At VS = 2.5 V to 5.5 V, RL = 100 kΩ connected to VS / 2, VOUT = VS / 2 (unless otherwise noted).
PARAMETER
TEST CONDITIONS
VOS
Input offset voltage
ΔVOS/ΔT
Offset voltage drift over temperature
PSRR
VS = 5 V, VCM = (V–) + 0.8 V
Offset voltage drift vs power supply
Channel separation
VCM
VS = 2.5 V to 5.5 V, VCM < (V+) – 1.7 V
TA
(1)
MIN
25°C
TYP
MAX
1
5
Full range
Full range
4
25°C
60
Full range
µV/°C
175
µV/V
300
25°C
0.2
f = 1 kHz
25°C
134
(V–) – 0.2 V < VCM < (V+) – 1.7 V
mV
6
dc
Input common-mode voltage range
UNIT
25°C
(V–) – 0.2
25°C
70
Full range
66
25°C
60
Full range
56
µV/V
dB
(V+) + 0.2
V
82
CMRR
Input common-mode rejection ratio
IB
Input bias current
25°C
±0.5
±10
pA
IOS
Input offset current
25°C
±0.5
±10
pA
VS = 5.5 V, (V–) – 0.2 V < VCM < (V+) + 0.2 V
VS = 5.5 V, (V–) < VCM < (V+)
1013|| 3
Differential
ZI
Input impedance
dB
71
25°C
Ω || pF
1013|| 3
Common-mode
Input voltage noise
VCM < (V+) – 1.7 V, f = 0.1 Hz to 10 Hz
25°C
10
µVPP
Vn
Input voltage noise density
VCM < (V+) – 1.7 V, f = 1 kHz
25°C
35
nV/√Hz
In
Input current noise density
VCM < (V+) – 1.7 V, f = 1 kHz
25°C
4
fA/√Hz
VS = 5 V, RL = 100 kΩ,
0.025 V < VO < 4.975 V
25°C
94
Full range
90
25°C
90
Full range
88
AOL
Open-loop voltage gain
VS = 5V, RL = 5 kΩ,
0.125 V < VO < 4.875 V
RL = 100 kΩ, AOL > 94 dB
Voltage output swing from rail
RL = 5 kΩ, AOL > 90 dB
25°C
Capacitive load drive
See the Typical Characteristics section
25°C
GBW
Gain-bandwidth product
CL = 100 pF
SR
Slew rate
CL = 100 pF, G = +1
Settling
time
100
mV
mV
±10
mA
25°C
1
MHz
25°C
0.5
V/µs
5
CL = 100 pF, VS = 5.5 V, 2V- step, G = +1
25°C
Overload recovery time
VIN × Gain > VS
25°C
1.6
THD+N
Total harmonic distortion plus noise
CL = 100 pF, VS = 5.5 V, VO = 3 VPP,
G = +1, f = 1 kHz
25°C
0.0023%
IQ
Quiescent current
Per amplifier
25°C
45
(1)
125
125
25°C
0.01%
25
25
25°C
Output short-circuit current
ts
18
Full range
CLOAD
dB
98
Full range
ISC
0.1%
108
µs
7
Full range
µs
65
75
µA
Full range TA = –40°C to +125°C.
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6.7 Typical Characteristics
At TA = 25°C, RL = 100 kΩ connected to VS / 2, VOUT = VS / 2 (unless otherwise noted).
140
100
0
80
100
80
Gain
60
–90
Phase
40
20
–135
PSRR, CMRR (dB)
–45
Phase (°)
Open-Loop Gain (dB)
120
CMRR
60
40
PSRR
20
0
–20
1
0.1
10
100
1k
10k
100k
1M
0
–180
10M
10
100
1k
Figure 1. Open-Loop Gain and Phase vs Frequency
6
10k
100k
1M
10M
Frequency (Hz)
Frequency (Hz)
Figure 2. PSRR and CMRR vs Frequency
140
V S = 5.5 V
Channel Separation (dB)
Output Voltage (Vp-p)
5
VS = 5 V
4
3
2
V S = 2.5 V
120
100
80
1
60
0
1k
10k
100k
1M
10
10M
100
1k
2
10
45
7
IQ
35
4
Output Voltage Swing (V)
55
Short-Circuit Current (mA)
ISC
+125°C
1
3
3.5
4
10M
4.5
5
5.5
Supply Voltage (V)
+25°C
1.5
–40°C
1
Sourcing Current
0.5
0
–0.5
–1
Sinking Current
–1.5
–40°C
+25°C
–2
25
2.5
1M
2.5
13
2
100k
Figure 4. Channel Separation vs Frequency
Figure 3. Maximum Output Voltage vs Frequency
65
Quiescent Current ( µA)
10k
Frequency (Hz)
Frequency (Hz)
+125°C
–2.5
0
5
10
15
20
Output Current (mA)
VS = ±2.5V
Figure 5. Quiescent and Short-Circuit Current
vs Supply Voltage
8
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Figure 6. Output Voltage Swing vs Output Current
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SBOS465C – JANUARY 2009 – REVISED JANUARY 2016
Typical Characteristics (continued)
At TA = 25°C, RL = 100 kΩ connected to VS / 2, VOUT = VS / 2 (unless otherwise noted).
100
130
90
Open-Loop Gain and
Power Supply Rejection (dB)
Common-Mode Rejection (dB)
AOL , R L = 100 kΩ
120
V– < VCM < (V+) – 1.7 V
80
V– < VCM < V+
70
60
50
AOL , R L = 5 kΩ
110
100
90
80
PSRR
70
60
–50
–75
–25
0
25
50
75
100
125
150
–50
–75
–25
0
Temperature (°C)
Figure 7. Common-Mode Rejection vs Temperature
75
55
12
45
10
IQ
35
8
25
6
15
4
0
25
50
100
125
150
1k
Input Bias Current (pA)
14
ISC
–25
75
Figure 8. Open-Loop Gain and PSRR vs Temperature
Short-Circuit Current (mA)
Quiescent Current ( µA)
65
–50
50
10k
16
–75
25
Temperature (°C)
75
100
125
100
10
1
0.1
150
–75
–50
–25
0
25
50
75
100
125
150
Temperature (°C)
Temperature (°C)
Figure 9. Quiescent and Short-Circuit Current
vs Temperature
Figure 10. Input Bias (IB) Current vs Temperature
25
20
Percentage of Amplifiers (%)
18
Percent of Amplifiers (%)
16
14
12
10
8
6
4
20
15
10
5
2
0
0
–6
–5
–4
–3
–2
–1
0
1
2
3
4
5
6
Offset Voltage (mV)
Typical production distribution of packaged units.
Figure 11. Offset Voltage Production Distribution
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1
2
3
4
5
6
7
8
9
10
11
12
Offset Voltage Drift (µV/°C)
Typical production distribution of packaged units.
Figure 12. Offset Voltage Drift Magnitude
Production Distribution
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Typical Characteristics (continued)
At TA = 25°C, RL = 100 kΩ connected to VS / 2, VOUT = VS / 2 (unless otherwise noted).
60
60
50
50
40
40
Overshoot (%)
Small-Signal Overshoot (%)
G = –1 V/V, R FB = 100 kW
30
G = +1 V/V, RL = 100 kW
20
30
20
G = –1 V/V, RFB = 5 kW
10
10
0
0
10
100
1k
10k
10
100
Load Capacitance (pF)
1k
10k
Load Capacitance (pF)
G = ±5 V/V, RFB = 100 kΩ
Figure 13. Small-Signal Overshoot vs Load Capacitance
20 mV/div
500 mV/div
Figure 14. Percent Overshoot vs Load Capacitance
10 µs/div
2 µs/div
G = 1 V/V
RL = 100 kΩ
CL = 100 pF
G = 1 V/V
Figure 16. Large-Signal Step Response
1k
1k
100
IN
VN
10
10
1
1
10
100
1k
10k
100k
Total Harmonic Distortion + Noise (%)
10k
100
0.100
0.010
0.001
10
100
Figure 17. Input Current and Voltage Noise Spectral Density
vs Frequency
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1k
10k
100k
Frequency (Hz)
Frequency (Hz)
10
CL = 100 pF
1.000
Current Noise (fA√Hz)
Voltage Noise (nV/√Hz)
Figure 15. Small-Signal Step Response
RL = 100 kΩ
Figure 18. Total Harmonic Distortion + Noise vs Frequency
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SBOS465C – JANUARY 2009 – REVISED JANUARY 2016
7 Detailed Description
7.1 Overview
The OPAx348-Q1 family of devices is a low-power, rail-to-rail input and output operational amplifier. These
devices operate from 1.8 V to 5.5 V, are unity-gain stable, and are suitable for a wide range of general-purpose
applications. The class AB output stage is capable of driving ≤ 10-kΩ loads connected to any point between V+
and ground. The input common-mode voltage range includes both rails and allows the OPAx348-Q1 family of
devices to be used in virtually any single-supply application. Rail-to-rail input and output swing significantly
increases dynamic range, especially in low-supply applications, and makes them ideal for driving sampling
analog-to-digital converters (ADCs).
7.2 Functional Block Diagram
OPA348-Q1
V+
Reference
Current
VIN+
VIN±
VBIAS1
Class AB
Control Circuitry
Vo
VBIAS2
V±
(Ground)
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7.3 Feature Description
7.3.1 Operating Voltage
The OPAx348-Q1 op amp is fully specified and ensured for operation from 1.8 V to 5.5 V. In addition, many
specifications apply from –40°C to +125°C. Parameters that vary significantly with operating voltages or
temperature are shown in the Typical Characteristics graphs. Power-supply pins should be bypassed with
0.01-μF ceramic capacitors.
7.3.2 Rail-to-Rail Input
The input common-mode voltage range of the OPAx348-Q1 family of devices extends 200 mV beyond the supply
rails. This performance is achieved with a complementary input stage: an N-channel input differential pair in
parallel with a P-channel differential pair. The N-channel pair is active for input voltages close to the positive rail,
typically (V+) – 1.3 V to 200 mV above the positive supply. The P-channel pair is on for inputs from 200 mV
below the negative supply to approximately (V+) – 1.3 V. A small transition region exists, typically (V+) – 1.4 V to
(V+) – 1.2 V, in which both pairs are on. This 200-mV transition region can vary up to 300 mV with process
variation. Thus, the transition region (both stages on) can range from (V+) – 1.7 V to (V+) – 1.5 V on the low end,
up to (V+) – 1.1 V to (V+) – 0.9 V on the high end. Within this transition region, PSRR, CMRR, offset voltage,
offset drift, and THD may be degraded compared to device operation outside this region.
7.3.3 Rail-to-Rail Input
The input common-mode range extends from (V–) – 0.2 V to (V+) + 0.2 V. For normal operation, the inputs
should be limited to this range. The absolute maximum input voltage is 500 mV beyond the supplies. Inputs
greater than the input common-mode range but less than the maximum input voltage, while not valid, do not
cause any damage to the op amp. Unlike some other op amps, if the input current is limited, the inputs may go
beyond the power supplies without phase inversion, as shown in Figure 19.
VIN
G = +1V/V, V S = +5V
5V
1V/div
VOUT
0V
10µs/div
Figure 19. No Phase Inversion with Inputs Greater Than Power-Supply Voltage
Normally, input currents are 0.5 pA. However, large inputs (greater than 500 mV beyond the supply rails) can
cause excessive current to flow in or out of the input pins. Therefore, limiting the input current to less than 10 mA
is important as well as keeping the input voltage below the maximum rating. This limiting is easily accomplished
with an input voltage resistor, as shown in Figure 20.
+5V
IOVERLOAD
10mA max
1/2
OPA2348
VOUT
VIN
5kW
Figure 20. Input Current Protection for Voltages Exceeding the Supply Voltage
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Feature Description (continued)
7.3.4 Input and ESD Protection
The OPAx348-Q1 family of devices incorporates internal electrostatic discharge (ESD) protection circuits on all
pins. In the case of input and output pins, this protection primarily consists of current-steering diodes connected
between the input and power-supply pins. These ESD protection diodes also provide in-circuit, input overdrive
protection, as long as the current is limited to 10 mA as stated in the Absolute Maximum Ratings table. Figure 21
shows how a series input resistor can be added to the driven input to limit the input current. The added resistor
contributes thermal noise at the amplifier input and the value should be kept to a minimum in noise-sensitive
applications.
V+
IOVERLOAD
10-mA max
VOUT
Device
VIN
5 kW
Figure 21. Input Current Protection
7.3.5 Common-Mode Rejection Ratio (CMRR)
CMRR for the OPAx348-Q1 family of devices is specified in several ways so the best match for a given
application may be used; see the Electrical Characteristics table. First, the CMRR of the device in the commonmode range below the transition region [VCM < (V+) – 1.3 V] is given. This specification is the best indicator of
the capability of the device when the application requires use of one of the differential input pairs. Second, the
CMRR over the entire common-mode range is specified at (VCM = –0.2 V to 5.7 V). This last value includes the
variations seen through the transition region (see Figure 22).
7.3.6 Common-Mode Voltage Range
The input common-mode voltage range of the OPAx348-Q1 device extends 200 mV beyond the supply rails.
This extended range is achieved with a complementary input stage—an N-channel input differential pair in
parallel with a P-channel differential pair. The N-channel pair is active for input voltages close to the positive rail,
typically (V+) – 1.2 V to 300 mV above the positive supply, while the P-channel pair is on for inputs from 300 mV
below the negative supply to approximately (V+) – 1.4 V. A small transition region exists, typically (V+) – 1.4 V to
(V+) – 1.2 V, in which both pairs are on. This 200-mV transition region, shown in Figure 22, can vary ±300 mV
with process variation. Thus, the transition region (both stages on) can range from (V+) – 1.7 V to (V+) – 1.5 V
on the low end, up to (V+) – 1.1 V to (V+) – 0.9 V on the high end. Within the 200-mV transition region, PSRR,
CMRR, offset voltage, offset drift, and THD may be degraded compared to operation outside this region.
OFFSET VOLTAGE
vs FULL COMMON-MODE VOLTAGE RANGE
2
Offset Voltage (mV)
1.5
1
0.5
0
–0.5
–1
V–
V+
–1.5
–2
–0.5 0
0.5
1
1.5
2
2.5
3
3.5
4
4.5
5
5.5
Common-Mode Voltage (V)
Figure 22. Behavior of Typical Transition Region at Room Temperature
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Feature Description (continued)
7.3.7 EMI Susceptibility and Input Filtering
Op amps vary with regard to the susceptibility of the device to electromagnetic interference (EMI). If conducted
EMI enters the op amp, the dc offset observed at the amplifier output may shift from the nominal value while EMI
is present. This shift is a result of signal rectification associated with the internal semiconductor junctions. While
all op amp pin functions can be affected by EMI, the signal input pins are likely to be the most susceptible. The
OPAx348-Q1 family of devices incorporates an internal input, low-pass filter that reduces the amplifier response
to EMI. Both common-mode and differential mode filtering are provided by this filter. The filter is designed for a
cutoff frequency of approximately 80 MHz (–3 dB), with a roll-off of 20 dB per decade.
Texas Instruments has developed the ability to accurately measure and quantify the immunity of an operational
amplifier over a broad frequency spectrum extending from 10 MHz to 6 GHz. The EMI rejection ratio (EMIRR)
metric allows op amps to be directly compared by the EMI immunity. Detailed information can also be found in
the application report, EMI Rejection Ratio of Operational Amplifiers (SBOA128), available for download from
www.ti.com.
7.3.8 Rail-to-Rail Output
Designed as a micro-power, low-noise operational amplifier, the OPAx348-Q1 family of devices delivers a robust
output drive capability. A class AB output stage with common-source transistors is used to achieve full rail-to-rail
output swing capability. For resistive loads up to 10 kΩ, the output swings typically to within 5 mV of either supply
rail regardless of the power-supply voltage applied. Different load conditions change the ability of the amplifier to
swing close to the rails; refer to the graph, Output Voltage Swing vs Output Current.
A class AB output stage with common-source transistors is used to achieve rail-to-rail output. This output stage is
capable of driving 5-kΩ loads connected to any potential between V+ and ground. For light resistive loads
(>100 kΩ), the output voltage can typically swing to within 18 mV from supply rail. With moderate resistive loads
(10 kΩ to 50 kΩ), the output voltage can typically swing to within 100 mV of the supply rails while maintaining
high open-loop gain (see Figure 6 in the Typical Characteristics section).
G = +1V/V, VS = +5V
Output (Inverted on Scope)
1V/div
5V
0V
20µs/div
Figure 23. Rail-to-Rail I/O
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Feature Description (continued)
7.3.9 Capacitive Load and Stability
The OPAx348-Q1 family of devices in a unity-gain configuration can directly drive up to 250-pF pure capacitive
load. Increasing the gain enhances the ability of the amplifier to drive greater capacitive loads (see Figure 13 in
the Typical Characteristics section). In unity-gain configurations, capacitive load drive can be improved by
inserting a small (10-Ω to 20-Ω) resistor, RS, in series with the output, as shown in Figure 24. This resistor
significantly reduces ringing while maintaining dc performance for purely capacitive loads. However, if a resistive
load exists in parallel with the capacitive load, a voltage divider is created, introducing a direct current (dc) error
at the output and slightly reducing the output swing. The error introduced is proportional to the ratio RS/RL and is
generally negligible.
V+
RS
1/2
OPA2348
VOUT
10W to
20W
VIN
RL
CL
Figure 24. Series Resistor in Unity-Gain Buffer Configuration Improves Capacitive Load Drive
In unity-gain inverter configuration, the phase margin can be reduced by the reaction between the capacitance at
the op amp input and the gain setting resistors, thus degrading capacitive load drive. The best performance is
achieved by using small-valued resistors. For example, when driving a 500-pF load, reducing the resistor values
from 100 kΩ to 5 kΩ decreases overshoot from 55% to 13% (see Figure 13 in the Typical Characteristics
section). However, when large-valued resistors cannot be avoided, a small (4-pF to 6-pF) capacitor, CFB, can be
inserted in the feedback loop, as shown in Figure 25. This small capacitor significantly reduces overshoot by
compensating the effect of capacitance, CIN, which includes the input capacitance of the amplifier and printed
circuit board (PCB) parasitic capacitance.
CFB
RF
RI
VIN
1/2
OPA2348
VOUT
CIN
CL
Figure 25. Improving Capacitive Load Drive
7.4 Device Functional Modes
The OPAx348-Q1 family of devices is powered on when the supply is connected. The device can be operated as
a single-supply operational amplifier or a dual-supply amplifier, depending on the application.
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8 Application and Implementation
NOTE
Information in the following applications sections is not part of the TI component
specification, and TI does not warrant its accuracy or completeness. TI’s customers are
responsible for determining suitability of components for their purposes. Customers should
validate and test their design implementation to confirm system functionality.
8.1 Application Information
The OPAx348-Q1 operational amplifiers (op amps) are unity-gain stable and suitable for a wide range of generalpurpose applications.
The OPAx348-Q1 device features wide bandwidth and unity-gain stability with rail-to-rail input and output for
increased dynamic range. Figure 23 shows the input and output waveforms for the OPAx348-Q1 device in unitygain configuration. Operation is from a single 5-V supply with a 100-kΩ load connected to VS / 2. The input is a
5-VPP sinusoid. Output voltage is approximately 4.98 VPP.
The power-supply pins should be bypassed with 0.01-µF ceramic capacitors.
8.1.1 Driving Analog-to-Digital Converters (ADCs)
The OPAx348-Q1 op amps are optimized for driving medium-speed sampling ADCs. The OPAx348-Q1 op amps
buffer the ADC input capacitance and resulting charge injection while providing signal gain.
Figure 26 shows the OPA2348 in a basic noninverting configuration driving the ADS7822 device. The ADS7822
device is a 12-bit, micropower sampling converter in the MSOP-8 package. When used with the low-power
miniature packages of the OPAx348-Q1 family of devices, the combination is ideal for space-limited, low-power
applications. In this configuration, an RC network at the ADC input can be used to provide for anti-aliasing
filtering and charge injection current.
5V
0.1 µF
8 V+
1/2
OPA2348-Q1
500 Ω
0.1 µF
1 VREF
DCLOCK
+IN
ADS7822
12-Bit A/D
2
VIN
3300 pF
–IN
3
DOUT
CS/SHDN
7
6
5
Serial
Interface
GND 4
VIN = 0 V to 5 V for
0-V to 5-V output.
RC network filters high-frequency noise.
A/D input = 0 V to VREF
Figure 26. Noninverting Configuration Driving ADS7822
The OPAx348-Q1 family of devices can also be used in noninverting configuration to drive the ADS7822 device
in limited low-power applications. In this configuration, an RC network at the ADC input can be used to provide
for anti-aliasing filtering and charge injection current. See Figure 26 for the OPAx348-Q1 driving an ADS7822
device in a speech bandpass filtered data acquisition system. This small, low-cost solution provides the
necessary amplification and signal conditioning to interface directly with an electret microphone. This circuit
operates with VS = 2.7 V to 5 V with less than 250-µA typical quiescent current.
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Application Information (continued)
V+ = 2.7 V to 5 V
Passband 300 Hz to 3 kHz
R9
510 kΩ
R1
1.5 kΩ
R4
20 kΩ
R2
1 MΩ
C1
1000 pF
1/2
C3
33 pF
R7
51 kΩ
R8
150 kΩ
VREF 1
8 V+
7
OPA2348-Q1
+IN
1/2
R3
1 MΩ
Electret
Microphone(1)
R6
100 kΩ
OPA2348-Q1
C2
2
–IN
1000 pF
DCLOCK
ADS7822 6
12-Bit A/D
5
DOUT
CS/SHDN
Serial
Interface
3
4
R5
20 kΩ
(1)
G = 100
GND
Electret microphone powered by R1.
Figure 27. Speech Bandpass Filtered Data Acquisition System
8.2 Typical Application
Some applications require differential signals. Figure 28 shows a simple circuit to convert a single-ended input of
0.1 V to 2.4 V into a differential output of ±2.3 V on a single 2.7-V supply. The output range is intentionally limited
to maximize linearity. The circuit is composed of two amplifiers. One amplifier functions as a buffer and creates a
voltage, VOUT+. The second amplifier inverts the input and adds a reference voltage to generate VOUT–. Both
VOUT+ and VOUT– range from 0.1 V to 2.4 V. The difference, VDIFF, is the difference between VOUT+ and VOUT–.
This configuration makes the differential output voltage range to be 2.3 V.
R2
2.7 V
R1
±
VOUT±
+
Device
R3
+
VREF
2.5 V
R4
V
VDIFF
+
2.7 V
±
VOUT+
+
Device
+
+
VIN
Figure 28. Schematic for a Single-Ended Input to Differential Output Conversion
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Typical Application (continued)
8.2.1 Design Requirements
The design requirements are as follows:
• Supply voltage: 2.7 V
• Reference voltage: 2.5 V
• Input: 0.1 V to 2.4 V
• Output differential: ±2.3 V
• Output common-mode voltage: 1.25 V
• Small-signal bandwidth: 1 MHz
8.2.2 Detailed Design Procedure
The circuit in Figure 28 takes a single-ended input signal, VIN, and generates two output signals, VOUT+ and
VOUT– using two amplifiers and a reference voltage, VREF. VOUT+ is the output of the first amplifier and is a
buffered version of the input signal, VIN (as shown in Equation 1). VOUT– is the output of the second amplifier
which uses VREF to add an offset voltage to VIN and feedback to add inverting gain. The transfer function for
VOUT– is given in Equation 2.
VOUT
VIN
(1)
V287±
§ R 4 · § R2 ·
R2
V5() u ¨
¸ u ¨1
¸ V,1 u
R
R
R
R1
4¹ ©
1¹
© 3
(2)
The differential output signal, VDIFF, is the difference between the two single-ended output signals, VOUT+ and
VOUT–. Equation 3 shows the transfer function for VDIFF. By applying the conditions that R1 = R2 and R3 = R4, the
transfer function is simplified into Equation 6. Using this configuration, the maximum input signal is equal to the
reference voltage and the maximum output of each amplifier is equal to VREF. The differential output range is 2 ×
VREF. Furthermore, the common-mode voltage (VCM) is one half of VREF (see Equation 7).
V',))
V287
VOUT
VIN
V287±
V5()
V287±
§ R 4 · § R2 ·
§ R2 ·
V,1 u ¨ 1
¸ u ¨1
¸ V5() u ¨
¸
R1 ¹
R1 ¹
©
© R3 R 4 ¹ ©
(3)
(4)
V,1
VDIFF
2 u VIN VREF
VCM
V287± ·
§ V287
¨
¸
2
©
¹
(5)
(6)
1
VREF
2
(7)
8.2.2.1 Amplifier Selection
Linearity over the input range is key for good dc accuracy. The common-mode input range and output swing
limitations determine the linearity. In general, an amplifier with rail-to-rail input and output swing is required.
Bandwidth is a key concern for this design, so the OPAx348-Q1 family of devices is selected because its
bandwidth is greater than the target of 1 MHz. The bandwidth and power ratio makes this device power-efficient,
and the low offset and drift ensure good accuracy for moderate precision applications.
8.2.2.2 Passive Component Selection
Because the transfer function of VOUT– relies heavily upon resistors (R1, R2, R3, and R4), use resistors with low
tolerances to maximize performance and minimize error. This design uses resistors with resistance values of
49.9 kΩ and tolerances of 0.1%. However, if the noise of the system is a key parameter, smaller resistance
values (6 kΩ or lower) can be selected to keep the overall system noise low. This technique ensures that the
noise from the resistors is lower than the amplifier noise.
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Typical Application (continued)
2.50
2.50
2.00
2.00
1.50
1.50
Vout- (V)
Vout+ (V)
8.2.3 Application Curves
1.00
0.50
0.00
0.00
1.00
0.50
0.50
1.00
1.50
2.00
0.00
0.00
2.50
Input voltage (V)
0.50
1.00
1.50
2.00
Input voltage (V)
C027
Figure 29. VOUT+ vs Input Voltage
2.50
C027
Figure 30. VOUT– vs Input Voltage
2.50
2.00
1.50
Vdiff (V)
1.00
0.50
0.00
-0.50
-1.00
-1.50
-2.00
-2.50
0.00
0.50
1.00
1.50
2.00
Input voltage (V)
2.50
C027
Figure 31. VDIFF vs Input Voltage
9 Power Supply Recommendations
The OPAx348-Q1 family of devices is specified for operation from 1.8 V to 5.5 V (±0.9 V to ±2.75 V); many
specifications apply from –40°C to 125°C. The Typical Characteristics presents parameters that can exhibit
significant variance with regard to operating voltage or temperature.
CAUTION
Supply voltages larger than 7 V can permanently damage the device (see the Absolute
Maximum Ratings).
Place 0.1-μF bypass capacitors close to the power-supply pins to reduce errors coupling in from noisy or highimpedance power supplies. For more detailed information on bypass capacitor placement, refer to the Layout
Guidelines section.
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10 Layout
10.1 Layout Guidelines
For best operational performance of the device, use good PCB layout practices, including:
• Noise can propagate into analog circuitry through the power pins of the circuit as a whole and the
operational amplifier. Bypass capacitors are used to reduce the coupled noise by providing lowimpedance power sources local to the analog circuitry.
– Connect low-ESR, 0.1-µF ceramic bypass capacitors between each supply pin and ground, placed as
close to the device as possible. A single bypass capacitor from V+ to ground is applicable for singlesupply applications.
• Separate grounding for analog and digital portions of the circuitry is one of the simplest and most
effective methods of noise suppression. One or more layers on multilayer PCBs are usually devoted to
ground planes. A ground plane helps distribute heat and reduces EMI noise pickup. Make sure to
physically separate digital and analog grounds, paying attention to the flow of the ground current. For
more detailed information, refer to Circuit Board Layout Techniques, SLOA089.
• To reduce parasitic coupling, run the input traces as far away from the supply or output traces as
possible. If these traces cannot be kept separate, crossing the sensitive trace perpendicularly is much
better than crossing in parallel with the noisy trace.
• Place the external components as close to the device as possible. Keep RF and RG close to the inverting
input to minimize parasitic capacitance, as shown in Figure 32.
• Keep the length of input traces as short as possible. Always remember that the input traces are the most
sensitive part of the circuit.
• Consider a driven, low-impedance guard ring around the critical traces. A guard ring can significantly
reduce leakage currents from nearby traces that are at different potentials.
10.2 Layout Example
+
VIN
VOUT
RG
RF
(Schematic Representation)
Run the input traces
as far away from
the supply lines
as possible
Place components
close to device and to
each other to reduce
parasitic errors
VS+
RF
N/C
N/C
GND
±IN
V+
VIN
+IN
OUTPUT
V±
N/C
RG
Use low-ESR,
ceramic bypass
capacitor
GND
GND
Use low-ESR, ceramic
bypass capacitor
VOUT
VS±
Ground (GND) plane on another layer
Figure 32. Operational Amplifier Board Layout for Noninverting Configuration
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11 Device and Documentation Support
11.1 Documentation Support
11.1.1 Related Documentation
For related documentation see the following:
• ADS7822: 12-Bit, 200kHz, microPower Sampling Analog-to-Digital Converter, SBAS062
• Application report: Circuit Board Layout Techniques, SLOA089
• Application report: EMI Rejection Ratio of Operational Amplifiers, SBOA128
11.2 Related Links
Table 1 lists quick access links. Categories include technical documents, support and community resources,
tools and software, and quick access to sample or buy.
Table 1. Related Links
PARTS
PRODUCT FOLDER
SAMPLE & BUY
TECHNICAL
DOCUMENTS
TOOLS &
SOFTWARE
SUPPORT &
COMMUNITY
OPA348-Q1
Click here
Click here
Click here
Click here
Click here
OPA2348-Q1
Click here
Click here
Click here
Click here
Click here
OPA4348-Q1
Click here
Click here
Click here
Click here
Click here
11.3 Community Resource
The following links connect to TI community resources. Linked contents are provided "AS IS" by the respective
contributors. They do not constitute TI specifications and do not necessarily reflect TI's views; see TI's Terms of
Use.
TI E2E™ Online Community TI's Engineer-to-Engineer (E2E) Community. Created to foster collaboration
among engineers. At e2e.ti.com, you can ask questions, share knowledge, explore ideas and help
solve problems with fellow engineers.
Design Support TI's Design Support Quickly find helpful E2E forums along with design support tools and
contact information for technical support.
11.4 Trademarks
E2E is a trademark of Texas Instruments.
All other trademarks are the property of their respective owners.
11.5 Electrostatic Discharge Caution
These devices have limited built-in ESD protection. The leads should be shorted together or the device placed in conductive foam
during storage or handling to prevent electrostatic damage to the MOS gates.
11.6 Glossary
SLYZ022 — TI Glossary.
This glossary lists and explains terms, acronyms, and definitions.
12 Mechanical, Packaging, and Orderable Information
The following pages include mechanical, packaging, and orderable information. This information is the most
current data available for the designated devices. This data is subject to change without notice and revision of
this document. For browser-based versions of this data sheet, refer to the left-hand navigation.
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PACKAGE OPTION ADDENDUM
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10-Dec-2020
PACKAGING INFORMATION
Orderable Device
Status
(1)
Package Type Package Pins Package
Drawing
Qty
Eco Plan
(2)
Lead finish/
Ball material
MSL Peak Temp
Op Temp (°C)
Device Marking
(3)
(4/5)
(6)
OPA2348AQDRQ1
ACTIVE
SOIC
D
8
2500
RoHS & Green
NIPDAU
Level-2-260C-1 YEAR
-40 to 125
OPA
2348Q
OPA348AQDBVRQ1
ACTIVE
SOT-23
DBV
5
3000
RoHS & Green
NIPDAU
Level-2-260C-1 YEAR
-40 to 125
A48
OPA348AQDRQ1
ACTIVE
SOIC
D
8
2500
RoHS & Green
NIPDAU
Level-2-260C-1 YEAR
-40 to 125
348Q1
OPA4348AQPWRQ1
ACTIVE
TSSOP
PW
14
2500
RoHS & Green
NIPDAU
Level-3-260C-168 HR
-40 to 125
OP4348Q
(1)
The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2)
RoHS: TI defines "RoHS" to mean semiconductor products that are compliant with the current EU RoHS requirements for all 10 RoHS substances, including the requirement that RoHS substance
do not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, "RoHS" products are suitable for use in specified lead-free processes. TI may
reference these types of products as "Pb-Free".
RoHS Exempt: TI defines "RoHS Exempt" to mean products that contain lead but are compliant with EU RoHS pursuant to a specific EU RoHS exemption.
Green: TI defines "Green" to mean the content of Chlorine (Cl) and Bromine (Br) based flame retardants meet JS709B low halogen requirements of
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