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OPA350, OPA2350, OPA4350
SBOS099D – SEPTEMBER 2000 – REVISED DECEMBER 2015
OPAx350 High-Speed, Single-Supply, Rail-to-Rail Operational Amplifiers MicroAmplifier
Series
1 Features
3 Description
•
•
•
•
•
•
•
•
•
The OPA350 series of rail-to-rail CMOS operational
amplifiers are optimized for low voltage, single-supply
operation. Rail-to-rail input and output, low noise (5
nV/√Hz), and high speed operation (38 MHz, 22 V/μs)
make the amplifiers ideal for driving sampling Analogto-Digital (A/D) converters. They are also suited for
cell phone PA control loops and video processing
(75-Ω drive capability), as well as audio and general
purpose applications. Single, dual, and quad versions
have identical specifications for maximum design
flexibility.
Rail-to-Rail Input
Rail-to-Rail Output (Within 10 mV)
Wide Bandwidth: 38 MHz
High Slew Rate: 22 V/μs
Low Noise: 5 nV/√Hz
Low THD+Noise: 0.0006%
Unity-Gain Stable
MicroSize Packages
Single, Dual, and Quad
1
The OPA350 series operates on a single supply as
low as 2.5 V, with an input common-mode voltage
range that extends 300 mV below ground and 300
mV above the positive supply. Output voltage swing
is to within 10 mV of the supply rails, with a 10-kΩ
load. Dual and quad designs feature completely
independent circuitry for lowest crosstalk and
freedom from interaction.
2 Applications
•
•
•
•
•
•
•
•
•
Cell Phone PA Control Loops
Driving A/D Converters
Video Processing
Data Acquisition
Process Controls
Audio Processing
Communications
Active Filters
Test Equipment
The single (OPA350) and dual (OPA2350) come in
the miniature MSOP-8 surface mount, SO-8 surface
mount, and DIP-8 packages. The quad (OPA4350)
packages are in the space-saving SSOP-16 surface
mount and SO-14 surface mount. All are specified
from −40°C to 85°C and operate from −55°C to
150°C.
OPAx350 Harmonic Distortion
Harmonic Distortion (%)
1
(−40dBc)
0.1
(−60dBc)
Device Information(1)
G=1
VO = 2.5VPP
RL = 600Ω
PART NUMBER
OPA350
0.01
(−80dBc)
OPA2350
0.001
(−100dBc)
3rd−Harmonic
2nd−Harmonic
0.0001
(−120dBc) 1k
10k
100k
Frequency (Hz)
OPA4350
PACKAGE
BODY SIZE (NOM)
MSOP (8)
3.00 mm × 3.00 mm
SOIC (8)
3.91 mm × 4.90 mm
PDIP (8)
6.35 mm × 9.81 mm
MSOP (8)
3.00 mm × 3.00 mm
SOIC (8)
3.91 mm × 4.90 mm
PDIP (8)
6.35 mm × 9.81 mm
SSOP (16)
3.90 mm × 4.90 mm
SOIC (14)
3.91 mm × 8.65 mm
1M
(1) For all available packages, see the orderable addendum at
the end of the data sheet.
1
An IMPORTANT NOTICE at the end of this data sheet addresses availability, warranty, changes, use in safety-critical applications,
intellectual property matters and other important disclaimers. PRODUCTION DATA.
OPA350, OPA2350, OPA4350
SBOS099D – SEPTEMBER 2000 – REVISED DECEMBER 2015
www.ti.com
Table of Contents
1
2
3
4
5
6
7
Features ..................................................................
Applications ...........................................................
Description .............................................................
Revision History.....................................................
Pin Configuration and Functions .........................
Specifications.........................................................
1
1
1
2
3
4
6.1
6.2
6.3
6.4
6.5
6.6
6.7
4
4
4
5
5
6
8
Absolute Maximum Ratings ......................................
ESD Ratings ............................................................
Recommended Operating Conditions.......................
Thermal Information: OPA350 and OPA2350...........
Thermal Information: OPA4350 ................................
Electrical Characteristics...........................................
Typical Characteristics ..............................................
Detailed Description ............................................ 12
7.1 Overview ................................................................. 12
7.2 Functional Block Diagram ....................................... 12
7.3 Feature Description................................................. 12
7.4 Device Functional Modes........................................ 17
8
Application and Implementation ........................ 18
8.1 Application Information............................................ 18
8.2 Typical Applications ................................................ 18
9 Power Supply Recommendations...................... 22
10 Layout................................................................... 22
10.1 Layout Guidelines ................................................. 22
10.2 Layout Example .................................................... 23
11 Device and Documentation Support ................. 24
11.1
11.2
11.3
11.4
11.5
11.6
11.7
Device Support ....................................................
Documentation Support .......................................
Related Links ........................................................
Community Resources..........................................
Trademarks ...........................................................
Electrostatic Discharge Caution ............................
Glossary ................................................................
24
24
24
25
25
25
25
12 Mechanical, Packaging, and Orderable
Information ........................................................... 25
4 Revision History
NOTE: Page numbers for previous revisions may differ from page numbers in the current version.
Changes from Revision C (January 2005) to Revision D
•
2
Page
Added ESD Ratings table, Feature Description section, Device Functional Modes, Application and Implementation
section, Power Supply Recommendations section, Layout section, Device and Documentation Support section, and
Mechanical, Packaging, and Orderable Information section. ................................................................................................ 1
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Copyright © 2000–2015, Texas Instruments Incorporated
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SBOS099D – SEPTEMBER 2000 – REVISED DECEMBER 2015
5 Pin Configuration and Functions
D Package
14-Pin SOIC
Top View
OPA350: P, D, and DGK Packages
8-Pin PDIP, SOIC, and VSSOP
Top View
NC
1
8
NC
−In
2
7
V+
+In
3
6
Output
V−
4
5
NC
Out A
1
−In A
2
13
−In D
3
12
+In D
V+
4
11
V−
+In B
5
10
+In C
B
Out A
1
−In A 2
+In A
3
−
4
A
B
8
V+
7
Out B
6
−In B
5
+In B
Out D
+In A
A
OPA2350: P, D, and DGK Packages
8-Pin PDIP, SOIC, and VSSOP
Top View
14
D
C
−In B
6
9
−In C
Out B
7
8
Out C
16
Out D
15
−In D
DBQ Package
16-Pin SSOP
Top View
Out A
1
−In A
2
A
D
+In A
3
14
+In D
+V
4
13
−V
+In B
5
12
+In C
B
C
−In B
6
11
−In C
Out B
7
10
Out C
NC
8
9
NC
Pin Functions
PIN
OPA350
NO.
OPA2350
NO.
OPA4350 SO-14
NO.
OPA4350 SSOP
NO.
I/O
DESCRIPTION
NC
1, 5, 8
—
—
8, 9
—
No internal connection
–In
2
—
—
—
I
Inverting input
+In
3
—
—
—
I
Noninverting input
V–
4
4
11
13
I
Negative power supply
Output
6
—
—
—
O
Output
V+
7
8
4
4
I
Positive power supply
Out A
—
1
1
1
O
Output channel A
–In A
—
2
2
2
I
Inverting input channel A
+In A
—
3
3
3
I
Noninverting input channel A
+In B
—
5
5
5
I
Noninverting input channel B
–In B
—
6
6
6
I
Inverting input channel B
Out B
—
7
7
7
O
Output channel B
Out C
—
—
8
10
O
Output channel C
–In C
—
—
9
11
I
Inverting input channel C
+In C
—
—
10
12
I
Noninverting input channel C
+In D
—
—
12
14
I
Noninverting input channel D
–In D
—
—
13
15
I
Inverting input channel D
Out D
—
—
14
16
O
Output channel D
NAME
Copyright © 2000–2015, Texas Instruments Incorporated
Product Folder Links: OPA350 OPA2350 OPA4350
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OPA350, OPA2350, OPA4350
SBOS099D – SEPTEMBER 2000 – REVISED DECEMBER 2015
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6 Specifications
6.1 Absolute Maximum Ratings
over operating free-air temperature range (unless otherwise noted)
(1)
MIN
Supply voltage
Voltage
Signal input terminals (2)
(V−) − 0.3
(1)
(2)
(3)
V
V
10
mA
Continuous
Operating temperature
Tstg
UNIT
7
(V+) + 0.3
Current
Open short circuit current (3)
MAX
150
°C
Lead temperature (soldering, 10 s)
–55
300
°C
Junction temperature
150
°C
150
°C
Storage temperature
–55
Stresses beyond those listed under Absolute Maximum Ratings may cause permanent damage to the device. These are stress ratings
only, which do not imply functional operation of the device at these or any other conditions beyond those indicated under Recommended
Operating Conditions. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability.
Input terminals are diode-clamped to the power-supply rails. Input signals that can swing more than 0.3 V beyond the supply rails should
be current-limited to 10 mA or less.
Short-circuit to ground, one amplifier per package.
6.2 ESD Ratings
VALUE
UNIT
±1000
V
±1500
V
OPA350, OPA2350, OPA4350 (ALL PACKAGE TYPES)
V(ESD)
Electrostatic discharge
Human-body model (HBM), per ANSI/ESDA/JEDEC JS-001 (1)
OPA350, OPA2350, OPA4350 (SOIC PACKAGES ONLY)
V(ESD)
(1)
(2)
Electrostatic discharge
Charged-device model (CDM), per JEDEC specification JESD22C101 (2)
JEDEC document JEP155 states that 500-V HBM allows safe manufacturing with a standard ESD control process.
JEDEC document JEP157 states that 250-V CDM allows safe manufacturing with a standard ESD control process.
6.3 Recommended Operating Conditions
over operating free-air temperature range (unless otherwise noted)
MIN
NOM
MAX
2.7 (±1.35)
5 (±2.5)
5.5 (±2.75)
V
Specified temperature
–40
25
85
°C
Operating temperature
–55
25
150
°C
Power supply voltage, (V+)-(V-)
4
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UNIT
Copyright © 2000–2015, Texas Instruments Incorporated
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SBOS099D – SEPTEMBER 2000 – REVISED DECEMBER 2015
6.4 Thermal Information: OPA350 and OPA2350
OPA350, OPA2350
THERMAL METRIC (1)
DGK (VSSOP)
P (PDIP)
D (SOIC)
8 PINS
8 PINS
8 PINS
169.2
53.1
140.1
°C/W
RθJC(top) Junction-to-case (top) thermal resistance
62.8
42.5
89.8
°C/W
RθJB
Junction-to-board thermal resistance
89.8
30.3
80.6
°C/W
ψJT
Junction-to-top characterization parameter
7.5
19.7
28.7
°C/W
ψJB
Junction-to-board characterization parameter
88.2
30.2
80.1
°C/W
RθJC(bot) Junction-to-case (bottom) thermal resistance
N/A
N/A
N/A
°C/W
RθJA
(1)
Junction-to-ambient thermal resistance
UNIT
For more information about traditional and new thermal metrics, see the IC Package Thermal Metrics application report, SPRA953.
6.5 Thermal Information: OPA4350
OPA4350
THERMAL METRIC (1)
D (SOIC)
DBQ (SSOP)
UNIT
14 PINS
16 PINS
RθJA
Junction-to-ambient thermal resistance
83.8
115.8
°C/W
RθJC(top)
Junction-to-case (top) thermal resistance
70.7
67
°C/W
RθJB
Junction-to-board thermal resistance
59.5
58.3
°C/W
ψJT
Junction-to-top characterization parameter
11.6
19.9
°C/W
ψJB
Junction-to-board characterization parameter
37.7
57.9
°C/W
RθJC(bot)
Junction-to-case (bottom) thermal resistance
N/A
N/A
°C/W
(1)
For more information about traditional and new thermal metrics, see the Semiconductor and IC Package Thermal Metrics application
report, SPRA953.
Copyright © 2000–2015, Texas Instruments Incorporated
Product Folder Links: OPA350 OPA2350 OPA4350
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OPA350, OPA2350, OPA4350
SBOS099D – SEPTEMBER 2000 – REVISED DECEMBER 2015
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6.6 Electrical Characteristics
VS = 2.7 V to 5.5 V; All specifications at TA = 25°C, RL = 1 kΩ connected to VS/2 and VOUT = VS/2, unless otherwise noted.
PARAMETER
TEST CONDITIONS
MIN
TYP (1)
MAX
UNIT
±150
±500
µV
±1
mV
OFFSET VOLTAGE
VS = 5 V
VOS
Input offset voltage
TA = −40°C to
85°C
vs Temperature
PSRR
TA = –40°C to 85°C
vs Power-supply
rejection ratio
VS = 2.7 V to 5.5 V, VCM = 0 V
Channel separation (dual, quad)
DC
μV/°C
±4
40
150
175
0.15
µV/V
µV/V
INPUT BIAS CURRENT
IB
Input bias current
IOS
Input offset current
±0.5
vs Temperature
±10
See Typical Characteristics
±0.5
±10
pA
pA
NOISE
en
in
Input voltage noise, f = 100 Hz to 400 kHz
4
μVrms
Input voltage noise density, f = 10 kHz
7
nV/√Hz
Input current noise density, f = 100 kHz
5
nV/√Hz
Current noise density, f = 10 kHz
4
fA/√Hz
INPUT VOLTAGE RANGE
VCM
Common-mode voltage range
CMRR
Common-mode rejection ratio
TA = −40°C to 85°C
–0.1
(V+) + 0.1
VS = 2.7 V, −0.1 V < VCM < 2.8 V
66
84
VS = 5.5 V, −0.1 V < VCM < 5.6 V
74
90
TA = −40°C to 85°C,
VS = 5.5 V, −0.1 V < VCM < 5.6 V
74
V
dB
INPUT IMPEDANCE
1013 || 2.5
Differential
13
Common-mode
10
Ω || pF
Ω || pF
|| 6.5
OPEN-LOOP GAIN
Open-loop voltage
gain
AOL
TA = –40°C to
85°C
RL = 10 kΩ, 50 mV < VO < (V+) –50 mV
100
RL = 10 kΩ, 50 mV < VO < (V+) –50 mV
100
RL = 1 kΩ, 200 mV < VO < (V+) –200 mV
100
RL = 1 kΩ, 200 mV < VO < (V+) –200 mV
100
122
dB
120
FREQUENCY RESPONSE (CL = 100 pF)
GBW
Gain-bandwidth product
G=1
38
MHz
SR
Slew rate
G=1
22
V/µs
Settling time
0.1%
0.01%
Overload recovery time
0.22
G = ±1, 2-V Step
VIN × G = VS
THD+N Total harmonic distortion + noise
µs
0.5
0.1
RL = 600 Ω, VO = 2.5 VPP (2), G = 1, f = 1 kHz
µs
0.0006%
Differential gain error
G = 2, RL = 600 Ω, VO = 1.4 V (3)
0.17%
Differential phase error
G = 2, RL = 600 Ω, VO = 1.4 V (3)
0.17
°
OUTPUT
RL = 10 kΩ, AOL ≥ 100 dB
VOUT
Voltage output swing
from rail (4)
IOUT
Output current
ISC
short circuit current
CLOAD
Capacitive load drive
(1)
(2)
(3)
(4)
(5)
6
TA = –40°C to
85°C
10
50
25
200
RL = 10 kΩ, AOL ≥ 100 dB
50
RL = 1 kΩ, AOL ≥ 100 dB
mV
±40 (5)
mA
±80
mA
See Typical Characteristics
VS = 5 V
VOUT = 0.25 V to 2.75 V
NTSC signal generator used. See Figure 31 for test circuit.
Output voltage swings are measured between the output and power supply rails.
See Figure 17.
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SBOS099D – SEPTEMBER 2000 – REVISED DECEMBER 2015
Electrical Characteristics (continued)
VS = 2.7 V to 5.5 V; All specifications at TA = 25°C, RL = 1 kΩ connected to VS/2 and VOUT = VS/2, unless otherwise noted.
PARAMETER
TEST CONDITIONS
MIN
TYP (1)
MAX
UNIT
POWER SUPPLY
VS
TA = −40°C to 85°C
Operating voltage range
2.7
Minimum operating voltage
IQ
Quiescent current
(per amplifier)
5.5
2.5
5.2
TA = –40°C to
85°C
IO = 0
V
V
7.5
8.5
mA
TEMPERATURE RANGE
Specified range
–40
85
°C
Operating range
–55
150
°C
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6.7 Typical Characteristics
All specifications at TA = 25°C, VS = 5 V, and RL = 1 kΩ connected to VS/2, unless otherwise noted.
100
0
160
90
120
80
PSRR, CMRR (dB)
100
φ
−90
60
G
40
PSRR
80
−45
Phase ( )
Voltage Gain (dB)
140
−135
20
70
CMRR
(VS = +5V
VCM = −0.1V to 5.1V)
60
50
40
30
20
0
0.1
1
10
100
1k
10k 100k
Frequency (Hz)
−180
10M 100M
1M
10
0
10
100
1k
10k
100k
1M
10M
Frequency (Hz)
Figure 1. Open-Loop Gain and Phase vs Frequency
Figure 2. Power Supply and Common-Mode Rejection Ratio
vs Frequency
140
10k
100k
100
1k
Voltage Noise
100
10
10
1
Channel Separation (dB)
1k
Current Noise
Current Noise (fA√
Hz)
Voltage Noise (nV√Hz)
130
10k
120
110
100
90
80
70
1
10
100
1k
10k
100k
1M
0.1
10M
Dual and quad devices.
60
10
100
1k
Frequency (Hz)
Figure 3. Input Voltage and Current Noise Spectral Density
vs Frequency
1
(−40dBc)
0.01
G = 10, 3VPP (VO = 1V to 4V)
Harmonic Distortion (%)
THD+N (%)
RL = 600Ω
G = 100, 3VPP (VO = 1V to 4V)
G = 1, 3VPP (VO = 1V to 4V)
Input goes through transition region
0.001
G = 1, 2.5VPP (VO = 0.25V to 2.75V)
Input does NOT go through transition region
100
1k
10k
100k
Figure 5. Total Harmonic Distortion + Noise vs Frequency
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10M
0.1
(−60dBc)
G=1
VO = 2.5VPP
RL = 600Ω
0.01
(−80dBc)
0.001
(−100dBc)
3rd−Harmonic
0.0001
(−120dBc) 1k
10k
100k
1M
Frequency (Hz)
Frequency (Hz)
8
1M
2nd−Harmonic
0.0001
10
100k
Figure 4. Channel Separation vs Frequency
1
0.1
10k
Frequency (Hz)
Figure 6. Harmonic Distortion + Noise vs Frequency
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SBOS099D – SEPTEMBER 2000 – REVISED DECEMBER 2015
Typical Characteristics (continued)
All specifications at TA = 25°C, VS = 5 V, and RL = 1 kΩ connected to VS/2, unless otherwise noted.
130
0.5
Open−Loop Gain (dB)
Phase
0.4
Differential Gain (%)
Differential Phase (° )
G=2
VO = 1.4V
NTSC Signal Generator
See Figure 6 for test circuit.
0.3
0.2
Gain
125
RL = 1kΩ
RL = 10kΩ
120
RL = 600Ω
115
0.1
110
0
0
100 200 300 400
500 600
−75
700 800 900 1000
−50
−25
0
110
75
100
125
40
CMRR, VS = 5.5V
(VCM = −0.1V to +5.6V)
35
100
PSRR
70
Slew Rate (V/µs)
90
CMRR, VS = 2.7V
(VCM =− 0.1V to +2.8V)
30
PSRR (dB)
90
CMRR (dB)
50
Figure 8. Open-Loop Gain vs Temperature
Figure 7. Differential Gain and Phase vs Resistive Load
100
80
25
Temperature ( °C)
Resistive Load ( Ω )
80
Negative Slew Rate
25
Positive Slew Rate
20
15
10
5
60
−75
−50
−25
0
25
50
75
100
70
125
0
−75
−50
−25
0
Temperature ( °C)
Figure 9. Common-Mode and Power-Supply Rejection Ratio
vs Temperature
7.0
100
6.0
90
5.5
IQ
60
4.5
50
4.0
40
30
−50
−25
0
25
50
Temperature ( °C)
75
100
125
Quiescent Current (mA)
70
Short−Circuit Current (mA)
Quiescent Current (mA)
80
−ISC
5.5
3.5
−75
75
100
125
Per Amplifier
6.5
5.0
50
Figure 10. Slew Rate vs Temperature
+ISC
6.0
25
Temperature ( °C)
5.0
4.5
4.0
3.5
3.0
2.0
2.5
3.0
3.5
4.0
4.5
5.0
5.5
Supply Voltage (V)
Figure 11. Quiescent Current and short circuit Current vs
Temperature
Figure 12. Quiescent Current vs Supply Voltage
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Typical Characteristics (continued)
1k
1.5
100
1.0
Input Bias Current (pA)
Input Bias Current (pA)
All specifications at TA = 25°C, VS = 5 V, and RL = 1 kΩ connected to VS/2, unless otherwise noted.
10
1
−50
−25
0
25
50
Temperature (°C)
75
100
0.0
−0.5
−0.5 0.0 0.5 1.0 1.5 2.0 2.5 3.0 3.5 4.0 4.5 5.0 5.5
0.1
−75
0.5
125
Common−Mode Voltage (V)
Figure 13. Input Bias Current vs Temperature
Figure 14. Input Bias Current vs Input Common-Mode
Voltage
100
6
Maximum output
voltage without
slew rate−induced
distortion.
5
Output Voltage (VPP)
10
Output Impedance (Ω)
VS = 5.5V
1
0.1
G = 100
0.01
G = 10
0.001
G=1
10
VS = 2.7V
3
2
1
0
100k
0.0001
1
4
100
1k
10k
100k
1M
10M
100M
1M
Frequency (Hz)
Figure 15. Closed-Loop Output Impedance vs Frequency
100M
Figure 16. Maximum Output Voltage vs Frequency
140
V+
(V+)−1
Open−Loop Gain (dB)
(V+)−2
+25°C
−55°C
+125°C
Depending on circuit configuration
(including closed−loop gain) performance
may be degraded in shaded region.
(V−)+2
+25°C
+125°C
−55 °C
(V−)+1
I OUT = 2.5mA
IOUT = 250µA
130
Output Voltage (V)
10M
Frequency (Hz)
120
110
IOUT = 4.2mA
100
90
80
70
60
(V−)
0
±10
±20
±30
±40
Output Current (mA)
Figure 17. Output Voltage Swing vs Output Current
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0
20
40
60
80
100 120
140 160 180 200
Output Voltage Swing from Rails (mV)
Figure 18. Open-Loop Gain vs Output Voltage Swing
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Typical Characteristics (continued)
All specifications at TA = 25°C, VS = 5 V, and RL = 1 kΩ connected to VS/2, unless otherwise noted.
18
Typical production
distribution of
packaged units.
18
14
Percent of Amplifiers (%)
Percent of Amplifiers (%)
20
Typical distribution of
packaged units.
16
12
10
8
6
4
16
14
12
10
8
6
4
2
2
0
−
500
−450
−400
−350
−
300
−250
−200
−150
−100
−50
0
50
100
150
200
250
300
350
400
450
500
0
0
1
2
3
4
Offset Voltage (µV)
5
6
7
8
9 10 11 12 13 14 15
Offset Voltage Drift (µV/ °C)
Figure 19. Offset Voltage Production Distribution
Figure 20. Offset Voltage Drift Production Distribution
80
10
70
G=1
Settling Time (µs)
Overshoot (%)
60
50
G= −1
40
30
G = ±10
20
0.01%
1
10
0.1%
0
0.1
10
100
1k
10k
100k
1M
−1
−10
Load Capacitance (pF)
Figure 21. Small-Signal Overshoot vs Load Capacitance
Figure 22. Settling Time vs Closed-Loop Gain
1V/div
50mV/div
−100
Closed−Loop Gain (V/V)
100ns/div
200ns/div
Figure 23. Small-Signal Step Response
CL = 100 pF
Figure 24. Large-Signal Step Response
CL = 100 pF
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7 Detailed Description
7.1 Overview
The OPA350 series rail-to-rail CMOS operational amplifiers are optimized for low voltage, single-supply
operation. Rail-to-rail input and output, low noise (5 nV/√Hz), and high speed operation (38 MHz, 22 V/μs) make
the amplifiers ideal for driving sampling Analog-to-Digital (A/D) converters. They are also suited for cell phone PA
control loops and video processing (75-Ω drive capability), as well as audio and general purpose applications.
Single, dual, and quad versions have identical specifications for maximum design flexibility.
7.2 Functional Block Diagram
V+
Reference
Current
VIN+
VINVBIAS1
Class AB
Control
Circuitry
VO
VBIAS2
V(Ground)
7.3 Feature Description
The OPA350 series of operational amplifiers (op amps) are fabricated on a state-of-the-art 0.6 micron CMOS
process. They are unity-gain stable and suitable for a wide range of general purpose applications. Rail-to-rail
input and output make them ideal for driving sampling A/D converters. They are also suited for controlling the
output power in cell phones. These applications often require high speed and low noise. In addition, the OPA350
series offers a low-cost solution for general-purpose and consumer video applications (75-Ω drive capability).
Excellent AC performance makes the OPA350 series suited for audio applications. Their bandwidth, slew rate,
low noise (5 nV/√Hz), low THD (0.0006%), and small package options are ideal for these applications. The class
AB output stage is capable of driving 600-Ω loads connected to any point between V+ and ground.
Rail-to-rail input and output swing significantly increases dynamic range, especially in low voltage supply
applications. Figure 25 shows the input and output waveforms for the OPA350 in unity-gain configuration.
Operation is from a single 5-V supply with a 1-kΩ load connected to VS/2. The input is a 5 VPP sinusoid. Output
voltage swing is approximately 4.95 VPP.
Power supply pins should be bypassed with 0.01-μF ceramic capacitors.
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Feature Description (continued)
VS = +5, G = +1, RL = 1kΩ
5V
0
5V
1.25V/div
VIN
VOUT
0
Figure 25. Rail-to-Rail Input and Output
7.3.1 Operating Voltage
OPA350 series operational amplifiers are fully specified from 2.7 V to 5.5 V. Supply voltage may range from 2.5
V to 5.5 V. Parameters are tested over the specified supply range: a feature of the OPA350 series. In addition,
many specifications apply from −40°C to 85°C. Most behavior remains virtually unchanged throughout the full
operating voltage range. Parameters that vary significantly with operating voltage or temperature are shown in
Typical Characteristics.
7.3.2 Rail-to-Rail Input
The tested input common-mode voltage range of the OPA350 series extends 100 mV beyond the supply rails.
This is achieved with a complementary input stage: an N-channel input-differential pair in parallel with a Pchannel differential pair, as shown in Figure 26. The N-channel pair is active for input voltages close to the
positive rail, typically (V+) – 1.8 V to 100 mV above the positive supply, while the P-channel pair is on for inputs
from 100 mV below the negative supply to approximately (V+) – 1.8 V. There is a small transition region, typically
(V+) – 2 V to (V+) – 1.6 V, in which both pairs are on. This 400-mV transition region can vary ±400 mV with
process variation. Thus, the transition region (both input stages on) can range from (V+) – 2.4 V to (V+) – 2 V on
the low end, up to (V+) – 1.6 V to (V+) – 1.2 V on the high end.
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Feature Description (continued)
V+
Reference
Current
VIN+
VIN−
VBIAS1
Class AB
Control
Circuitry
VO
VBIAS2
V−
(Ground)
Figure 26. Simplified Schematic
OPA350 series operational amplifiers are laser-trimmed to reduce offset voltage difference between the Nchannel and P-channel input stages, resulting in improved common-mode rejection and a smooth transition
between the N-channel pair and the P-channel pair. However, within the 400-mV transition region PSRR, CMRR,
offset voltage, offset drift, and THD may be degraded compared to operation outside this region.
A double-folded cascode adds the signal from the two input pairs and presents a differential signal to the class
AB output stage. Normally, input bias current is approximately 500 fA. However, large inputs (greater than 300
mV beyond the supply rails) can turn on the input protection diodes, causing excessive current to flow in or out of
the input pins. Momentary voltages greater than 300 mV beyond the power supply can be tolerated if the current
on the input pins is limited to 10 mA. This is easily accomplished with an input resistor, as shown in Figure 27.
Many input signals are inherently current-limited to less than 10 mA; therefore, a limiting resistor is not required.
V+
IOVERLOAD
10mA max
OPAx350
VOUT
VIN
5kΩ
Figure 27. Input Current Protection for Voltages Exceeding the Supply Voltage
7.3.3 Rail-to-Rail Output
A class AB output stage with common-source transistors achieves rail-to-rail output. For light resistive loads (>10
kΩ), the output voltage swing is typically ten millivolts from the supply rails. With heavier resistive loads (600 Ω to
10 kΩ), the output can swing to within a few tens of millivolts from the supply rails and maintain high open-loop
gain. See Figure 17 and Figure 18 for more information.
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Feature Description (continued)
7.3.4 Capacitive Load and Stability
OPA350 series operational amplifiers can drive a wide range of capacitive loads. However, all operational
amplifiers under certain conditions may become unstable. operational amplifier configuration, gain, and load
value are just a few of the factors to consider when determining stability. An operational amplifier in unity-gain
configuration is the most susceptible to the effects of capacitive load. The capacitive load reacts with the output
impedance of the operational amplifier, along with any additional load resistance, to create a pole in the smallsignal response that degrades the phase margin.
In unity gain, OPA350 series operational amplifiers perform well with large capacitive loads. Increasing gain
enhances the ability of the amplifier to drive more capacitance. Figure 21 shows performance with a 1-kΩ
resistive load. Increasing load resistance improves capacitive load drive capability.
7.3.5 Driving A/D Converters
OPA350 series operational amplifiers are optimized for driving medium speed (up to 500 kHz) sampling A/D
converters, and also offer excellent performance for higher speed converters. The OPA350 series provides an
effective means of buffering the input capacitance of the A/D and resulting charge injection while providing signal
gain.
Figure 28 shows the OPA350 driving an ADS7861. The ADS7861 is a dual, 500 kHz, 12-bit sampling converter
in the tiny SSOP-24 package. When used with the miniature package options of the OPA350 series, the
combination is ideal for space-limited applications. For further information, consult the ADS7861 data sheet,
Dual, 500kSPS, 12-Bit, 2 + 2 Channel, Simultaneous Sampling ANALOG-TO-DIGITAL CONVERTER
(SBAS110).
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Feature Description (continued)
CB1
2
4
1
1/ 4
3
VIN B1
+5V
2kΩ
2kΩ
O P A 43 5 0
0.1µF
0.1µF
CB0
24
2kΩ
2kΩ
2
3
6
7
1/ 4
5
VIN B0
4
O P A 43 5 0
5
6
CA1
7
2kΩ
2kΩ
8
9
9
VIN A1
10
8
1/ 4
10
13
+VD
O P A 43 5 0
11
CA0
+VA
CH B1+
SERIAL DATA A
CH B1−
SERIAL DATA B
CH B0+
BUSY
CH B0−
CLOCK
CH A1+
CS
CH A1−
ADS7861
RD
CH A0+
CONVST
CH A0−
A0
REFIN
M0
REFOUT
M1
DGND
1
23
22
21
20
19
18
Serial
Interface
17
16
15
14
AGND
12
2kΩ
2kΩ
12
14
1/ 4
VIN A0
13
O P A 43 5 0
11
VIN = 0V to 2.45V for 0V to 4.9V output.
Choose CB1, CB0, CA1, CA0 to filter high frequency noise.
Figure 28. OPA4350 Driving Sampling A/D Converter
7.3.6 Output Impedance
The low-frequency open-loop output impedance of the common-source output stage of the OPA350 is
approximately 1 kΩ. When the operational amplifier is connected with feedback, this value is reduced
significantly by the loop gain of the operational amplifier. For example, with 122 dB of open-loop gain, the output
impedance is reduced in unity-gain to less than 0.001 Ω. For each decade rise in the closed-loop gain, the loop
gain is reduced by the same amount which results in a ten-fold increase in effective output impedance (see
Figure 15).
At higher frequencies, the output impedance rises as the open-loop gain of the operational amplifier drops.
However, at these frequencies the output also becomes capacitive due to parasitic capacitance. This prevents
the output impedance from becoming too high, which can cause stability problems when driving capacitive loads.
The OPA350 has excellent capacitive load drive capability for an operational amplifier with its bandwidth.
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7.4 Device Functional Modes
The OPAx350 has a single functional mode and is operational when the power-supply voltage is greater than
2.7 V (±1.35 V). The maximum power supply voltage for the OPAx350 is 5.5V (±2.75 V).
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8 Application and Implementation
NOTE
Information in the following applications sections is not part of the TI component
specification, and TI does not warrant its accuracy or completeness. TI’s customers are
responsible for determining suitability of components for their purposes. Customers should
validate and test their design implementation to confirm system functionality.
8.1 Application Information
Low pass filters are commonly employed in signal processing applications to reduce noise and prevent aliasing.
The OPAx350 are ideally suited to construct high speed, high precision active filters. Figure 29 illustrates a
second order low pass filter commonly encountered in signal processing applications.
8.2 Typical Applications
8.2.1 Second Order Low Pass Filter
R4
2.94 k
C5
1 nF
R1
590
R3
499
Input
C2
39 nF
±
Output
+
OPAx350
Figure 29. Second Order Low Pass Filter
8.2.1.1 Design Requirements
Use the following parameters for this design example:
• Gain = 5 V/V (inverting gain).
• Low pass cutoff frequency = 25 kHz.
• Second order Chebyshev filter response with 3-dB gain peaking in the passband.
8.2.1.2 Detailed Design Procedure
The infinite-gain multiple-feedback circuit for a low-pass network function is shown in Equation 1. Use Equation 2
to calculate the voltage transfer function.
1 R1R3C2C5
Output
s
2
Input
s
s C2 1 R1 1 R3 1 R4 1 R3R4C2C5
(1)
This circuit produces a signal inversion. For this circuit the gain at DC and the low pass cutoff frequency can be
calculated using Equation 2.
R4
Gain
R1
fC
1
2S
1 R3R 4 C2C5
(2)
Software tools are readily available to simplify filter design. WEBENCH® Filter Designer is a simple, powerful,
and easy-to-use active filter design program. The WEBENCH Filter Designer lets you create optimized filter
designs using a selection of TI operational amplifiers and passive components from TI's vendor partners.
Available as a web based tool from the WEBENCH® Design Center, WEBENCH® Filter Designer allows you to
design, optimize, and simulate complete multi-stage active filter solutions within minutes.
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Typical Applications (continued)
8.2.1.3 Application Curve
20
Gain (db)
0
-20
-40
-60
100
1k
10k
Frequency (Hz)
100k
1M
Figure 30. OPAx350 2nd Order 25-kHz, Chebyshev, Low-Pass Filter
8.2.2 Single-Supply Video Line Driver
Figure 31 shows a circuit for a single supply, G = 2 composite video line driver. The synchronized outputs of a
composite video line driver extend below ground. As shown, the input to the operational amplifier should be ACcoupled and shifted positively to provide adequate signal swing to account for these negative signals in a singlesupply configuration.
The input is terminated with a 75-Ω resistor and AC-coupled with a 47-μF capacitor to a voltage divider that
provides the DC bias point to the input. In Figure 31, this point is approximately (V−) + 1.7 V. Setting the optimal
bias point requires some understanding of the nature of composite video signals. For best performance, avoid
the distortion caused by the transition region of the complementary input stage of the OPA350. See the
discussion of rail-to-rail input in Rail-to-Rail Input.
RF
1kΩ
RG
1kΩ
+5V
C1
220µF
C4
0.1µF
0.1µF
2
+
7
6
C5
1000µF
ROUT
VOUT
RL
3
R1
75Ω
Cable
OPA350
C2
47µF
Video
In
10µF
4
R2
5kΩ
R3
5kΩ
R4
5kΩ
+5V (pin 7)
C3
10µF
Figure 31. Single-Supply Video Line Driver
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Typical Applications (continued)
8.2.3 Adding a Feedback Capacitor to Improve Response
For optimum settling time and stability with high-impedance feedback networks, it may be necessary to add a
feedback capacitor across the feedback resistor, RF, as shown in Figure 32. This capacitor compensates for the
zero created by the feedback network impedance and the input capacitance of the OPA350 (and any parasitic
layout capacitance). The effect becomes more significant with higher impedance networks.
CF
RF
R IN
VIN
V+
CIN
RIN • CIN = RF • CF
VOUT
O PA350
CL
CIN
Where CIN is equal to the OPA350’s input
capacitance (approximately 9pF) plus any
parasitic layout capacitance.
Figure 32. Feedback Capacitor Improves Dynamic Performance
A variable capacitor can be used for the feedback capacitor, because input capacitance may vary between
operational amplifiers and layout capacitance is difficult to determine. For the circuit shown in Figure 32, the
value of the variable feedback capacitor should be chosen so that the input resistance times the input
capacitance of the OPA350 (typically 9 pF) plus the estimated parasitic layout capacitance equals the feedback
capacitor times the feedback resistor:
RIN × CIN = RF × CF
where
•
CIN is equal to the input capacitance of the OPA350 (sum of differential and common-mode) plus the layout
capacitance.
(3)
The capacitor can be varied until optimum performance is obtained.
8.2.4 Two Op-Amp Instrumentation Amplifier With Improved High-Frequency Common-Mode Rejection
The OPAx350 is well suited for high input impedance applications such as an instrumentation amplifier. The two
amplifier configuration shown in Figure 33 rejects any common mode signals and senses the small differential
input voltage developed by the resistive bridge. The voltage reference sets the output to 2.5 V when the
differential signal developed by the bridge is zero. The high common mode rejection versus frequency response
of the OPAx350, rejects and common mode noise that may be coupled into the bridge circuit from the bridge
excitation source. The gain of the circuit is determined by RG according to the equation shown in Figure 33.
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Typical Applications (continued)
+5V
50kΩ
(2.5V)
8
RG
REF1004−2.5
4
R1
100kΩ
+5V
R2
25kΩ
R3
25kΩ
1/ 2
R4
100kΩ
O P A 2 35 0
1/ 2
VO
O P A 23 5 0
G=5+
RL
10kΩ
200kΩ
RG
Figure 33. Two Op-Amp Instrumentation Amplifier With Improved High-Frequency Common-Mode
Rejection Schematic
8.2.5 10-kHz High-Pass Filter
High-pass filters are used to reject DC signals and low-frequency time varying signals such as drift versus
temperature. Figure 34 illustrates a high-pass filter with a 10 kHz low-frequency cutoff frequency.
R1
10.5kΩ
+2.5V
C1
1830pF
C2
270pF
VOUT
OPA350
RL
20kΩ
VIN
R2
49.9kΩ
−2.5V
Figure 34. 10-kHz High-Pass Filter
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9 Power Supply Recommendations
The OPAx350 are specified for operation from 2.7 V to 5.5 V (±1.35 V to ±2.75 V); many specifications apply
from –40°C to 85°C. Parameters that can exhibit significant variance with regard to operating voltage or
temperature are presented in the Typical Characteristics.
10 Layout
10.1 Layout Guidelines
For best operational performance of the device, use good PCB layout practices, including:
• Noise can propagate into analog circuitry through the power pins of the circuit as a whole and operational
amplifier itself. Bypass capacitors are used to reduce the coupled noise by providing low-impedance
power sources local to the analog circuitry.
– Connect low-ESR, 0.1-µF ceramic bypass capacitors between each supply pin and ground, placed as
close to the device as possible. A single bypass capacitor from V+ to ground is applicable for singlesupply applications.
• Separate grounding for analog and digital portions of circuitry is one of the simplest and most-effective
methods of noise suppression. One or more layers on multilayer PCBs are usually devoted to ground
planes. A ground plane helps distribute heat and reduces EMI noise pickup. Make sure to physically
separate digital and analog grounds paying attention to the flow of the ground current. For more detailed
information, see Circuit Board Layout Techniques (SLOA089).
• To reduce parasitic coupling, run the input traces as far away from the supply or output traces as
possible. If these traces cannot be kept separate, crossing the sensitive trace perpendicular is much
better as opposed to in parallel with the noisy trace.
• Place the external components as close to the device as possible. As illustrated in Figure 35, keeping RF
and RG close to the inverting input minimizes parasitic capacitance.
• Keep the length of input traces as short as possible. Always remember that the input traces are the most
sensitive part of the circuit.
• Consider a driven, low-impedance guard ring around the critical traces. A guard ring can significantly
reduce leakage currents from nearby traces that are at different potentials.
• Cleaning the PCB following board assembly is recommended for best performance.
• Any precision integrated circuit may experience performance shifts due to moisture ingress into the
plastic package. Following any aqueous PCB cleaning process, baking the PCB assembly is
recommended to remove moisture introduced into the device packaging during the cleaning process. A
low temperature, post cleaning bake at 85°C for 30 minutes is sufficient for most circumstances.
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10.2 Layout Example
+
VIN
VOUT
RG
RF
(Schematic Representation)
Run the input traces
as far away from
the supply lines
as possible
Place components
close to device and to
each other to reduce
parasitic errors
VS+
RF
N/C
N/C
GND
±IN
V+
VIN
+IN
OUTPUT
V±
N/C
RG
Use low-ESR,
ceramic bypass
capacitor
GND
GND
Use low-ESR, ceramic
bypass capacitor
VOUT
VS±
Ground (GND) plane on another layer
Figure 35. Operational Amplifier Board Layout for Noninverting Configuration
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11 Device and Documentation Support
11.1 Device Support
11.1.1 Development Support
11.1.1.1 TINA-TI™ (Free Software Download)
TINA™ is a simple, powerful, and easy-to-use circuit simulation program based on a SPICE engine. TINA-TI™ is
a free, fully-functional version of the TINA software, preloaded with a library of macro models in addition to a
range of both passive and active models. TINA-TI provides all the conventional DC, transient, and frequency
domain analysis of SPICE, as well as additional design capabilities.
Available as a free download from the Analog eLab Design Center, TINA-TI offers extensive post-processing
capability that allows users to format results in a variety of ways. Virtual instruments offer the ability to select
input waveforms and probe circuit nodes, voltages, and waveforms, creating a dynamic quick-start tool.
WEBENCH® Filter Designer is a simple, powerful, and easy-to-use active filter design program. The WEBENCH
Filter Designer lets you create optimized filter designs using a selection of TI operational amplifiers and passive
components from TI's vendor partners. Available as a web based tool from the WEBENCH® Design Center,
WEBENCH® Filter Designer allows you to design, optimize, and simulate complete multi-stage active filter
solutions within minutes.
NOTE
These files require that either the TINA software (from DesignSoft™) or TINA-TI software
be installed. Download the free TINA-TI software from the TINA-TI folder.
11.1.1.2 TI Precision Designs
The OPA350 is featured in several TI Precision Designs, available online at
http://www.ti.com/ww/en/analog/precision-designs/. TI Precision Designs are analog solutions created by TI’s
precision analog applications experts and offer the theory of operation, component selection, simulation,
complete PCB schematic and layout, bill of materials, and measured performance of many useful circuits.
11.2 Documentation Support
11.2.1 Related Documentation
For related documentation see the following:
• Circuit Board Layout Techniques, SLOA089
• Op Amps for Everyone, SLOD006
• Compensate Transimpedance Amplifiers Intuitively, SBOS055
• Noise Analysis for High Speed op Amps, SBOA066
11.3 Related Links
The table below lists quick access links. Categories include technical documents, support and community
resources, tools and software, and quick access to sample or buy.
Table 1. Related Links
24
PARTS
PRODUCT FOLDER
SAMPLE & BUY
TECHNICAL
DOCUMENTS
TOOLS &
SOFTWARE
SUPPORT &
COMMUNITY
OPA350
Click here
Click here
Click here
Click here
Click here
OPA2350
Click here
Click here
Click here
Click here
Click here
OPA4350
Click here
Click here
Click here
Click here
Click here
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11.4 Community Resources
The following links connect to TI community resources. Linked contents are provided "AS IS" by the respective
contributors. They do not constitute TI specifications and do not necessarily reflect TI's views; see TI's Terms of
Use.
TI E2E™ Online Community TI's Engineer-to-Engineer (E2E) Community. Created to foster collaboration
among engineers. At e2e.ti.com, you can ask questions, share knowledge, explore ideas and help
solve problems with fellow engineers.
Design Support TI's Design Support Quickly find helpful E2E forums along with design support tools and
contact information for technical support.
11.5 Trademarks
TINA-TI, E2E are trademarks of Texas Instruments.
TINA, DesignSoft are trademarks of DesignSoft, Inc.
All other trademarks are the property of their respective owners.
11.6 Electrostatic Discharge Caution
These devices have limited built-in ESD protection. The leads should be shorted together or the device placed in conductive foam
during storage or handling to prevent electrostatic damage to the MOS gates.
11.7 Glossary
SLYZ022 — TI Glossary.
This glossary lists and explains terms, acronyms, and definitions.
12 Mechanical, Packaging, and Orderable Information
The following pages include mechanical, packaging, and orderable information. This information is the most
current data available for the designated devices. This data is subject to change without notice and revision of
this document. For browser-based versions of this data sheet, refer to the left-hand navigation.
Copyright © 2000–2015, Texas Instruments Incorporated
Product Folder Links: OPA350 OPA2350 OPA4350
Submit Documentation Feedback
25
PACKAGE OPTION ADDENDUM
www.ti.com
24-Aug-2018
PACKAGING INFORMATION
Orderable Device
Status
(1)
Package Type Package Pins Package
Drawing
Qty
Eco Plan
Lead/Ball Finish
MSL Peak Temp
(2)
(6)
(3)
Op Temp (°C)
Device Marking
(4/5)
OPA2350EA/250
ACTIVE
VSSOP
DGK
8
250
Green (RoHS
& no Sb/Br)
CU NIPDAUAG
Level-2-260C-1 YEAR
-40 to 85
D50
OPA2350EA/250G4
ACTIVE
VSSOP
DGK
8
250
Green (RoHS
& no Sb/Br)
CU NIPDAUAG
Level-2-260C-1 YEAR
-40 to 85
D50
OPA2350EA/2K5
ACTIVE
VSSOP
DGK
8
2500
Green (RoHS
& no Sb/Br)
CU NIPDAUAG
Level-2-260C-1 YEAR
-40 to 85
D50
OPA2350EA/2K5G4
ACTIVE
VSSOP
DGK
8
2500
Green (RoHS
& no Sb/Br)
CU NIPDAUAG
Level-2-260C-1 YEAR
-40 to 85
D50
OPA2350UA
ACTIVE
SOIC
D
8
75
Green (RoHS
& no Sb/Br)
CU NIPDAU
Level-2-260C-1 YEAR
-40 to 85
OPA
2350UA
OPA2350UA/2K5
ACTIVE
SOIC
D
8
2500
Green (RoHS
& no Sb/Br)
CU NIPDAU
Level-2-260C-1 YEAR
-40 to 85
OPA
2350UA
OPA2350UA/2K5G4
ACTIVE
SOIC
D
8
2500
Green (RoHS
& no Sb/Br)
CU NIPDAU
Level-2-260C-1 YEAR
-40 to 85
OPA
2350UA
OPA2350UAG4
ACTIVE
SOIC
D
8
75
Green (RoHS
& no Sb/Br)
CU NIPDAU
Level-2-260C-1 YEAR
-40 to 85
OPA
2350UA
OPA350EA/250
ACTIVE
VSSOP
DGK
8
250
Green (RoHS
& no Sb/Br)
CU NIPDAUAG
Level-2-260C-1 YEAR
-40 to 85
C50
OPA350EA/250G4
ACTIVE
VSSOP
DGK
8
250
Green (RoHS
& no Sb/Br)
CU NIPDAUAG
Level-2-260C-1 YEAR
-40 to 85
C50
OPA350EA/2K5
ACTIVE
VSSOP
DGK
8
2500
Green (RoHS
& no Sb/Br)
CU NIPDAUAG
Level-2-260C-1 YEAR
-40 to 85
C50
OPA350PA
ACTIVE
PDIP
P
8
50
Green (RoHS
& no Sb/Br)
CU NIPDAU
N / A for Pkg Type
-40 to 85
OPA350PA
OPA350UA
ACTIVE
SOIC
D
8
75
Green (RoHS
& no Sb/Br)
CU NIPDAU
Level-2-260C-1 YEAR
-40 to 85
OPA
350UA
OPA350UA/2K5
ACTIVE
SOIC
D
8
2500
Green (RoHS
& no Sb/Br)
CU NIPDAU
Level-2-260C-1 YEAR
-40 to 85
OPA
350UA
OPA350UA/2K5G4
ACTIVE
SOIC
D
8
2500
Green (RoHS
& no Sb/Br)
CU NIPDAU
Level-2-260C-1 YEAR
-40 to 85
OPA
350UA
OPA350UAG4
ACTIVE
SOIC
D
8
75
Green (RoHS
& no Sb/Br)
CU NIPDAU
Level-2-260C-1 YEAR
-40 to 85
OPA
350UA
OPA4350EA/250
ACTIVE
SSOP
DBQ
16
250
Green (RoHS
& no Sb/Br)
CU NIPDAU
Level-2-260C-1 YEAR
Addendum-Page 1
OPA
4350EA
Samples
PACKAGE OPTION ADDENDUM
www.ti.com
24-Aug-2018
Orderable Device
Status
(1)
Package Type Package Pins Package
Drawing
Qty
Eco Plan
Lead/Ball Finish
MSL Peak Temp
(2)
(6)
(3)
Op Temp (°C)
Device Marking
(4/5)
OPA4350EA/2K5
ACTIVE
SSOP
DBQ
16
2500
Green (RoHS
& no Sb/Br)
CU NIPDAU
Level-2-260C-1 YEAR
-40 to 85
OPA
4350EA
OPA4350UA
ACTIVE
SOIC
D
14
50
Green (RoHS
& no Sb/Br)
CU NIPDAU
Level-2-260C-1 YEAR
OPA4350UA
OPA4350UA/2K5
ACTIVE
SOIC
D
14
2500
Green (RoHS
& no Sb/Br)
CU NIPDAU
Level-2-260C-1 YEAR
OPA4350UA
OPA4350UA/2K5G4
ACTIVE
SOIC
D
14
2500
Green (RoHS
& no Sb/Br)
CU NIPDAU
Level-2-260C-1 YEAR
OPA4350UA
(1)
The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2)
RoHS: TI defines "RoHS" to mean semiconductor products that are compliant with the current EU RoHS requirements for all 10 RoHS substances, including the requirement that RoHS substance
do not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, "RoHS" products are suitable for use in specified lead-free processes. TI may
reference these types of products as "Pb-Free".
RoHS Exempt: TI defines "RoHS Exempt" to mean products that contain lead but are compliant with EU RoHS pursuant to a specific EU RoHS exemption.
Green: TI defines "Green" to mean the content of Chlorine (Cl) and Bromine (Br) based flame retardants meet JS709B low halogen requirements of
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