TPA0223
2-W MONO AUDIO POWER AMPLIFIER
WITH HEADPHONE DRIVE
SLOS277C – JANUARY 2000 – REVISED NOVEMBER 2002
D Ideal for Notebook Computers, PDAs, and
D
D
D
D
D
D
D
D
D
D
D
Other Small Portable Audio Devices
2 W Into 4-Ω From 5-V Supply
0.6 W Into 4-Ω From 3-V Supply
Stereo Head Phone Drive
Separate Inputs for the Mono (BTL) Signal
and Stereo (SE) Left/Right Signals
Wide Power Supply Compatibility
3 V to 5 V
Meets PC99 Desktop Specs (Target)
Low Supply Current
– 11 mA Typical at 5 V
– 10 mA Typical at 3 V
Shutdown Control . . . 1 µA Typical
Shutdown Pin Is TTL Compatible
–40°C to 85°C Operating Temperature
Range
Space-Saving, Thermally-Enhanced MSOP
Packaging
DGQ PACKAGE
(TOP VIEW)
MONO–IN
SHUTDOWN
VDD
BYPASS
RIN
1
2
3
4
5
10
9
8
7
6
LO/MO–
LIN
GND
ST/MN
RO/MO+
description
The TPA0223 is a 2-W mono bridge-tied-load (BTL) amplifier designed to drive speakers with as low as 4-Ω
impedance. The amplifier can be reconfigured on the fly to drive two stereo single-ended (SE) signals into head
phones. This makes the device ideal for small notebook computers, PDAs, digital personal audio players,
anyplace a mono speaker and stereo headphones are required. From a 5-V supply, the TPA0223 can deliver
2 W of power into a 4-Ω speaker.
The gain of the input stage is set by the user-selected input resistor and a 50-kΩ internal feedback resistor
(AV = – RF/ RI). The power stage is internally configured with a gain of –1.25 V/V in SE mode, and –2.5 V/V in
BTL mode. Thus, the overall gain of the amplifier is 62.5 kΩ/ RI in SE mode and 125 kΩ/ RI in BTL mode. The
input terminals, high-impedance CMOS inputs, can be used as summing nodes.
The TPA0223 is available in the 10-pin thermally-enhanced MSOP package (DGQ) and operates over an
ambient temperature range of –40°C to 85°C.
Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of
Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet.
Copyright 2002, Texas Instruments Incorporated
PRODUCTION DATA information is current as of publication date.
Products conform to specifications per the terms of Texas Instruments
standard warranty. Production processing does not necessarily include
testing of all parameters.
POST OFFICE BOX 655303
• DALLAS, TEXAS 75265
1
TPA0223
2-W MONO AUDIO POWER AMPLIFIER
WITH HEADPHONE DRIVE
SLOS277C – JANUARY 2000 – REVISED NOVEMBER 2002
CB
4
p140
BYPASS
VDD
3
VDD
GND
8
VDD
BYPASS
Mono
Audio
Input
Right
Audio
Input
CI
CI
50 kΩ
RI
1.25*R
100 kΩ
1
MONO-IN
5
RIN
M
U
X
R
–
–
+
CC
RO/MO+
6
+
RI
BYPASS
BYPASS
100 kΩ
50 kΩ
Stereo/Mono
Control
ST/MN
7
LO/MO–
10
50 kΩ
1.25*R
Left
Audio
Input
CI
RI
9
LIN
M
U
X
R
–
–
+
CC
+
1 kΩ
BYPASS
BYPASS
From
System Control
2
SHUTDOWN
Shutdown
and Depop
Circuitry
AVAILABLE OPTIONS
TA
PACKAGED DEVICES
MSOP†
(DGQ)
MSOP
SYMBOLIZATION
– 40°C to 85°C
TPA0223DGQ
AEI
† The DGQ package are available taped and reeled. To order a taped and reeled part, add the
suffix R to the part number (e.g., TPA0223DGQR).
2
POST OFFICE BOX 655303
• DALLAS, TEXAS 75265
TPA0223
2-W MONO AUDIO POWER AMPLIFIER
WITH HEADPHONE DRIVE
SLOS277C – JANUARY 2000 – REVISED NOVEMBER 2002
Terminal Functions
TERMINAL
NAME
NO.
I/O
DESCRIPTION
I
BYPASS is the tap to the voltage divider for internal mid-supply bias. This terminal should be connected to a
0.1-µF to 1-µF capacitor.
BYPASS
4
GND
8
LIN
9
I
Left-channel input terminal
LO/MO–
10
O
Left-output in SE mode and mono negative output in BTL mode.
MONO-IN
1
I
Mono input terminal
RIN
5
I
Right-channel input terminal
RO/MO+
6
O
Right-output in SE mode and mono positive output in BTL mode
SHUTDOWN
2
I
SHUTDOWN places the entire device in shutdown mode when held low. TTL compatible input.
ST/MN
7
I
Selects between stereo and mono mode. When held high, the amplifier is in SE stereo mode, while held low,
the amplifier is in BTL mono mode.
VDD
3
I
VDD is the supply voltage terminal.
Ground terminal
absolute maximum ratings over operating free-air temperature range (unless otherwise noted)†
Supply voltage, VDD . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 6 V
Input voltage range, VI . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . –0.3 V to VDD +0.3 V
Continuous total power dissipation . . . . . . . . . . . . . . . . . . . . . internally limited (see Dissipation Rating Table)
Operating free-air temperature range, TA (see Table 3) . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . – 40°C to 85°C
Operating junction temperature range, TJ . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . – 40°C to 150°C
Storage temperature range, Tstg . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . –65°C to 150°C
Lead temperature 1,6 mm (1/16 inch) from case for 10 seconds . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 260°C
† Stresses beyond those listed under “absolute maximum ratings” may cause permanent damage to the device. These are stress ratings only, and
functional operation of the device at these or any other conditions beyond those indicated under “recommended operating conditions” is not
implied. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability.
DISSIPATION RATING TABLE
PACKAGE
DGQ
TA ≤ 25°C
2.14 W‡
DERATING FACTOR
17.1 mW/°C
TA = 70°C
1.37 W
TA = 85°C
1.11 W
‡ See the Texas Instruments document, PowerPAD Thermally Enhanced Package Application Report
(SLMA002), for more information on the PowerPAD package. The thermal data was measured on a PCB
layout based on the information in the section entitled Texas Instruments Recommended Board for PowerPAD
on page 33 of that document.
recommended operating conditions
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
Supply voltage, VDD
High-level
input
High
level in
ut voltage, VIH
ST/MN
VDD = 3 V
VDD = 5 V
SHUTDOWN
Low-level
Low
level in
input
ut voltage, VIL
ST/MN
MIN
MAX
2.5
5.5
UNIT
V
2.7
4.5
V
2
VDD = 3 V
VDD = 5 V
1.65
2.75
V
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
SHUTDOWN
0.8
Operating free-air temperature, TA
– 40
85
°C
PowerPAD is a trademark of Texas Instruments.
POST OFFICE BOX 655303
• DALLAS, TEXAS 75265
3
TPA0223
2-W MONO AUDIO POWER AMPLIFIER
WITH HEADPHONE DRIVE
SLOS277C – JANUARY 2000 – REVISED NOVEMBER 2002
electrical characteristics at specified free-air temperature, VDD = 3 V, TA = 25°C (unless otherwise
noted)
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁ
ÁÁÁÁÁÁ
ÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁ
ÁÁÁ
ÁÁÁ
ÁÁÁ
ÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
PARAMETER
TEST CONDITIONS
MIN
|VOO|
Output offset voltage (measured differentially)
ST/MN = 0, RL = 4 Ω, SHUTDOWN = 2 V
IDD
IDD(SD)
Supply current
VDD = 2.5 V, SHUTDOWN = 2 V
SHUTDOWN = 0
|IIH|
High level input current
High-level
|IIL|
Low level input current
Low-level
RF
Feedback resistor
Supply current, shutdown mode
TYP
MAX
mV
10
13
mA
1
10
µA
SHUTDOWN, VDD = 3.3 V,
ST/MN, VDD = 3.3 V,
VI = VDD
VI = VDD
1
SHUTDOWN, VDD = 3.3 V,
VI = 0 V
VI = 0 V
1
ST/MN, VDD = 3.3 V,
VDD = 2.5 V, RL = 4 Ω, ST/MN = 1.375 V,
SHUTDOWN = 2 V
1
1
48
UNIT
30
50
57
µA
A
µA
A
kΩ
operating characteristics, VDD = 3 V, TA = 25°C, RL = 4 Ω
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁ
ÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
PARAMETER
PO
power see Note 1
Output power,
THD + N
Total harmonic distortion plus noise
BOM
Maximum output power bandwidth
TEST CONDITIONS
MIN
THD = 1%,
BTL mode
THD = 0.1%,
SE mode,
PO = 500 mW,
Gain = 2,
f = 20 Hz to 20 kHz
TYP
MAX
UNIT
660
RL = 32 Ω
mW
33
0.3%
THD = 2%
20
kHz
NOTE 1: Output power is measured at the output terminals of the device at f = 1 kHz.
electrical characteristics at specified free-air temperature, VDD = 5 V, TA = 25°C (unless otherwise
noted)
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁ
ÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁ
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
|VOO|
Output offset voltage (measured differentially)
ST/MN = 0, RL = 4 Ω, SHUTDOWN = 2 V
IDD
IDD(SD)
Supply current
SHUTDOWN = 2 V
Supply current, shutdown mode
SHUTDOWN = 0 V
High level input current
High-level
SHUTDOWN, VDD = 5.5 V,
ST/MN, VDD = 5.5 V,
VI = VDD
VI = VDD
1
|IIH|
Low level input current
Low-level
SHUTDOWN, VDD = 5.5 V,
VI = 0 V
VI = 0 V
1
|IIL|
ST/MN, VDD = 5.5 V,
UNIT
30
mV
11
17
mA
1
10
µA
1
1
µA
A
µA
A
operating characteristics, VDD = 5 V, TA = 25°C, RL = 4 Ω
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁ
ÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
ÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁÁ
PARAMETER
PO
power see Note 1
Output power,
THD + N
Total harmonic distortion plus noise
BOM
Maximum output power bandwidth
TEST CONDITIONS
THD = 1%,
BTL mode
THD = 0.1%,
SE mode,
PO = 1 W,
Gain = 2.5,
RL = 32 Ω
f = 20 Hz to 20 kHz
THD = 2%
NOTE 1: Output power is measured at the output terminals of the device at f = 1 kHz.
4
POST OFFICE BOX 655303
• DALLAS, TEXAS 75265
MIN
TYP
MAX
UNIT
2
W
95
mW
0.2%
20
kHz
TPA0223
2-W MONO AUDIO POWER AMPLIFIER
WITH HEADPHONE DRIVE
SLOS277C – JANUARY 2000 – REVISED NOVEMBER 2002
TYPICAL CHARACTERISTICS
Table of Graphs
FIGURE
Supply ripple rejection ratio
vs Frequency
IDD
Supply current
vs Supply voltage
1, 2
3
vs Supply voltage
4, 5
PO
Output power
vs Load resistance
6, 7
vs Frequency
THD+N
Total harmonic distortion plus noise
Vn
Output noise voltage
8, 9, 10, 11
12, 13, 14, 15,
16, 17
vs Output power
vs Frequency
18, 19
Closed loop response
20, 21
SUPPLY RIPPLE REJECTION RATIO
vs
FREQUENCY
SUPPLY RIPPLE REJECTION RATIO
vs
FREQUENCY
0
0
RL = 8 Ω
CB = 1 µF
Mode = Mono
–20
RL = 32 Ω
CB = 1 µF
Mode = Stereo
–10
Supply Ripple Rejection Ratio – dB
Supply Ripple Rejection Ratio – dB
–10
–30
–40
–50
–60
–70
–80
–20
–30
–40
–50
–60
–70
–80
–90
–90
–100
–100
20
100
1k
10 k 20 k
20
100
1k
10 k 20 k
f – Frequency – Hz
f – Frequency – Hz
Figure 1
Figure 2
POST OFFICE BOX 655303
• DALLAS, TEXAS 75265
5
TPA0223
2-W MONO AUDIO POWER AMPLIFIER
WITH HEADPHONE DRIVE
SLOS277C – JANUARY 2000 – REVISED NOVEMBER 2002
TYPICAL CHARACTERISTICS
OUTPUT POWER
vs
SUPPLY VOLTAGE
SUPPLY CURRENT
vs
SUPPLY VOLTAGE
3
18
VDD From Low to High
Mode = Stereo
RL = Open
THD+N = 1%
f = 1 kHz
Mode = Mono
AV = 8 dB
2.5
14
PO – Output Power – W
I DD – Supply Current – mA
16
TA = 25 °C
12
10
8
6
RL = 4 Ω
2
RL = 8 Ω
1.5
1
4
0.5
2
0
0
0
0.5
1
1.5 2 2.5 3 3.5 4
VDD – Supply Voltage – V
4.5
5
5.5
3
3.5
4
4.5
5
VDD – Supply Voltage – V
Figure 3
Figure 4
OUTPUT POWER
vs
LOAD RESISTANCE
OUTPUT POWER
vs
SUPPLY VOLTAGE
2.5
500
THD+N = 1%
f = 1 kHz
Mode = Stereo
AV = 2 dB
THD+N = 1%
f = 1 kHz
Mode = Mono
AV = 8 dB
2
PO – Output Power – W
400
PO – Output Power – mW
5.5
RL = 8 Ω
300
200
1.5
VDD = 5 V
1
RL = 32 Ω
100
0.5
0
0
VDD = 3 V
3
3.5
4
4.5
5
VDD – Supply Voltage – V
5.5
0
20
30
Figure 6
POST OFFICE BOX 655303
40
50
RL – Load Resistance – Ω
Figure 5
6
10
• DALLAS, TEXAS 75265
60
TPA0223
2-W MONO AUDIO POWER AMPLIFIER
WITH HEADPHONE DRIVE
SLOS277C – JANUARY 2000 – REVISED NOVEMBER 2002
TYPICAL CHARACTERISTICS
OUTPUT POWER
vs
LOAD RESISTANCE
TOTAL HARMONIC DISTORTION PLUS NOISE
vs
FREQUENCY
THD+N = 1%
f = 1 kHz
Mode = Stereo
AV = 2 dB
600
PO – Output Power – mW
THD+N – Total Harmonic Distortion Plus Noise – %
700
500
400
300
VDD = 5 V
200
100
VDD = 3 V
0
0
10
20
30
40
50
RL – Load Resistance – Ω
60
1
VDD = 3 V
PO = 250 mW
RL = 8 Ω
Mode = Mono
0.1
AV = 20 dB
AV = 8 dB
0.01
0.001
20
100
1k
f – Frequency – Hz
Figure 7
Figure 8
1
VDD = 5 V
PO = 1 W
RL = 8 Ω
Mode = Mono
0.1
AV = 20 dB
AV = 8 dB
0.01
0.001
100
1k
f – Frequency – Hz
TOTAL HARMONIC DISTORTION PLUS NOISE
vs
FREQUENCY
THD+N – Total Harmonic Distortion Plus Noise – %
THD+N – Total Harmonic Distortion Plus Noise – %
TOTAL HARMONIC DISTORTION PLUS NOISE
vs
FREQUENCY
20
10 k 20 k
10 k 20 k
1
VDD = 3 V
PO = 25 mW
RL = 32 Ω
Mode = Stereo
0.1
AV = 14 dB
0.01
AV = 2 dB
0.001
20
100
1k
10 k 20 k
f – Frequency – Hz
Figure 9
Figure 10
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7
TPA0223
2-W MONO AUDIO POWER AMPLIFIER
WITH HEADPHONE DRIVE
SLOS277C – JANUARY 2000 – REVISED NOVEMBER 2002
TYPICAL CHARACTERISTICS
1
VDD = 5 V
PO = 75 mW
RL = 32 Ω
Mode = Stereo
0.1
AV = 14 dB
0.01
AV = 2 dB
0.001
20
100
TOTAL HARMONIC DISTORTION PLUS NOISE
vs
OUTPUT POWER
THD+N – Total Harmonic Distortion Plus Noise – %
THD+N – Total Harmonic Distortion Plus Noise – %
TOTAL HARMONIC DISTORTION PLUS NOISE
vs
FREQUENCY
1k
f – Frequency – Hz
10 k 20 k
10
20 kHz
1
15 kHz
0.1
1 kHz
20 Hz
0.01
VDD = 3 V
RL = 4 Ω
Mode = Mono
AV = 8 dB
0.001
10 m
Figure 11
VDD = 3 V
RL = 8 Ω
Mode = Mono
AV = 8 dB
20 kHz
15 kHz
0.1
1 kHz
20 Hz
0.01
100 m
PO – Output Power – W
1
2
10
VDD = 3 V
RL = 32 Ω
Mode = Stereo
AV = 2 dB
1
0.1
20 kHz
15 kHz
0.01
20 Hz
0.001
10 m
Figure 13
8
2
TOTAL HARMONIC DISTORTION PLUS NOISE
vs
OUTPUT POWER
THD+N – Total Harmonic Distortion Plus Noise – %
THD+N – Total Harmonic Distortion Plus Noise – %
10
0.001
10 m
1
Figure 12
TOTAL HARMONIC DISTORTION PLUS NOISE
vs
OUTPUT POWER
1
100 m
PO – Output Power – W
1 kHz
100 m
PO – Output Power – mW
Figure 14
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• DALLAS, TEXAS 75265
1
TPA0223
2-W MONO AUDIO POWER AMPLIFIER
WITH HEADPHONE DRIVE
SLOS277C – JANUARY 2000 – REVISED NOVEMBER 2002
TYPICAL CHARACTERISTICS
TOTAL HARMONIC DISTORTION PLUS NOISE
vs
OUTPUT POWER
10
THD+N – Total Harmonic Distortion Plus Noise – %
THD+N – Total Harmonic Distortion Plus Noise – %
TOTAL HARMONIC DISTORTION PLUS NOISE
vs
OUTPUT POWER
VDD = 5 V
RL = 4 Ω
Mode = Mono
AV = 8 dB
1
20 kHz
15 kHz
0.1
1 kHz
20 Hz
0.01
0.001
10 m
100 m
1
PO – Output Power – W
10
10
VDD = 5 V
RL = 8 Ω
Mode = Mono
AV = 8 dB
1
20 KHz
15 kHz
0.1
20 Hz
0.01
0.001
10 m
100 m
PO – Output Power – W
Figure 15
Vn – Output Noise Voltage – µV RMS
THD+N – Total Harmonic Distortion Plus Noise – %
1M
VDD = 5 V
RL = 32 Ω
Mode = Stereo
AV = 2 dB
15 kHz
20 kHz
0.01
20 Hz
1 kHz
0.001
10 m
2
OUTPUT NOISE VOLTAGE
vs
FREQUENCY
10
0.1
1
Figure 16
TOTAL HARMONIC DISTORTION PLUS NOISE
vs
OUTPUT POWER
1
1 kHz
100 m
PO – Output Power – W
1
VDD = 5 V
RL = 8 Ω
Mode = Mono
AV = 8 dB
100
10
1
20
100
Figure 17
1k
f – Frequency – Hz
10 k 20 k
Figure 18
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TPA0223
2-W MONO AUDIO POWER AMPLIFIER
WITH HEADPHONE DRIVE
SLOS277C – JANUARY 2000 – REVISED NOVEMBER 2002
TYPICAL CHARACTERISTICS
OUTPUT NOISE VOLTAGE
vs
FREQUENCY
CLOSED LOOP RESPONSE
180°
30
VDD = 5 V
RL = 32 Ω
Mode = Stereo
AV = 2 dB
20
10
VDD = 5 V
RL = 4 Ω
Mode = Mono
AV = 8 dB
135°
Gain
90°
100
0
45°
Phase
–10
0°
–20
–45°
–30
–90°
–40
–135°
10
–50
10
1
20
100
1k
f – Frequency – Hz
10 k 20 k
100
1k
10k
f – Frequency – Hz
Figure 19
Figure 20
CLOSED LOOP RESPONSE
30
Gain – dB
10
135°
Gain
90°
0
45°
Phase
–10
0°
–20
–45°
–30
–90°
–40
–135°
–50
10
100
1k
10k
100k
f – Frequency – Hz
Figure 21
10
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–180°
1M
Phase
20
180°
VDD = 5 V
RL = 32 Ω
Mode = Stereo
AV = 2 dB
Phase
Gain – dB
Vn – Output Noise Voltage – µV RMS
1M
100k
–180°
1M
TPA0223
2-W MONO AUDIO POWER AMPLIFIER
WITH HEADPHONE DRIVE
SLOS277C – JANUARY 2000 – REVISED NOVEMBER 2002
APPLICATION INFORMATION
gain setting via input resistance
The gain of the input stage is set by the user-selected input resistor and a 50-kΩ internal feedback resistor.
However, the power stage is internally configured with a gain of –1.25 V/V in SE mode, and –2.5 V/V in BTL
mode. Thus, the feedback resistor (RF) is effectively 62.5 kΩ in SE mode and 125 kΩ in BTL mode. Therefore,
the overall gain can be calculated using equations (1) and (2).
A + –125 kW
V
R
I
(BTL)
A + –62.5 kW
V
R
I
(SE)
(1)
(2)
The –3 dB frequency can be calculated using equation 3:
ƒ –3 dB +
1
2p R C
I i
(3)
If the filter must be more accurate, the value of the capacitor should be increased while the value of the resistor
to ground should be decreased. In addition, the order of the filter could be increased.
input capacitor, Ci
In the typical application an input capacitor, Ci, is required to allow the amplifier to bias the input signal to the
proper dc level for optimum operation. In this case, Ci and the input resistance of the amplifier, RI, form a
high-pass filter with the corner frequency determined in equation 4.
–3 dB
f c(highpass) +
(4)
1
2 p RI Ci
fc
The value of Ci is important to consider as it directly affects the bass (low frequency) performance of the circuit.
Consider the example where RI is 710 kΩ and the specification calls for a flat bass response down to 40 Hz.
Equation 2 is reconfigured as equation 5.
1
C +
i
2p R f c
I
(5)
In this example, CI is 5.6 nF so one would likely choose a value in the range of 5.6 nF to 1 µF. A further
consideration for this capacitor is the leakage path from the input source through the input network (Ci) and the
feedback network to the load. This leakage current creates a dc offset voltage at the input to the amplifier that
reduces useful headroom, especially in high gain applications. For this reason a low-leakage tantalum or
ceramic capacitor is the best choice. When polarized capacitors are used, the positive side of the capacitor
should face the amplifier input in most applications as the dc level there is held at VDD/2, which is likely higher
than the source dc level. Note that it is important to confirm the capacitor polarity in the application.
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TPA0223
2-W MONO AUDIO POWER AMPLIFIER
WITH HEADPHONE DRIVE
SLOS277C – JANUARY 2000 – REVISED NOVEMBER 2002
APPLICATION INFORMATION
input capacitor, Ci (continued)
power supply decoupling, C(S)
The TPA0223 is a high-performance CMOS audio amplifier that requires adequate power supply decoupling
to ensure the output total harmonic distortion (THD) is as low as possible. Power supply decoupling also
prevents oscillations for long lead lengths between the amplifier and the speaker. The optimum decoupling is
achieved by using two capacitors of different types that target different types of noise on the power supply leads.
For higher frequency transients, spikes, or digital hash on the line, a good low equivalent-series-resistance
(ESR) ceramic capacitor, typically 0.1 µF placed as close as possible to the device VDD lead, works best. For
filtering lower-frequency noise signals, a larger aluminum electrolytic capacitor of 10 µF or greater placed near
the audio power amplifier is recommended.
midrail bypass capacitor, C(BYP)
The midrail bypass capacitor, C(BYP), is the most critical capacitor and serves several important functions.
During start-up or recovery from shutdown mode, C(BYP) determines the rate at which the amplifier starts up.
The second function is to reduce noise produced by the power supply caused by coupling into the output drive
signal. This noise is from the midrail generation circuit internal to the amplifier, which appears as degraded
PSRR and THD+N.
Bypass capacitor, C(BYP), values of 0.47 µF to 1 µF ceramic or tantalum low-ESR capacitors are recommended
for the best THD and noise performance.
output-coupling capacitor, C(C)
In the typical single-supply SE configuration, an output-coupling capacitor (C(C)) is required to block the dc bias
at the output of the amplifier, thus preventing dc currents in the load. As with the input-coupling capacitor, the
output-coupling capacitor and impedance of the load form a high-pass filter governed by equation 6.
–3 dB
f c(high) +
1
2 p R L C (C)
(6)
fc
The main disadvantage, from a performance standpoint, is that the load impedances are typically small, which
drives the low-frequency corner higher, degrading the bass response. Large values of C(C) are required to pass
low frequencies into the load. Consider the example where a C(C) of 330 µF is chosen and loads vary from
3 Ω, 4 Ω, 8 Ω, 32 Ω, 10 kΩ, to 47 kΩ. Table 1 summarizes the frequency response characteristics of each
configuration.
12
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TPA0223
2-W MONO AUDIO POWER AMPLIFIER
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SLOS277C – JANUARY 2000 – REVISED NOVEMBER 2002
APPLICATION INFORMATION
Table 1. Common Load Impedances vs Low Frequency Output Characteristics in SE Mode
RL
C(C)
330 µF
Lowest Frequency
3Ω
4Ω
330 µF
120 Hz
161 Hz
8Ω
330 µF
60 Hz
32 Ω
330 µF
Ą15 Hz
10,000 Ω
330 µF
0.05 Hz
47,000 Ω
330 µF
0.01 Hz
As Table 1 indicates, most of the bass response is attenuated into a 4-Ω load, an 8-Ω load is adequate,
headphone response is good, and drive into line level inputs (a home stereo for example) is exceptional.
Furthermore, the total amount of ripple current that must flow through the capacitor must be considered when
choosing the component. As shown in the application circuit, one coupling capacitor must be in series with the
mono loudspeaker for proper operation of the stereo-mono switching circuit. For a 4-Ω load, this capacitor must
be able to handle about 700 mA of ripple current for a continuous output power of 2 W.
using low-ESR capacitors
Low-ESR capacitors are recommended throughout this applications section. A real (as opposed to ideal)
capacitor can be modeled simply as a resistor in series with an ideal capacitor. The voltage drop across this
resistor minimizes the beneficial effects of the capacitor in the circuit. The lower the equivalent value of this
resistance the more the real capacitor behaves like an ideal capacitor.
bridged-tied load versus single-ended mode
Figure 22 shows a Class-AB audio power amplifier (APA) in a BTL configuration. The TPA0223 BTL amplifier
consists of two Class-AB amplifiers driving both ends of the load. There are several potential benefits to this
differential drive configuration, but initially consider power to the load. The differential drive to the speaker
means that as one side is slewing up, the other side is slewing down, and vice versa. This, in effect, doubles
the voltage swing on the load as compared to a ground referenced load. Plugging 2 × VO(PP) into the power
equation, where voltage is squared, yields 4× the output power from the same supply rail and load impedance.
See equation 7.
V
V
(RMS)
+
V
Power +
O(PP)
2 Ǹ2
(7)
2
(RMS)
R
L
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TPA0223
2-W MONO AUDIO POWER AMPLIFIER
WITH HEADPHONE DRIVE
SLOS277C – JANUARY 2000 – REVISED NOVEMBER 2002
APPLICATION INFORMATION
bridged-tied load versus single-ended mode (continued)
VDD
VO(PP)
2x VO(PP)
RL
VDD
–VO(PP)
Figure 22. Bridge-Tied Load Configuration
In a typical computer sound channel operating at 5 V, bridging raises the power into an 8-Ω speaker from a
singled-ended (SE, ground reference) limit of 250 mW to 1 W. In sound power, that is a 6-dB improvement—
which is loudness that can be heard. In addition to increased power, there are frequency response concerns.
Consider the single-supply SE configuration shown in Figure 23. A coupling capacitor is required to block the
dc offset voltage from reaching the load. These capacitors can be quite large (approximately 33 µF to 1000 µF)
so they tend to be expensive, heavy, occupy valuable PCB area, and have the additional drawback of limiting
low-frequency performance of the system. This frequency-limiting effect is due to the high pass filter network
created with the speaker impedance and the coupling capacitance and is calculated with equation 8.
fc +
1
2p R C
L (C)
(8)
For example, a 68-µF capacitor with an 8-Ω speaker would attenuate low frequencies below 293 Hz. The BTL
configuration cancels the dc offsets, which eliminates the need for the blocking capacitors. Low-frequency
performance is then limited only by the input network and speaker response. Cost and PCB space are also
minimized by eliminating the bulky coupling capacitor.
VDD
–3 dB
VO(PP)
C(C)
RL
VO(PP)
fc
Figure 23. Single-Ended Configuration and Frequency Response
14
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TPA0223
2-W MONO AUDIO POWER AMPLIFIER
WITH HEADPHONE DRIVE
SLOS277C – JANUARY 2000 – REVISED NOVEMBER 2002
APPLICATION INFORMATION
bridged-tied load versus single-ended mode (continued)
Increasing power to the load does carry a penalty of increased internal power dissipation. The increased
dissipation is understandable considering that the BTL configuration produces 4× the output power of the SE
configuration. Internal dissipation versus output power is discussed further in the crest factor and thermal
considerations section.
single-ended operation
In SE mode (see Figure 22 and Figure 23), the load is driven from the primary amplifier output for each channel
(LO and RO, terminals 6 and 10)
The amplifier switches to single-ended operation when the ST/MN terminal is held high.
input MUX operation
The input MUX allows two separate inputs to be applied to the amplifier. When the ST/MN terminal is held high,
the headphone inputs (LIN and RIN) are active. When the ST/MN terminal is held low, the line BTL input
(MONO-IN) is active.
BTL amplifier efficiency
Class-AB amplifiers are inefficient. The primary cause of inefficiencies is the voltage drop across the output
stage transistors. There are two components of the internal voltage drop. One is the headroom or dc voltage
drop that varies inversely to output power. The second component is due to the sinewave nature of the output.
The total voltage drop can be calculated by subtracting the RMS value of the output voltage from VDD. The
internal voltage drop multiplied by the RMS value of the supply current, IDDrms, determines the internal power
dissipation of the amplifier.
An easy-to-use equation to calculate efficiency starts out as being equal to the ratio of power from the power
supply to the power delivered to the load. To accurately calculate the RMS and average values of power in the
load and in the amplifier, the current and voltage waveform shapes must first be understood. See Figure 24.
IDD
VO
IDD(avg)
V(LRMS)
Figure 24. Voltage and Current Waveforms for BTL Amplifiers
Although the voltages and currents for SE and BTL are sinusoidal in the load, currents from the supply are very
different between SE and BTL configurations. In an SE application the current waveform is a half-wave rectified
shape, whereas in BTL it is a full-wave rectified waveform. This means RMS conversion factors are different.
Keep in mind that for most of the waveform both the push and pull transistors are not on at the same time, which
supports the fact that each amplifier in the BTL device only draws current from the supply for half the waveform.
The following equations are the basis for calculating amplifier efficiency.
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TPA0223
2-W MONO AUDIO POWER AMPLIFIER
WITH HEADPHONE DRIVE
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APPLICATION INFORMATION
BTL amplifier efficiency (continued)
Efficiency of a BTL amplifier +
where
PL +
V LRMS
RL
2
PL
(9)
P SUP
2
V
V
, and V LRMS + P , therefore, P L + P
Ǹ2
2 RL
and P SUP + V DD I DDavg
1
I DDavg + p
and
ŕ
p
0
VP
1
sin(t) dt + p
RL
VP
RL
[cos(t)]
p
2V P
+
0
p RL
therefore,
P SUP +
2 V DD V P
p RL
substituting PL and PSUP into equation 9,
2
Efficiency of a BTL amplifier +
where
VP +
VP
2 RL
2 V DD V P
p RL
+
p VP
4 V DD
Ǹ2 P L RL
therefore,
h BTL +
p
Ǹ2 PL R L
(10)
4 V DD
PL = Power devilered to load
PSUP = Power drawn from power supply
VLRMS = RMS voltage on BTL load
RL = Load resistance
VP = Peak voltage on BTL load
IDDavg = Average current drawn from the power supply
VDD = Power supply voltage
ηBTL = Efficiency of a BTL amplifier
Table 2 employs equation 10 to calculate efficiencies for four different output power levels. Note that the
efficiency of the amplifier is quite low for lower power levels and rises sharply as power to the load is increased
resulting in a nearly flat internal power dissipation over the normal operating range. Note that the internal
dissipation at full output power is less than in the half power range. Calculating the efficiency for a specific
system is the key to proper power supply design. For a stereo 1-W audio system with 8-Ω loads and a 5-V supply,
the maximum draw on the power supply is almost 3.25 W.
Table 2. Efficiency Vs Output Power in 5-V 8-Ω BTL Systems
Output Power
(W)
Efficiency
(%)
Peak Voltage
(V)
Internal Dissipation
(W)
0.25
31.4
2.00
0.55
0.50
44.4
2.83
0.62
1.00
62.8
70.2
4.00
4.47†
0.59
1.25
† High peak voltages cause the THD to increase.
16
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0.53
TPA0223
2-W MONO AUDIO POWER AMPLIFIER
WITH HEADPHONE DRIVE
SLOS277C – JANUARY 2000 – REVISED NOVEMBER 2002
APPLICATION INFORMATION
BTL amplifier efficiency (continued)
A final point to remember about Class-AB amplifiers (either SE or BTL) is how to manipulate the terms in the
efficiency equation to utmost advantage when possible. Note that in equation 10, VDD is in the denominator.
This indicates that as VDD goes down, efficiency goes up.
crest factor and thermal considerations
Class-AB power amplifiers dissipate a significant amount of heat in the package under normal operating
conditions. A typical music CD requires 12 dB to 15 dB of dynamic range, or headroom above the average power
output, to pass the loudest portions of the signal without distortion. In other words, music typically has a crest
factor between 12 dB and 15 dB. When determining the optimal ambient operating temperature, the internal
dissipated power at the average output power level must be used. The TPA0223 data sheet shows that when
the TPA0223 is operating from a 5-V supply into a 4-Ω speaker 4-W peaks are available. Converting watts to
dB:
P dB + 10Log
PW
P ref
+ 10 Log 4 W + 6 dB
1W
(11)
Subtracting the headroom restriction to obtain the average listening level without distortion yields:
6 dB – 15 dB = –9 dB (15-dB crest factor)
6 dB – 12 dB = –6 dB (12-dB crest factor)
6 dB – 9 dB = –3 dB (9-dB crest factor)
6 dB – 6 dB = 0 dB (6-dB crest factor)
6 dB – 3 dB = 3 dB (3-dB crest factor)
Converting dB back into watts:
P W + 10 PdBń10
+
+
+
+
+
+
P ref
(12)
63 mW (18-dB crest factor)
125 mW (15-dB crest factor)
250 mW (12-dB crest factor)
500 mW (9-dB crest factor)
1000 mW (6-dB crest factor)
2000 mW (3-dB crest factor)
This is valuable information to consider when attempting to estimate the heat dissipation requirements for the
amplifier system. Comparing the absolute worst case, which is 2 W of continuous power output with a 3 dB crest
factor, against 12 dB and 15 dB applications drastically affects maximum ambient temperature ratings for the
system. Table 3 shows maximum ambient temperatures and TPA223 internal power dissipation for various
output-power levels.
Table 3. TPA0223 Power Rating, 5-V, 3-Ω, Mono
PEAK OUTPUT POWER
(W)
AVERAGE OUTPUT POWER
POWER DISSIPATION
(W)
4
2 W (3-dB crest factor)
1.7
4
1000 mW (6-dB crest factor)
1.6
6°C
4
500 mW (9-dB crest factor)
1.4
24°C
4
250 mW (12-dB crest factor)
1.1
51°C
4
125 mW (15-dB crest factor)
0.8
78°C
4
63 mW (18-dB crest factor)
0.6
96°C
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MAXIMUM AMBIENT
TEMPERATURE
– 3°C
17
TPA0223
2-W MONO AUDIO POWER AMPLIFIER
WITH HEADPHONE DRIVE
SLOS277C – JANUARY 2000 – REVISED NOVEMBER 2002
APPLICATION INFORMATION
crest factor and thermal considerations (continued)
Table 4. TPA0223 Power Rating, 5-V, 8-Ω, Stereo
PEAK OUTPUT POWER
(W)
AVERAGE OUTPUT POWER
POWER DISSIPATION
(W)
MAXIMUM AMBIENT
TEMPERATURE
2.5
1250 mW (3-dB crest factor)
0.55
100°C
2.5
1000 mW (4-dB crest factor)
0.62
94°C
2.5
500 mW (7-dB crest factor)
0.59
97°C
2.5
250 mW (10-dB crest factor)
0.53
102°C
The maximum dissipated power, PDmax, is reached at a much lower output power level for an 4-Ω load than for
an 8-Ω load. As a result, this simple formula for calculating PDmax may be used for a 4-Ω application:
P Dmax +
2V 2
DD
(13)
p 2R L
However, in the case of a 8-Ω load, the PDmax occurs at a point well above the normal operating power level.
The amplifier may therefore be operated at a higher ambient temperature than required by the PDmax formula
for an 8-Ω load.
The maximum ambient temperature depends on the heat sinking ability of the PCB system. The derating factor
for the DGQ package is shown in the dissipation rating table (see page 4). Converting this to ΘJA:
Θ JA +
1
1
+
+ 58.48°CńW
0.0171
Derating Factor
(14)
To calculate maximum ambient temperatures, first consider that the numbers from the dissipation graphs are
per channel so the dissipated power needs to be doubled for two channel operation. Given ΘJA, the maximum
allowable junction temperature, and the total internal dissipation, the maximum ambient temperature can be
calculated with the following equation. The maximum recommended junction temperature for the TPA0223 is
150°C. The internal dissipation figures are taken from the Power Dissipation vs Output Power graphs.
T A Max + T J Max * Θ JA P D + 150 * 58.48 (0.8
2) + 56°C (15-dB crest factor)
(15)
NOTE:
Internal dissipation of 0.8 W is estimated for a 2-W system with 15-dB crest factor per channel.
Tables 3 and 4 show that for some applications no airflow is required to keep junction temperatures in the
specified range. The TPA0223 is designed with thermal protection that turns the device off when the junction
temperature surpasses 150°C to prevent damage to the IC. Tables 3 and 4 were calculated for maximum
listening volume without distortion. When the output level is reduced the numbers in the table change
significantly. Also, using 8-Ω speakers dramatically increases the thermal performance by increasing amplifier
efficiency.
ST/MN (stereo/mono) operation
The ability of the TPA0223 to easily switch between mono BTL and stereo SE modes is one of its most important
cost saving features. This feature eliminates the requirement for an additional headphone amplifier in
applications where an internal speaker is driven in BTL mode but external stereo headphone or speakers must
be accommodated. When ST/MN is held high, the input mux selects the RIN and LIN inputs and the output is
in stereo SE mode. When ST/MN is held low, the input mux selects the mono-in input and the output is in mono
BTL mode. Control of the ST/MN input can be from a logic-level CMOS source or, more typically, from a
switch-controlled resistor divider network as shown in Figure 25.
18
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TPA0223
2-W MONO AUDIO POWER AMPLIFIER
WITH HEADPHONE DRIVE
SLOS277C – JANUARY 2000 – REVISED NOVEMBER 2002
APPLICATION INFORMATION
ST/MN (stereo/mono) operation (continued)
CB
4
VDD
3
BYPASS
VDD
GND
Ci
50 kΩ
RI
1.25*R
100 kΩ
1
Right
Audio
Input
5
Ci
VDD
BYPASS
50 kΩ
Mono
Audio
Input
1 kΩ
8
MONO-IN
RIN
RI
M
U
X
–
R
–
+
CC
RO/MO+
6
+
BYPASS
BYPASS
100 kΩ
50 kΩ
Stereo/Mono
Control
50 kΩ
ST/MN
7
LO/MO–
10
50 kΩ
1.25*R
Left
Audio
Input
Ci
RI
9
M
U
X
LIN
–
R
–
+
CC
+
1 kΩ
BYPASS
From
System Control
BYPASS
2
SHUTDOWN
Shutdown
and Depop
Circuitry
Figure 25. TPA0223 Resistor Divider Network Circuit
Using a readily available 1/8-in. (3,5 mm) stereo headphone jack, the control switch is closed when no plug is
inserted. When closed, the 100-kΩ/1-kΩ divider pulls the ST/MN input low. When a plug is inserted, the 1-kΩ
resistor is disconnected and the ST/MN input is pulled high. The mono speaker is also physically disconnected
from the RO/MO+ output so that no sound is heard from the speaker while the headphones are inserted.
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PACKAGE OPTION ADDENDUM
www.ti.com
10-Dec-2020
PACKAGING INFORMATION
Orderable Device
Status
(1)
Package Type Package Pins Package
Drawing
Qty
Eco Plan
(2)
Lead finish/
Ball material
MSL Peak Temp
Op Temp (°C)
Device Marking
(3)
(4/5)
(6)
TPA0223DGQR
ACTIVE
HVSSOP
DGQ
10
2500
RoHS & Green
NIPDAU
Level-1-260C-UNLIM
-40 to 125
AEI
(1)
The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2)
RoHS: TI defines "RoHS" to mean semiconductor products that are compliant with the current EU RoHS requirements for all 10 RoHS substances, including the requirement that RoHS substance
do not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, "RoHS" products are suitable for use in specified lead-free processes. TI may
reference these types of products as "Pb-Free".
RoHS Exempt: TI defines "RoHS Exempt" to mean products that contain lead but are compliant with EU RoHS pursuant to a specific EU RoHS exemption.
Green: TI defines "Green" to mean the content of Chlorine (Cl) and Bromine (Br) based flame retardants meet JS709B low halogen requirements of
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