TPA2001D2PWP

TPA2001D2 1-W FILTERLESS STEREO CLASS-D AUDIO POWER AMPLIFIER SLOS292A – MARCH 2000 – REVISED APRIL 2000
Modulation Scheme Optimized to Operate PWP PACKAGE (TOP VIEW) Without a Filter
1 W Into 8-Ω Speakers (THD+N< 0.4%)
< 0.08% THD+N at 0.5 W, 1 kHz, Into 8-Ω



PGND LOUTN GAIN0 PVDD LINN AGND COSC RINN PVDD SHUTDOWN ROUTN PGND Load Extremely Efficient 3rd Generation 5-V Class-D Technology: – Low Supply Current (No Filter) . . . 8 mA – Low Supply Current (Filter) . . . 15 mA – Low Shutdown Current . . . 1 µA – Low Noise Floor . . . 56 µVRMS – Maximum Efficiency Into 8 Ω, 75 – 85% – 4 Internal Gain Settings . . . 8 – 23.5 dB – PSRR . . . –77 dB Integrated Depop Circuitry Short-Circuit Protection (Short to Battery, Ground, and Load) –40°C to 85°C Operating Temperature Range 1 2 3 4 5 6 7 8 9 10 11 12 24 23 22 21 20 19 18 17 16 15 14 13 PGND LOUTP BYPASS PVDD LINP VDD ROSC RINP PVDD GAIN1 ROUTP PGND description The TPA2001D2 is the third generation 5-V class-D amplifier from Texas Instruments. Improvements to previous generation devices include: lower supply current, lower noise floor, better efficiency, four different gain settings, smaller packaging, and fewer external components. The most significant advancement with this device is its modulation scheme that allows the amplifier to operate without the output filter. Eliminating the output filter saves the user approximately 30% in system cost and 75% in PCB area. The TPA2001D2 is a monolithic class-D power IC stereo audio amplifier, using the high switching speed of power MOSFET transistors. These transistors reproduce the analog signal through high-frequency switching of the output stage. The TPA2001D2 is configured as a bridge-tied load (BTL) amplifier capable of delivering greater than 1 W of continuous average power into an 8-Ω load at less than 0.6% THD+N from a 5-V power supply in the high fidelity range (20 Hz to 20 kHz). With 1 W being delivered to an 8-Ω load at 1 kHz, the typical THD+N is less than 0.08%. A BTL configuration eliminates the need for external coupling capacitors on the output. Low supply current of 8 mA makes the device ideal for battery-powered applications. Protection circuitry increases device reliability: thermal, over-current, and under-voltage shutdown. Efficient class-D modulation enables the TPA2001D2 to operate at full power into 8-Ω loads at an ambient temperature of 85°C. AVAILABLE OPTIONS PACKAGED DEVICE TA TSSOP (PWP) – 40°C to 85°C TPA2001D2PWP NOTE: The PWP package is available taped and reeled. To order a taped and reeled part, add the suffix R to the part number (e.g., TPA2001D2PWPR). Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet. PowerPAD is a trademark of Texas Instruments. Copyright  2000, Texas Instruments Incorporated PRODUCTION DATA information is current as of publication date. Products conform to specifications per the terms of Texas Instruments standard warranty. Production processing does not necessarily include testing of all parameters. POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 1 TPA2001D2 1-W FILTERLESS STEREO CLASS-D AUDIO POWER AMPLIFIER SLOS292A – MARCH 2000 – REVISED APRIL 2000 functional block diagram VDD AGND PVDD VDD Gain Adjust RINN + _ Gate Drive ROUTN _ + PGND + _ PVDD _ Gain Adjust RINP Gate Drive + ROUTP PGND SHUTDOWN 2 GAIN1 GAIN0 Gain Biases and References Start-up Protection Logic Ramp Generator COSC ROSC BYPASS Thermal OC Detect OC Detect VDD ok PVDD LINP Gain Adjust + _ Gate Drive _ + PGND + _ PVDD _ LINN LOUTP Gain Adjust + Gate Drive LOUTN PGND 2 POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 TPA2001D2 1-W FILTERLESS STEREO CLASS-D AUDIO POWER AMPLIFIER SLOS292A – MARCH 2000 – REVISED APRIL 2000 Terminal Function TERMINAL NAME NO. I/O DESCRIPTION AGND 6 – Analog ground BYPASS 22 I Tap to voltage divider for internal midsupply bias generator used for analog reference. COSC 7 I A capacitor connected to this terminal sets the oscillation frequency in conjunction with ROSC. For proper operation, connect a 220 pF capacitor from COSC to ground. GAIN0 3 I Bit 0 of gain control (TTL logic level) GAIN1 15 I Bit 1 of gain control (TTL logic level) LINN 5 I Left channel negative differential audio input LINP 20 I Left channel positive differential audio input LOUTN 2 O Left channel negative audio output LOUTP 23 O Left channel positive audio output 1, 24 – Power ground for left channel H-bridge 12, 13 – Power ground for right channel H-bridge 4, 21 – Power supply for left channel H-bridge 9, 16 – Power supply for right channel H-bridge RINN 8 I Right channel negative differential audio input RINP 17 I Right channel positive differential audio input ROSC 18 I A resistor connected to this terminal sets the oscillation frequency in conjunction with COSC. For proper operation, connect a 120 kΩ resistor from ROSC to ground. ROUTN 11 O Right channel negative audio output ROUTP 14 O Right channel positive output SHUTDOWN 10 I Places the amplifier in shutdown mode if a TTL logic low is placed on this terminal; normal operation if a TTL logic high is placed on this terminal. VDD 19 – Analog power supply PGND PVDD absolute maximum ratings over operating free-air temperature (unless otherwise noted)† Supply voltage, VDD, PVDD . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . –0.3 V to 6 V Input voltage, VI . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . –0.3 V to VDD+0.3 V Continuous total power dissipation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . See Dissipation Rating Table Operating free-air temperature range, TA . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . –40°C to 85°C Operating junction temperature range, TJ . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . –40°C to 150°C Storage temperature range, Tstg . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . –65°C to 150°C Lead temperature 1,6 mm (1/16 inch) from case for 10 seconds . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 260°C † Stresses beyond those listed under “absolute maximum ratings” may cause permanent damage to the device. These are stress ratings only, and functional operation of the device at these or any other conditions beyond those indicated under “recommended operating conditions” is not implied. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability. DISSIPATION RATING TABLE PACKAGE TA ≤ 25°C POWER RATING DERATING FACTOR ABOVE TA = 25°C TA = 70°C POWER RATING TA = 125°C POWER RATING PWP 2.7 W 21.8 mW/°C 1.7 W 1.4 W POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 3 TPA2001D2 1-W FILTERLESS STEREO CLASS-D AUDIO POWER AMPLIFIER SLOS292A – MARCH 2000 – REVISED APRIL 2000 recommended operating conditions MIN Supply voltage, VDD, PVDD 4.5 High-level input voltage, VIH GAIN0, GAIN1, SHUTDOWN Low-level input voltage, VIL GAIN0, GAIN1, SHUTDOWN MAX 5.5 2 UNIT V V 0.8 V Operating free-air temperature, TA –40 85 °C PWM Frequency 200 300 kHz TYP MAX UNIT electrical characteristics, TA = 25°C, VDD = PVDD = 5 V (unless otherwise noted) PARAMETER TEST CONDITIONS | VOO | Output offset voltage (measured differentially) PSRR Power supply rejection ratio IIH IIL High-level input current IDD IDD Supply current VDD=PVDD = 5.5 V, VI = VDD = PVDD VDD=PVDD = 5.5 V, VI = 0 V No filter (with or without speaker load) Supply current With filter, L = 22 µH, IDD(SD) Supply current, shutdown mode Low-level input current MIN VI = 0 V VDD=PVDD = 4.5 V to 5.5 V 10 mV 1 µA 10 mA –77 dB µA –1 8 C = 1 µF 15 1 mA 10 µA operating characteristics, TA = 25°C, VDD = PVDD = 5 V, RL = 8 Ω, Gain = 8 dB (unless otherwise noted) PARAMETER TEST CONDITIONS f = 1 kHz, RL = 8 Ω f = 20 Hz to 20 kHz PO THD+N Output power THD = 0.4%, Total harmonic distortion plus noise BOM kSVR Maximum output power bandwidth PO = 0.5 W, THD = 5% Supply ripple rejection ratio f = 1 kHz, SNR Signal-to-noise ratio 20 Hz to 20 kHz Integrated noise floor 20 Hz to 20 kHz, No input ZI MIN C(BYPASS) = 0.4 µF 4 AMPLIFIER GAIN (dB) INPUT IMPEDANCE (kΩ) TYP TYP 0 0 8 104 0 1 12 74 1 0 17.5 44 1 1 23.5 24 POST OFFICE BOX 655303 –60 87 Table 1. Gain Settings GAIN1 1 • DALLAS, TEXAS 75265 MAX UNIT W 20 kΩ TPA2001D2 1-W FILTERLESS STEREO CLASS-D AUDIO POWER AMPLIFIER SLOS292A – MARCH 2000 – REVISED APRIL 2000 APPLICATION INFORMATION eliminating the output filter with the TPA2001D2 This section will focus on why the user can eliminate the output filter with the TPA2001D2. effect on audio The class-D amplifier outputs a pulse-width modulated (PWM) square wave, which is the sum of the switching waveform and the amplified input audio signal. The human ear acts as a band-pass filter such that only the frequencies between approximately 20 Hz and 20 kHz are passed. The switching frequency components are much greater than 20 kHz, so the only signal heard is the amplified input audio signal. traditional class-D modulation scheme The traditional class-D modulation scheme, which is used in the TPA005Dxx family, has a differential output where each output is 180 degrees out of phase and changes from ground to the supply voltage, VDD. Therefore, the differential pre-filtered output varies between positive and negative VDD, where filtered 50% duty cycle yields 0 volts across the load. The traditional class-D modulation scheme with voltage and current waveforms is shown in Figure 1. Note that even at an average of 0 volts across the load (50% duty cycle), the current to the load is high causing high loss thus causing a high supply current. OUT+ OUT– +5 V Differential Voltage Across Load OV –5 V Current Figure 1. Traditional Class-D Modulation Scheme’s Output Voltage and Current Waveforms Into an Inductive Load With no Input TPA2001D2 modulation scheme The TPA2001D2 uses a modulation scheme that still has each output switching from 0 to the supply voltage. However, OUT+ and OUT– are now in phase with each other with no input. The duty cycle of OUT+ is greater than 50% and OUT– is less than 50% for positive voltages. The duty cycle of OUT+ is less than 50% and OUT– is greater than 50% for negative voltages. The voltage across the load sits at 0 volts throughout most of the switching period greatly reducing the switching current, which reduces any I2R losses in the load. POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 5 TPA2001D2 1-W FILTERLESS STEREO CLASS-D AUDIO POWER AMPLIFIER SLOS292A – MARCH 2000 – REVISED APRIL 2000 APPLICATION INFORMATION OUT+ OUT– Differential Voltage Across Load Output = 0 V +5 V 0V –5 V Current OUT+ OUT– Differential Voltage Output > 0 V +5 V 0V Across Load –5 V Current Figure 2. The TPA2001D2 Output Voltage and Current Waveforms Into an Inductive Load efficiency: why you must use a filter with the traditional class-D modulation scheme The main reason that the traditional class-D amplifier needs an output filter is that the switching waveform results in maximum current flow. This causes more loss in the load, which causes lower efficiency. The ripple current is large for the traditional modulation scheme because the ripple current is proportional to voltage multiplied by the time at that voltage. The differential voltage swing is 2 × VDD and the time at each voltage is half the period for the traditional modulation scheme. An ideal LC filter is needed to store the ripple current from each half cycle for the next half cycle, while any resistance causes power dissipation. The speaker is both resistive and reactive, whereas an LC filter is almost purely reactive. The TPA2001D2 modulation scheme has very little loss in the load without a filter because the pulses are very short and the change in voltage is VDD instead of 2 × VDD. As the output power increases, the pulses widen making the ripple current larger. Ripple current could be filtered with an LC filter for increased efficiency, but for most applications the filter is not needed. An LC filter with a cut-off frequency less than the class-D switching frequency allows the switching current to flow through the filter instead of the load. The filter has less resistance than the speaker that results in less power dissipated, which increases efficiency. 6 POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 TPA2001D2 1-W FILTERLESS STEREO CLASS-D AUDIO POWER AMPLIFIER SLOS292A – MARCH 2000 – REVISED APRIL 2000 APPLICATION INFORMATION effects of applying a square wave into a speaker Audio specialists have said for years not to apply a square wave to speakers. If the amplitude of the waveform is high enough and the frequency of the square wave is within the bandwidth of the speaker, the square wave could cause the voice coil to jump out of the air gap and/or scar the voice coil. A 250-kHz switching frequency, however, is not significant because the speaker cone movement is proportional to 1/f2 for frequencies beyond the audio band. Therefore, the amount of cone movement at the switching frequency is very small. However, damage could occur to the speaker if the voice coil is not designed to handle the additional power. To size the speaker for added power, the ripple current dissipated in the load needs to be calculated by subtracting the theoretical supplied power, PSUP THEORETICAL, from the actual supply power, PSUP, at maximum output power, POUT. The switching power dissipated in the speaker is the inverse of the measured efficiency, ηMEASURED, minus the theoretical efficiency, ηTHEORETICAL. PSPKR = PSUP – PSUP THEORETICAL (at max output power) (1) PSPKR = PSUP / POUT – PSUP THEORETICAL / POUT (at max output power) (2) PSPKR = 1/ηMEASURED – 1/ηTHEORETICAL (at max output power) (3) The maximum efficiency of the TPA2001D2 with an 8-Ω load is 85%. Using equation 3 with the efficiency at maximum power (78%) there is an additional 106 mW dissipated in the speaker. The added power dissipated in the speaker is not an issue as long as it is taken into account when choosing the speaker. when to use an output filter Design the TPA2001D2 without the filter if the traces from amplifier to speaker are short. The TPA2001D2 passed FCC and CE radiated emissions with no shielding with speaker wires 8 inches long or less. Notebook PCs and powered speakers where the speaker is in the same enclosure as the amplifier are good applications for class-D without a filter. A ferrite bead filter can often be used if the design is failing radiated emissions without a filter, and the frequency sensitive circuit is greater than 1 MHz. This is good for circuits that just have to pass FCC and CE because FCC and CE only test radiated emissions greater than 30 MHz. If choosing a ferrite bead, choose one with high impedance at high frequencies, but very low impedance at low frequencies. Use an output filter if there are low frequency (< 1 MHz) EMI sensitive circuits and/or there are long leads from amplifier to speaker. gain setting via GAIN0 and GAIN1 inputs The gain of the TPA2001D2 is set by two input terminals, GAIN0 and GAIN1. The gains listed in Table 2 are realized by changing the taps on the input resistors inside the amplifier. This causes the input impedance, ZI, to be dependent on the gain setting. The actual gain settings are controlled by ratios of resistors, so the actual gain distribution from part-to-part is quite good. However, the input impedance may shift by 30% due to shifts in the actual resistance of the input resistors. For design purposes, the input network (discussed in the next section) should be designed assuming an input impedance of 20 kΩ, which is the absolute minimum input impedance of the TPA2001D2. At the higher gain settings, the input impedance could increase as high as 115 kΩ. POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 7 TPA2001D2 1-W FILTERLESS STEREO CLASS-D AUDIO POWER AMPLIFIER SLOS292A – MARCH 2000 – REVISED APRIL 2000 APPLICATION INFORMATION Table 2. Gain Settings AMPLIFIER GAIN (dB) INPUT IMPEDANCE (kΩ) TYP TYP 8 104 1 12 74 1 0 17.5 44 1 1 23.5 24 GAIN0 GAIN1 0 0 0 input resistance Each gain setting is achieved by varying the input resistance of the amplifier, which can range from its smallest value to over 6 times that value. As a result, if a single capacitor is used in the input high pass filter, the –3 dB or cut-off frequency will also change by over 6 times. If an additional resistor is connected from the input pin of the amplifier to ground, as shown in the figure below, the variation of the cut-off frequency will be much reduced. ZF Ci IN Input Signal ZI R The –3 dB frequency can be calculated using equation 4: f –3 dB
1 2
C iR  Z I (4) If the filter must be more accurate, the value of the capacitor should be increased while value of the resistor to ground should be decreased. In addition, the order of the filter could be increased. input capacitor, Ci In the typical application an input capacitor, Ci, is required to allow the amplifier to bias the input signal to the proper dc level for optimum operation. In this case, Ci and the input impedance of the amplifier, ZI, form a high-pass filter with the corner frequency determined in equation 5. –3 dB f c(highpass)
(5) 1 2
ZI Ci fc 8 POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 TPA2001D2 1-W FILTERLESS STEREO CLASS-D AUDIO POWER AMPLIFIER SLOS292A – MARCH 2000 – REVISED APRIL 2000 APPLICATION INFORMATION The value of Ci is important as it directly affects the bass (low frequency) performance of the circuit. Consider the example where ZI is 20 kΩ and the specification calls for a flat bass response down to 80 Hz. Equation 5 is reconfigured as equation 6. Ci
1 2
Z I f c (6) In this example, Ci is 0.1 µF so one would likely choose a value in the range of 0.1 µF to 1 µF. If the gain is known and will be constant, use ZI from Table 1 to calculate Ci. A further consideration for this capacitor is the leakage path from the input source through the input network (Ci) and the feedback network to the load. This leakage current creates a dc offset voltage at the input to the amplifier that reduces useful headroom, especially in high gain applications. For this reason a low-leakage tantalum or ceramic capacitor is the best choice. When polarized capacitors are used, the positive side of the capacitor should face the amplifier input in most applications as the dc level there is held at VDD/2, which is likely higher than the source dc level. Note that it is important to confirm the capacitor polarity in the application. Ci must be 10 times smaller than the bypass capacitor to reduce clicking and popping noise from power on/off and entering and leaving shutdown. After sizing Ci for a given cut-off frequency, size the bypass capacitor to 10 times that of the input capacitor. Ci ≤ CBYP / 10 (7) power supply decoupling, CS The TPA2001D2 is a high-performance CMOS audio amplifier that requires adequate power supply decoupling to ensure the output total harmonic distortion (THD) is as low as possible. Power supply decoupling also prevents oscillations for long lead lengths between the amplifier and the speaker. The optimum decoupling is achieved by using two capacitors of different types that target different types of noise on the power supply leads. For higher frequency transients, spikes, or digital hash on the line, a good low equivalent-series-resistance (ESR) ceramic capacitor, typically 0.1 µF placed as close as possible to the device VDD lead works best. For filtering lower-frequency noise signals, a larger aluminum electrolytic capacitor of 10 µF or greater placed near the audio power amplifier is recommended. midrail bypass capacitor, CBYP The midrail bypass capacitor, CBYP, is the most critical capacitor and serves several important functions. During start-up or recovery from shutdown mode, CBYP determines the rate at which the amplifier starts up. The second function is to reduce noise produced by the power supply caused by coupling into the output drive signal. This noise is from the midrail generation circuit internal to the amplifier, which appears as degraded PSRR and THD+N. Bypass capacitor, CBYP, values of 0.47 µF to 1 µF ceramic or tantalum low-ESR capacitors are recommended for the best THD and noise performance. Increasing the bypass capacitor reduces clicking and popping noise from power on/off and entering and leaving shutdown. To have minimal pop, CBYP should be 10 times larger than Ci. CBYP ≥ 10 × Ci (8) POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 9 TPA2001D2 1-W FILTERLESS STEREO CLASS-D AUDIO POWER AMPLIFIER SLOS292A – MARCH 2000 – REVISED APRIL 2000 APPLICATION INFORMATION differential input The differential input stage of the amplifier cancels any noise that appears on both input lines of a channel. To use the TPA2001D2 EVM with a differential source, connect the positive lead of the audio source to the RINP (LINP) input and the negative lead from the audio source to the RINN (LINN) input. To use the TPA2001D2 with a single-ended source, ac ground the RINN and LINN inputs through a capacitor and apply the audio single to the RINP and LINP inputs. In a single-ended input application, the RINN and LINN inputs should be ac grounded at the audio source instead of at the device inputs for best noise performance. shutdown modes The TPA2001D2 employs a shutdown mode of operation designed to reduce supply current, IDD, to the absolute minimum level during periods of nonuse for battery-power conservation. The SHUTDOWN input terminal should be held high during normal operation when the amplifier is in use. Pulling SHUTDOWN low causes the outputs to mute and the amplifier to enter a low-current state, IDD(SD) = 1 µA. SHUTDOWN should never be left unconnected because amplifier operation would be unpredictable. using low-ESR capacitors Low-ESR capacitors are recommended throughout this application section. A real (as opposed to ideal) capacitor can be modeled simply as a resistor in series with an ideal capacitor. The voltage drop across this resistor minimizes the beneficial effects of the capacitor in the circuit. The lower the equivalent value of this resistance the more the real capacitor behaves like an ideal capacitor. evaluation circuit LOUT– GAIN0 GND U1 TPA2001D2 C1 0.1 µF PGND GND PGND LOUTN LOUTP GAIN0 BYPASS LPVDD LPVDD LIN+ C2 0.1 µF C17 120 k 0.1 µF R1 LIN– C3 C7 0.1 µF LINP R3 120 k C18 0.1 µF RIN+ VDD COSC ROSC RINN RINP RPVDD ROUTN GND GAIN1 ROUTP PGND SHUTDOWN VDD 0.1 µF VDD C20 0.1 µF R2 120k C8 RPVDD SHUTDOWN 0.1 µF 10 µF C19 R4 120 k GAIN1 AGND 220 pF RIN– C6 LOUT+ 1 µF C21 LINN C4 C5 10 uF 0.1 µF PGND ROUT+ GND S1 GND GND ROUT– NOTE: R1, R3, and R4 are used in the EVM but are not required for normal applications. 10 POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 TPA2001D2 1-W FILTERLESS STEREO CLASS-D AUDIO POWER AMPLIFIER SLOS292A – MARCH 2000 – REVISED APRIL 2000 APPLICATION INFORMATION Table 3. TPA2001D2 Evaluation Bill of Materials SIZE QUANTITY C1–4, C17–21 REFERENCE Capacitor, ceramic chip, 0.1 µF, ±10%, X7R, 50 V DESCRIPTION 0805 9 Kemet MANUFACTURER C0805C104K5RAC PART NUMBER C5 Capacitor, ceramic, 1.0 µF, +80%/–20%, Y5V, 16 V 0805 1 Murata GRM40-Y5V105Z16 C6, C8 Capacitor, ceramic, 10 µF, +80%/–20%, Y5V, 16 V 1210 2 Murata GRM235-Y5V106Z16 C7 Capacitor, ceramic, 220 pF, ±10%, XICON, 50 V 0805 2 Mouser 140–CC501B221K R2, R1†, R3†, R4† Resistor, chip, 120 kΩ, 1/10 W, 5%, XICON 0805 2 Mouser 260–120K U1 IC, TPA2001D2, audio power amplifier, 2-W, 2-channel, class-D 24 pin TSSOP 1 TI TPA2001D2PWP † These components are used in the EVM, but they are not required for normal applications. POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 11 TPA2001D2 1-W FILTERLESS STEREO CLASS-D AUDIO POWER AMPLIFIER SLOS292A – MARCH 2000 – REVISED APRIL 2000 MECHANICAL DATA PWP (R-PDSO-G**) PowerPAD PLASTIC SMALL-OUTLINE 20 PINS SHOWN 0,30 0,19 0,65 20 0,10 M 11 Thermal Pad (See Note D) 4,50 4,30 0,15 NOM 6,60 6,20 Gage Plane 1 10 0,25 A 0°–
8° 0,75 0,50 Seating Plane 0,15 0,05 1,20 MAX PINS ** 0,10 14 16 20 24 28 A MAX 5,10 5,10 6,60 7,90 9,80 A MIN 4,90 4,90 6,40 7,70 9,60 DIM 4073225/F 10/98 NOTES: A. B. C. D. All linear dimensions are in millimeters. This drawing is subject to change without notice. Body dimensions do not include mold flash or protrusions. The package thermal performance may be enhanced by bonding the thermal pad to an external thermal plane. This pad is electrically and thermally connected to the backside of the die and possibly selected leads. E. Falls within JEDEC MO-153 PowerPAD is a trademark of Texas Instruments Incorporated. 12 POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 PACKAGE OPTION ADDENDUM www.ti.com 10-Dec-2020 PACKAGING INFORMATION Orderable Device Status (1) Package Type Package Pins Package Drawing Qty Eco Plan (2) Lead finish/ Ball material MSL Peak Temp Op Temp (°C) Device Marking (3) (4/5) (6) TPA2001D2PWP ACTIVE HTSSOP PWP 24 60 RoHS & Green NIPDAU Level-2-260C-1 YEAR -40 to 85 TPA2001D2 TPA2001D2PWPR ACTIVE HTSSOP PWP 24 2000 RoHS & Green NIPDAU Level-2-260C-1 YEAR -40 to 85 TPA2001D2 (1) The marketing status values are defined as follows: ACTIVE: Product device recommended for new designs. LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect. NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design. PREVIEW: Device has been announced but is not in production. Samples may or may not be available. OBSOLETE: TI has discontinued the production of the device. (2) RoHS: TI defines "RoHS" to mean semiconductor products that are compliant with the current EU RoHS requirements for all 10 RoHS substances, including the requirement that RoHS substance do not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, "RoHS" products are suitable for use in specified lead-free processes. TI may reference these types of products as "Pb-Free". RoHS Exempt: TI defines "RoHS Exempt" to mean products that contain lead but are compliant with EU RoHS pursuant to a specific EU RoHS exemption. Green: TI defines "Green" to mean the content of Chlorine (Cl) and Bromine (Br) based flame retardants meet JS709B low halogen requirements of