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TPS544B20, TPS544C20
SLUSB69B – MAY 2014 – REVISED JULY 2016
TPS544x20 4.5-V to 18-V, 20-A, and 30-A SWIFT™
Synchronous Buck Converters with PMBus™
1 Features
3 Description
•
•
•
•
•
The TPS544B20 and TPS544C20 devices are
PMBus compatible, non-isolated DC-DC Integrated
FET converters, capable of high-frequency operation
and delivering 20-A , or 30-A current output from a
5 mm × 7 mm package, enabling high-power density
and fast transient performance with minimal PCB
area. The PMBus interface provides for converter
configuration as well as monitoring of key parameters
including output voltage, current and an optional
external temperature. High-frequency, low-loss
switching, provided by an integrated NexFET power
stage and optimized drivers, allows for very highdensity power solutions and reduced inductor and
filter capacitor sizes. Response to fault conditions can
be set to either restart or latch off depending on
system requirements.
1
•
•
•
•
•
•
•
•
•
•
•
PMBus-Enabled Converters: 20 A, 30 A
4.5-V to 18-V input, 0.6-V to 5.5-V Output
5 mm × 7 mm LQFN Package with 0.5-mm Pitch
Single Thermal Pad
Integrated 4.5-mΩ and 2.0-mΩ Stacked
NexFET™ Power Stage
600-mV, 0.5% Reference
Lossless, Low-Side MOSFET Current Sensing
Selectable D-CAP™ and D-CAP2™ Mode Control
Differential Remote Sensing
Monotonic Start-Up into Pre-Biased Output
Output Voltage Margin and Trim
Output Voltage and Output Current Reporting
External Temperature Monitoring with 2N3904
Programmable via PMBus
– Overcurrent Protection
– UVLO, Soft-Start
– PGOOD, OV, UV, OT Levels
– Fault Responses
– Turn-On and Turn-Off Delays
Thermal Shutdown
Pin Compatible 20-A, 30-A Converters
Table 1. Device Information(1)
PART NAME
TPS544B20
TPS544C20
LQFN (40)
5.00 mm × 7.00 mm
Efficiency vs Output Current
100
95
90
Efficiency (%)
•
•
•
Test and Instrumentation
Ethernet Switches, Optical Switches, Routers,
Base Stations
Servers
Enterprise Storage SSD
High-Density Power Solutions
BODY SIZE (NOM)
(1) For all available packages, see the orderable addendum at
the end of the datasheet.
2 Applications
•
•
PACKAGE
85
80
75
Output Voltage
70
65
0.6 V
0.8 V
1.0 V
1.2 V
1.8 V
2.5 V
3.3 V
60
0
5
10
15
Load Current (A)
VIN = 12 V
fSW = 500 kHz
L = 410 nH
RDCR = 0.3 mŸ
20
25
30
C003
Snubber = Open
RBOOT = 0 Ÿ
1
An IMPORTANT NOTICE at the end of this data sheet addresses availability, warranty, changes, use in safety-critical applications,
intellectual property matters and other important disclaimers. PRODUCTION DATA.
TPS544B20, TPS544C20
SLUSB69B – MAY 2014 – REVISED JULY 2016
www.ti.com
Table of Contents
1
2
3
4
5
6
7
Features ..................................................................
Applications ...........................................................
Description .............................................................
Revision History.....................................................
Device Comparison Table.....................................
Pin Configuration and Functions .........................
Specifications.........................................................
7.1
7.2
7.3
7.4
7.5
7.6
7.7
8
1
1
1
2
4
4
6
Absolute Maximum Ratings ...................................... 6
ESD Ratings.............................................................. 6
Recommended Operating Conditions....................... 6
Thermal Information .................................................. 7
Electrical Characteristics........................................... 8
Switching Characteristics ........................................ 11
Typical Characteristics ............................................ 12
Detailed Description ............................................ 16
8.1
8.2
8.3
8.4
Overview .................................................................
Functional Block Diagram .......................................
Feature Description.................................................
Device Functional Modes........................................
16
16
17
27
8.5 Programming........................................................... 28
8.6 Register Maps ......................................................... 30
9
Applications and Implementation ...................... 52
9.1 Application Information............................................ 52
9.2 Typical Application .................................................. 52
10 Power Supply Recommendations ..................... 61
11 Layout................................................................... 62
11.1 Layout Guidelines ................................................. 62
11.2 Layout Example .................................................... 63
12 Device and Documentation Support ................. 65
12.1
12.2
12.3
12.4
12.5
12.6
12.7
Device Support......................................................
Related Links ........................................................
Trademarks ...........................................................
Receiving Notification of Documentation Updates
Community Resources..........................................
Electrostatic Discharge Caution ............................
Glossary ................................................................
65
66
66
67
67
67
67
13 Mechanical, Packaging, and Orderable
Information ........................................................... 67
4 Revision History
NOTE: Page numbers for previous revisions may differ from page numbers in the current version.
Changes from Revision A (February 2016) to Revision B
Page
•
Changed From: PGND to GND in the Pin Functions table Description for pins BP6 and BPEXT. ....................................... 4
•
Changed Pin Functions table Description for VDD pin To: "Bypass with a 0.1-µF to 1.0-µF capacitor to GND
(thermal pad or GND pins) or through a dedicated connection to AGNDSNS." ................................................................... 5
•
Changed From: "PGND" To: "GND" in Linear Regulators BP3 and BP6 and External Bypass (BPEXT) Section text. ..... 20
•
Changed instances From: "PGND" To: "GND" in the Device Functional Modes ................................................................. 27
•
Changed From: " a value of 4.7 μF" To: " a value of 0.1 μF to 1.0 μF" in the Input Capacitor Selection ............................ 55
•
Changed text string From: "...one 4.7-μF, 25-V ceramic capacitor..." To: "...one 1.0-μF, 25-V ceramic capacitor..." in
the Input Capacitor Selection description. ............................................................................................................................ 56
•
Changed From: "PGND" To: "GND" in the BP6, BP3 and BPEXT section ......................................................................... 56
•
Added text to Layout Guidelines section for emphasis on grounding schemes. ................................................................. 62
•
Changed PCB Layout Recommendation figure. ................................................................................................................. 63
•
Added Receiving Notification of Documentation Updates section. ...................................................................................... 67
Changes from Original (May 2014) to Revision A
Page
•
Deleted package suffix and reel quantities from Device Comparison Table ......................................................................... 4
•
Changed "Handling" Ratings table to "ESD" Ratings and moved Tstg spec to the Absolute Maximum Ratings table........... 6
•
Added sentence in Switching Frequency description........................................................................................................... 20
•
Changed "Hiccup" to "Shutdown and latch-off" as the Default Behavior for CMD Command; and, changed Default
Register Value from 3Fh to 07h in Table 5, CMD Code 47h .............................................................................................. 29
•
Changed "address" to "frequency" in the PMBus Command Description for CMD Code 80h in Table 5. .......................... 29
•
Changed Default Value for Bit Position 5, 4, and 3 from 1 1 1 to 0 0 0 respectively in the
IOUT_OC_FAULT_RESPONSE (47h) table. ...................................................................................................................... 37
•
Changed "IVADDR" to "IVFREQ" for Function at Bit Position 4 of the STATUS_MFR_SPECIFIC (80h); and also in
the accompanying description. ............................................................................................................................................ 44
2
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TPS544B20, TPS544C20
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•
SLUSB69B – MAY 2014 – REVISED JULY 2016
Added Community Resources section ................................................................................................................................ 66
Copyright © 2014–2016, Texas Instruments Incorporated
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3
TPS544B20, TPS544C20
SLUSB69B – MAY 2014 – REVISED JULY 2016
www.ti.com
5 Device Comparison Table
DEVICE NUMBER
CURRENT OPTION (A)
TPS544B20
20
TPS544C20
30
6 Pin Configuration and Functions
FB
DIFFO
COMP
TSNS
PGOOD
AGND
MODE
RT
RVF Package
40-Pin LQFN with Thermal Tab
(TOP VIEW)
40 39 38 37 36 35 34 33
1
32 VOUTSt
ADDR1 2
31 VOUTS+
ADDR0
3
30 BPEXT
DATA
4
29 VDD
CLK
5
28 BP6
SMBALERT
6
27 BP3
BOOT
7
26 PGND
SW
8
25 VIN
SW
9
24 VIN
SW 10
23 VIN
CNTL
SW 11
22 VIN
Thermal Tab
21 VIN
SW 12
GND
GND
GND
GND
GND
GND
GND
AGNDSNS
13 14 15 16 17 18 19 20
Pin Functions
PIN
I/O (1)
DESCRIPTION
NAME
NO.
ADDR0
3
O
Sets low order 3-bits of the PMBus address. Connect a resistor from this pin to AGND.
ADDR1
2
O
Sets high order 3-bits of the PMBus address. Connect a resistor from this pin to AGND.
AGNDSNS
13
G
Analog ground sense. Provides Kelvin connection point to analog ground for precise current
measurement. AGNDSNS is internally connected to the thermal tab. Do not connect to the thermal tab
externally. Kelvin connect back to AGND pin with a low impedance, low noise path. This kelvin
connection serves as the only connection between AGND and GND.
AGND
38
G
Analog ground return for control circuitry. AGND should not be connected to the exposed thermal pad,
GND or PGND, but should be Kelvin connected to the AGNDSNS pin.
BP3
27
S
Output of the 3.3-V on-board regulator. This regulator powers the controller and should be bypassed
with a minimum of 100-nF capacitor to AGND.
BP6
28
S
Output of the 6-V on-board regulator. This regulator powers the driver stage of the controller and should
be bypassed with a 4.7-µF ceramic capacitor to GND.
BOOT
7
S
Bootstrap pin for the internal flying high-side driver. Connect a typical 100-nF capacitor from this pin to
the SW pins.
(1)
4
I = Input, O = Output, P = Supply, G = Ground
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SLUSB69B – MAY 2014 – REVISED JULY 2016
Pin Functions (continued)
PIN
I/O (1)
DESCRIPTION
30
I
External BP voltage for BP crossover function. Bypass with a 4.7-µF ceramic capacitor to GND if used..
Connect to GND if not used.
CLK
5
I
PMBus CLK pin. See PMBus specification.
CNTL
1
I
PMBus CNTL pin. See PMBus specification.
COMP
35
O
Output of the error amplifier. This regulates the D-CAP and D-CAP2 valley voltage reference for output
regulation and should be bypassed with a 10-nF capacitor to AGND.
DATA
4
I/O
PMBus DATA pin. See PMBus specification.
DIFFO
33
O
Output of the differential sense amplifier.
FB
34
I
Feedback pin for the control loop. Regulates to a nominal 600 mV if there is no trim applied to the
device using VREF_TRIM.
G
Power stage ground return.
NAME
NO.
BPEXT
14
15
16
GND
17
18
19
20
PGND
26
G
Power ground return for controller device. Connect to GND at the thermal tab with a minimum 8 mil
wide PCB trace
PGOOD
36
O
Power good output. Open drain output that floats up when the device is operating and in regulation. Any
fault condition causes this pin to pull low.
RT
40
O
Frequency-setting resistor. Connect a resistor from this pin to AGND to program the switching
frequency.
SMBALERT
6
O
SMBus alert pin. See SMBus specification.
O
Switched power output of the device. Connect the output averaging filter and bootstrap capacitor to this
group of pins.
8
9
SW
10
11
12
MODE
39
I
D-CAP and D-CAP2 control mode selection pin. Connect to BP3 for D-CAP2 mode control. Connect to
AGND for D-CAP mode control.
TSNS
37
O
External temperature sense signal input. TSNS can be connected to AGND to disable external
temperature measurement.
I
Input Voltage for analog control circuitry. Bypass with a 0.1-µF to 1.0-µF capacitor to GND (thermal pad
or GND pins) or through a dedicated connection to AGNDSNS. The VDD voltage is also used for input
feed-forward, ON-time generation and High Side Over Current (HSOC). VIN and VDD must be at the
same voltage for accurate short circuit protection.
I
Input power to the power stage. Bypass High-Frequency bypassing with multiple ceramic capacitors to
GND is critical. See Layout Recommendations
VDD
29
21
22
VIN
23
24
25
VOUTS+
31
I
Output voltage sensing, positive side. This sensing provides remote sensing for PMBus reporting and
the voltage control loop. Connect to VOUT at desried regulation point through < 100-Ω resistor. Route
with GND to VOUT- using coupled differential pair PCB routing.
VOUTS–
32
I
Output voltage sensing, negative or common side. This sensing provides remote sensing for PMBus
reporting and the voltage control loop. Connect to Ground at desried regulation point through < 100-Ω
resistor. Route with VOUT to VOUT+ using coupled differential pair PCB routing.
Thermal tab
Package thermal tab. Connect to GND. The thermal tab must have adequate solder coverage for proper
operation.
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TPS544B20, TPS544C20
SLUSB69B – MAY 2014 – REVISED JULY 2016
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7 Specifications
7.1 Absolute Maximum Ratings
over operating free-air temperature range (unless otherwise noted) See
Input voltage
Output voltage
(1) (2) (3)
MIN
MAX
VIN, VDD
–0.3
20
BOOT
–0.3
37
BOOT – SW (BOOT to SW differential)
–0.3
7
CLK, DATA
–0.3
3.6
FB, SYNC, CNTL, VOUTS–, VOUTS+, BPEXT
–0.3
7
BP6
–0.3
7
SW
–1
30
SW ( > 50 ns, > 10 µJ)
-5
30
COMP, DIFFO, SMBALERT, PGOOD
–0.3
7
ADDR0, ADDR1, BP3, RT, TSNS
UNIT
V
V
–0.3
3.6
TJ , operating junction temperature
–40
150
°C
Tstg, Storage temperature
–55
150
°C
(1)
(2)
(3)
Absolute Maximum Ratings indicate limits beyond which damage to the device may occur, including inoperability and degradation of
device reliability or performance. Functional operation of the device and/or non-degradation at the Absolute Maximum Ratings or other
conditions beyond those indicated in the Operating Ratings is not implied. The recommended Operating Ratings indicate conditions at
which the device is functional and the device should not be operated beyond such conditions.
The human body model is a 100-pF capacitor discharged through a 1.5-kΩ resistor into each pin.
If Military or Aerospace specified devices are required, contact the Texas Instruments Sales/Office/Distributors for availability and
specifications.
7.2 ESD Ratings
VALUE
V(ESD)
(1)
(2)
Electrostatic discharge
Human body model (HBM), per ANSI/ESDA/JEDEC JS-001, all
pins (1)
±2000
Charged device model (CDM), per JEDEC specification JESD22C101, all pins (2)
±500
UNIT
V
JEDEC document JEP155 states that 500-V HBM allows safe manufacturing with a standard ESD control process.
JEDEC document JEP157 states that 250-V CDM allows safe manufacturing with a standard ESD control process.
7.3 Recommended Operating Conditions
over operating free-air temperature range (unless otherwise noted)
MIN
TYP
MAX
UNIT
VDD
Controller input voltage
4.5
18
V
VIN
Power stage input voltage
4.5
18
V
TJ
Junction temperature
–40
125
°C
6
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SLUSB69B – MAY 2014 – REVISED JULY 2016
7.4 Thermal Information
THERMAL METRIC (1)
(2)
TPS544B20
TPS544C20
UNIT
RθJA
Junction-to-ambient thermal resistance
27.5
°C/W
RθJCtop
Junction-to-case (top) thermal resistance (3)
13.9
°C/W
RθJB
Junction-to-board thermal resistance
4.0
°C/W
ψJT
Junction-to-top characterization parameter (4)
0.3
°C/W
ψJB
Junction-to-board characterization parameter (5)
3.9
°C/W
(6)
0.9
°C/W
RθJCbot
(1)
(2)
(3)
(4)
(5)
(6)
Junction-to-case (bottom) thermal resistance
For more information about traditional and new thermal metrics, see the IC Package Thermal Metrics application report, SPRA953.
The junction-to-ambient thermal resistance under natural convection is obtained in a simulation on a JEDEC-standard, high-K board, as
specified in JESD51-7, in an environment described in JESD51-2a.
The junction-to-case (top) thermal resistance is obtained by simulating a cold plate test on the package top. No specific JEDECstandard test exists, but a close description can be found in the ANSI SEMI standard G30-88.
The junction-to-top characterization parameter, ψJT, estimates the junction temperature of a device in a real system and is extracted
from the simulation data for obtaining RθJA, using a procedure described in JESD51-2a (sections 6 and 7).
The junction-to-board characterization parameter, ψJB, estimates the junction temperature of a device in a real system and is extracted
from the simulation data for obtaining RθJA, using a procedure described in JESD51-2a (sections 6 and 7).
The junction-to-case (bottom) thermal resistance is obtained by simulating a cold plate test on the exposed (power) pad. No specific
JEDEC standard test exists, but a close description can be found in the ANSI SEMI standard G30-88.
Spacer
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TPS544B20, TPS544C20
SLUSB69B – MAY 2014 – REVISED JULY 2016
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7.5 Electrical Characteristics
TJ = –40°C to 125°C, VIN = VVDD= 12 V, RRT = 38.3 kΩ; zero power dissipation (unless otherwise noted)
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
INPUT SUPPLY
VVDD
Input supply voltage range
4.5
18
VVIN
Power stage voltage range
4.5
18
V
V
IVDD
Input Operating Current
Not switching
10
mA
VIN(on)
Input turn on voltage
Default settings
4.05
4.25
4.45
V
VIN(off)
Input turn off voltage
Default settings
3.8
4
4.2
V
VINON(rng)
Programmable range for turn-on
voltage
4.25
16
V
VINOFF(rng)
Programmable range for turn-off
voltage
4
15.75
V
UVLO
ERROR AMPLIFIER AND FEEDBACK VOLTAGE
0°C ≤ TJ ≤ 70°C
597
600
603
–40°C ≤ TJ ≤ 125°C
594
600
606
VFB
Feedback Voltage
gM
Transconductance
IFB
FB pin bias current (out of pin)
VFB = 0.6 V
VLOOP_COMP
Loop comparator offset voltage
VFB = 0.6 V, TJ = 25°C
130
-7.5
mV
µS
50
nA
7.5
mV
BP6 REGULATOR
VBP6
Output voltage
IBP6 = 10 mA
VBP6(do)
Dropout voltage
VVIN – VBP6, VVDD = 4.5 V, IBP6 = 25 mA
6.2
6.5
6.8
V
100
mV
IBP6
Output current (1)
VVDD = 12 V
VBP6UV
Regulator UVLO voltage (1)
3.3
3.55
3.8
V
VBP6UV(hyst)
Regulator UVLO voltage
hysteresis (1)
230
255
270
mV
4.5
4.65
200
mV
120
mA
BPEXT
VBPEXT(swover)
BPEXT switch-over voltage
Vhys(swover)
BPEXT switch-over hysteresis
VDD > VIN(on)
VBPEXT(do)
BPEXT dropout voltage
VBPEXT -VBP6, VBPEXT = 4.8 V, IBP6 = 25 mA
100
mV
Bootstrap voltage drop
IBOOT = 5 mA
150
mV
3.5
V
100
V
BOOTSTRAP
VBOOT(drop)
BP3 REGULATOR
VBP3
Output voltage
VVDD = 4.5 V, IBP3 ≤ 5 mA
Soft-start time (2)
Factory default settings
3.1
3.3
SOFT START
tSS
Programmable range (1)
2.7
0.6
Accuracy over range (1)
ms
9
ms
±10%
tON(DELAY)
Turn-on delay
Factory default settings
0
ms
tOFF(DELAY)
Turn-off delay
Factory default settings
0
ms
(1)
(2)
8
Specified by design. Not production tested.
Soft-start time is defined by the rise time of the internal reference, VREF
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SLUSB69B – MAY 2014 – REVISED JULY 2016
Electrical Characteristics (continued)
TJ = –40°C to 125°C, VIN = VVDD= 12 V, RRT = 38.3 kΩ; zero power dissipation (unless otherwise noted)
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
REMOTE SENSE AMPLIFIER
VDIFFO(ERROR)
Error voltage from DIFFO to VSNS
BW
Closed-loop bandwidth (1)
RVOUTx
Output voltage sense input
impedance
VDIFFO(max)
Maximum DIFFO output voltage
IDIFFO
(VOUTS+ – VOUTS–) = 0.6 V
-5
(VOUTS+ – VOUTS–) = 1.2 V
-8
5
8
(VOUTS+ – VOUTS–) = 3.0 V
-17
17
2
VOUT+ = 1.2V
55
MHz
80
105
VBP6-0.2
DIFFO sourcing current
1
DIFFO sinking current
1
mV
kΩ
V
mA
POWER STAGE
RHS
High-side on-resistance
IHS(leak)
High-side leakage current
RLS
Low-side on-resistance
VVDD = 4.5 V, TJ = 25°C
4.9
VVDD ≥ 12 V, TJ = 25°C
4.5
VVDD = 18 V, TJ = 25°C
0.4
VVDD = 18 V, TJ = 125°C (1)
1.5
VVDD = 4.5 V, TJ = 25°C
2.2
VVDD ≥ 12 V, TJ = 25°C
2.0
mΩ
0.7
µA
mΩ
CURRENT LIMIT
tOFF(OC)
Off time between restart attempts
Hiccup mode
Factory default settings
IOC(flt)
Output current overcurrent fault
threshold
Programmable range
Factory default settings
Programmable range
Factory default settings
IOC(warn)
Output current overcurrent warning Programmable range
threshold
Factory default settings
Programmable range
IOC(acc)
Output current overcurrent fault
and warning accuracy
tLSOC(min)
Minimum LDRV pulse width for
valid current sensing (1)
7 × tSS
TPS544B20
TPS544C20
TPS544B20
TPS544C20
ms
26
5
30
39
5
A
45
20
4
29.5
30
4
IOCF = 20 A (1)
A
44.5
±3
400
A
500
ns
HIGH-SIDE SHORT CIRCUIT PROTECTION
IHSOC
High-side short-circuit protection
fault threshold
TJ = 25°C
TPS544B20
30
58
TPS544C20
45
75
A
POWER GOOD (PGOOD)
VFBPGH
FB PGOOD high threshold
Factory default settings
675
VFBPGL
FB PGOOD low threshold
Factory default settings
525
VPG(acc)
PGOOD accuracy over range
Factory default settings
Vpg(hyst)
FB PGOOD hysteresis voltage
RPGOOD
PGOOD pull-down resistance
VFB = 0, IPGOOD = 5 mA
IPGOOD(lk)
PGOOD pin leakage current
Factory default settings, VPGOOD = 5 V
–5%
mV
mV
5%
10
50
30
mV
70
Ω
20
µA
OUTPUT OVERVOLTAGE AND UNDERVOLTAGE PROTECTION
VFBOV
FB pin over voltage threshold
Factory default settings
700
VFBUV
FB pin under voltage threshold
Factory default settings
499
VUVOV(acc)
FB UV, OV accuracy over range
Factory default settings
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–4.5%
mV
mV
4.5%
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Electrical Characteristics (continued)
TJ = –40°C to 125°C, VIN = VVDD= 12 V, RRT = 38.3 kΩ; zero power dissipation (unless otherwise noted)
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
OUTPUT VOLTAGE TRIMMING AND MARGINING
VFBTM(step)
Resolution of FB steps with trim
and margin
tFBTM(step)
Transition time per trim or margin
step
VFBTM(max)
2
mV
30
µs
Maximum FB voltage with trim or
margin only
660
mV
VFBTM(min)
Minimum FB voltage with trim or
margin only
480
mV
VFBTM(rng)
FB voltage range with trim and
margin combined
VFBMH
Margin high FB pin voltage
Factory default settings
660
mV
VFBML
Margin low FB pin voltage
Factory default settings
540
mV
After soft-start time
420
660
mV
TEMPERATURE SENSE AND THERMAL SHUTDOWN
TSD
Junction shutdown temperature (1)
135
145
155
°C
THYST
Thermal shutdown hysteresis (1)
20
25
30
°C
ITSNS(ratio)
Ratio of bias current flowing out of
TSNS pin, state 2 to state 1
9.7
10.0
10.3
ITSNS
State 1 current out of TSNS pin
10
ITSNS
State 2 current out of TSNS pin
100
VTSNS
Voltage range on TSNS pin (1)
Overtemperature fault limit (1)
TOT(flt)
0
Factory default settings
OT fault limit range (1)
Overtemperature warning limit (1)
TOT(warn)
TOT(step)
OT fault, warning step (1)
TOT(hys)
OT fault, warning hysteresis (1)
µA
150
Factory default settings
OT warning limit range (1)
µA
1.00
120
165
125
100
140
5
15
20
µA/µA
V
°C
°C
°C
25
°C
V
MEASUREMENT SYSTEM
MVOUT(rng)
Output voltage measurement
range
0.5
5.8
MVOUT(acc)
Output voltage measurement
accuracy
–2.0%
2.0%
MVOUT(lsb)
Output voltage measurement bit
resolution
MIOUT(acc)
Output current measurement
accuracy (3)
MIOUT(lsb)
Output current measurement bit
resolution (1)
MTSNS(rng)
External temperature sense
range (1)
MTSNS(acc)
External temperature sense
accuracy (1)
MTSNS(lsb)
External temperature sense bit
resolution (1)
1.95
IOUT ≥ 20 A, -40 ≤ TA ≤ 85°C
3 A ≤ IOUT < 20 A, –40 ≤ TA ≤ 85°C
mV
-15%
+15%
-3
+3
62.5
-40°C ≤ TJ(sensor) ≤ 165°C
A
mA
-40
165
°C
-8
8
°C
1.238
°C
PMBus INTERFACE ADDRESSING
IADD
Address pin bias current
8.23
VADD(rng)
Address pin legal address voltage
range
0.08
(3)
10
9.75
11.21
µA
2.35
V
Current sense amplifier gain and offset are production tested. Output current monitoring guaranteed by correlation.
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SLUSB69B – MAY 2014 – REVISED JULY 2016
7.6 Switching Characteristics
VIN = VDD = 12 V, TA = 25 ºC, RRT = 38.3 kΩ (unless otherwise specified).
PARAMETER
TEST CONDITIONS
MIN
TYP
MAX
UNIT
TON GENERATOR AND SW TIMING
Switching frequency (1)
fSW
IRT
RT output current
tOFF(min)
Minimum off-time (2)
tON(min)
Minimum controllable pulse width (2)
VDCAP2
D-CAP2 mode threshold
VDCAP
D-CAP mode threshold
IMODE
MODE output current
tDEAD
Power stage driver dead-time (2)
tSLEW(SW)
(1)
(2)
(3)
SW slew rate
Adjustment range
250
RRT = 10.0 kΩ
210
250
1000
290
RRT = 17.8 kΩ
250
300
350
RRT = 27.4 kΩ
340
400
460
RRT = 38.3 kΩ
425
500
575
RRT = 56.2 kΩ
550
650
750
RRT = 86.6 kΩ
640
750
860
RRT = 133 kΩ
720
850
980
RRT = 205 kΩ
850
1000
1150
kHz
9.75
(3)
(2)
µA
175
ns
80
ns
2.10
V
13
µA
0.8
V
7
SW rising
15
SW falling
15
SW rising (10% to 90%), IOUT = 30
A, RBOOT= 0 Ω
9.2
SW falling (90% to 10%), IOUT = 30
A, RBOOT= 0 Ω
6.2
ns
V/ns
On-times are production tested, but steady-state switching frequency is not.
Specified by design. Not production tested.
Minimum off time for valid current sensing is 400-ns typical, 500-ns maximum.
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7.7 Typical Characteristics
3.0
6.25
2.8
6.00
High-Side MOSFET
On-Resistance (mŸ)
Low-Side MOSFET
On-Resistance (mŸ)
VIN = VDD = 12 V, TA = 25 ºC, RRT = 38.3 kΩ (unless otherwise specified). Safe operating area curves were measured using a
Texas Instruments Evaluation Module.
2.6
2.4
2.2
2.0
5.75
5.50
5.25
5.00
4.75
4.50
1.8
4.25
1.6
4.00
±50
±25
0
25
50
75
100
125
150
Junction Temperature (£C)
±50
Non-Switching Quiescent Current (mA)
Feedback Voltate (mV)
604
603
602
601
600
599
598
597
596
595
0
25
50
75
100
125
C008
VVDD==12
12VV
Vdd
Vdd
VVDD==18
18VV
5.0
±25
0
25
50
75
100
125
150
Junction Temperature (£C)
C001
Figure 4. Non-Switching Input Current (IVDD) vs. Junction
Temperature
3.255
6.510
3.250
BP3 Voltage (V)
BP6 Voltage (V)
150
Vdd
VVDD==4.5
4.5VV
5.5
6.515
3.245
3.240
3.235
6.490
3.230
6.485
3.225
3.220
±50
±25
0
25
50
75
100
125
150
Junction Temperature (£C)
IBP6 = 25 mA
Figure 5. BP6 Voltage vs. Junction Temperature
12
6.0
3.260
6.480
125
6.5
6.520
6.495
100
7.0
±50
Figure 3. Feedback Voltage vs. Junction Temperature
6.500
75
7.5
C009
6.505
50
8.0
150
Junction Temperature (£C)
25
Figure 2. High-Side MOSFET On-Resistance (RDS(on)) vs.
Junction Temperature
605
±25
0
Junction Temperature (£C)
Figure 1. Low-Side MOSFET On-Resistance (RDS(on)) vs.
Junction Temperature
±50
±25
C007
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±50
±25
0
25
50
75
100
125
150
Junction Temperature (£C)
C005
C006
IBP3 = 5 mA
Figure 6. BP3 Voltage vs. Junction Temperature
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SLUSB69B – MAY 2014 – REVISED JULY 2016
Typical Characteristics (continued)
VIN = VDD = 12 V, TA = 25 ºC, RRT = 38.3 kΩ (unless otherwise specified). Safe operating area curves were measured using a
Texas Instruments Evaluation Module.
4.40
45
Turn-On Voltage (V)
PGOOD Pull-Down Resistance (Ÿ)
50
40
35
30
4.35
4.30
4.25
25
4.20
20
±50
±25
0
25
50
75
100
125
Junction Temperature (£C)
±50
150
0
±25
25
50
75
100
125
Junction Temperature (£C)
C004
150
C011
VIN_ON = 4.25 V
Figure 8. Turn-On Voltage vs. Junction Temperature
Figure 7. PGOOD Pull-Down Resistance vs. Junction
Temperature
125
Maximum Ambient Temperature (£C)
Turn-Off Voltage (V)
4.10
4.05
4.00
3.95
3.90
105
85
65
Nat. Conv
100 LFM
45
200 LFM
400 LFM
25
±50
0
±25
25
50
75
100
125
Junction Temperature (£C)
150
0
10
15
20
25
Load Current (A)
VIN_OFF = 4.00 V
VIN = 12 V
Figure 9. Turn-Off Voltage vs. Junction Temperature
30
C001
VOUT = 0.9 V
fSW = 650 kHz
Figure 10. Safe Operating Area
125
Maximum Ambient Temperature (£C)
125
Maximum Ambient Temperature (£C)
5
C012
105
85
65
Nat. Conv
100 LFM
45
200 LFM
400 LFM
25
105
85
65
Nat. Conv
100 LFM
45
200 LFM
400 LFM
25
0
5
10
15
20
Load Current (A)
VIN = 12 V
VOUT = 0.9 V
Figure 11. Safe Operating Area
Copyright © 2014–2016, Texas Instruments Incorporated
25
30
0
5
fSW = 300 kHz
10
15
20
25
Load Current (A)
C002
VIN = 12 V
VOUT =1.8 V
30
C003
fSW = 650 kHz
Figure 12. Safe Operating Area
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Typical Characteristics (continued)
VIN = VDD = 12 V, TA = 25 ºC, RRT = 38.3 kΩ (unless otherwise specified). Safe operating area curves were measured using a
Texas Instruments Evaluation Module.
125
Maximum Ambient Temperature (£C)
Maximum Ambient Temperature (£C)
125
105
85
65
Nat. Conv
100 LFM
45
200 LFM
400 LFM
25
105
85
65
Nat. Conv
100 LFM
45
200 LFM
400 LFM
25
0
5
10
15
20
25
Load Current (A)
VIN = 12 V
30
0
VOUT = 1.8 V
fSW = 300 kHz
VIN = 12 V
Figure 13. Safe Operating Area
20
25
30
C005
VOUT = 3.3 V
fSW = 650 kHz
Figure 14. Safe Operating Area
Maximum Ambient Temperature (£C)
Maximum Ambient Temperature (£C)
15
125
105
85
65
Nat. Conv
100 LFM
45
200 LFM
400 LFM
0
5
105
85
65
Nat. Conv
100 LFM
45
200 LFM
400 LFM
25
25
10
15
20
25
Load Current (A)
VIN = 12 V
0
30
5
10
VOUT = 3.3 V
15
20
25
Load Current (A)
C006
VIN = 5 V
fSW = 300 kHz
30
C007
VOUT = 0.9 V
fSW = 650 kHz
Figure 16. Safe Operating Area
Figure 15. Safe Operating Area
125
Maximum Ambient Temperature (£C)
125
Maximum Ambient Temperature (£C)
10
Load Current (A)
125
105
85
65
Nat. Conv
100 LFM
45
200 LFM
400 LFM
25
105
85
65
Nat. Conv
100 LFM
45
200 LFM
400 LFM
25
0
5
10
15
20
Load Current (A)
VIN = 5 V
VOUT = 0.9 V
Figure 17. Safe Operating Area
14
5
C004
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25
30
0
5
fSW = 300 kHz
10
15
20
Load Current (A)
C008
VIN = 5 V
VOUT = 1.8 V
25
30
C009
fSW = 650 kHz
Figure 18. Safe Operating Area
Copyright © 2014–2016, Texas Instruments Incorporated
TPS544B20, TPS544C20
www.ti.com
SLUSB69B – MAY 2014 – REVISED JULY 2016
Typical Characteristics (continued)
VIN = VDD = 12 V, TA = 25 ºC, RRT = 38.3 kΩ (unless otherwise specified). Safe operating area curves were measured using a
Texas Instruments Evaluation Module.
Maximum Ambient Temperature (£C)
125
105
85
65
Nat. Conv
100 LFM
45
200 LFM
400 LFM
25
0
5
10
15
20
25
Load Current (A)
VIN = 5 V
VOUT = 1.8 V
30
C010
fSW = 300 kHz
Figure 19. Safe Operating Area
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TPS544B20, TPS544C20
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8 Detailed Description
8.1 Overview
The TPS544B20 and TPS544C20 devices are 20-A, and 30-A, high-performance, synchronous buck converters
with two integrated N-channel NexFET™ power MOSFETs. These devices implement TI's proprietary D-CAP
and D-CAP2 mode control providing natural input voltage feed-forward and fast transient response with a
precision error amplifier and low-offset differential remote sense amplifier for precise ouptut voltage regulation
with minimal external compensation. Monotonic pre-bias capability eliminates concerns about damaging sensitive
loads. Integrated PMBus capability provides current, voltage and on-board temperature monitoring, as well as
many user-programmable configuration options as well as Adaptive Voltage Scaling (AVS) and output voltage
margin testing.
8.2 Functional Block Diagram
VDD
BP6
VIN
Linear Regulators and
BP Switchover
BP3
BP6
BOOT
Minimum tOFF
Delay
BPEXT
VPBEXT(swovr)
Stacked
1H[)(7Œ
Power
Stage &
Sensefet
+
Fault
FB
S
Q
R
Q
Driver Control:
Anti-Cross
Conduction,
Prebias
+
COMP
SW
On-Time
Generator
BP6
SW
+
GND
RT
fSW Decode
Reference
DAC
Reference Soft-Start, Trim and Margin
Average IOUT
VOUTS +
Overcurrent
Detection,
Current
Sensing
OC Threshold
VOUTS -CLK
SMBALRT
Temperature
Sensing
Interface
TSNS
AGND
Analog
PMBus 1.1 Inputs and
Interface
ADC
and
Commands EEPROM
DATA
AGNDSNS
Fault
Device
Interface
VOUT+
+
CNTL
VOUT-
PMBus Engine.
TPS544C20
ADDR0 ADDR1
16
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PGOOD
PGND
DIFFO
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TPS544B20, TPS544C20
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SLUSB69B – MAY 2014 – REVISED JULY 2016
8.3 Feature Description
8.3.1 Turn-On and Turn-Off Delay and Sequencing
The TPS544C20 and TPS544B20 devices provide many sequencing options. Using the ON_OFF_CONFIG
command, the device can be configured to start up when the input voltage is above the undervoltage lockout
(UVLO) threshold, or to additionally require a signal on the CNTL pin and/or receive an update to the
OPERATION command according to the PMBus protocol. When the gating signal as specified by
ON_OFF_CONFIG command is asserted, a programmable turn-on delay can be set with the TON_DELAY
command to delay the start of regulation. Similarly, a programmable turn-off delay can be set with the
TOFF_DELAY command to delay the stop of regulation once the gating signal is de-asserted. Delay times are
specified as an integer multiple of the soft-start time.
When the output voltage remains within the PGOOD window after the start-up period, PGOOD is released, and
rises to an externally supplied logic level. The PGOOD signal can be connected to the CNTL pin of another
device to provide additional controlled turn-on and turn-off sequencing.
Figure 20 shows control of the start-up and shutdown operations of the device, when the device is configured to
respond to a logical AND of both CNTL and the OPERATION command. The device can also be configured to
respond to only the CNTL signal, only the OPERATION command, or to convert power whenever VDD is greater
than the VIN_ON command value setting.
TON_DELAY
TON_RISE
TOFF_DELAY
ON
OFF
VIN
OPERATION[7]
OFF
CNTL
VOUT
(1)
Bit 7 of OPERATION is used to control power conversion. Other bits in this register control output voltage margining.
Figure 20. Turn-On Controlled By Both Operation and Control
8.3.2 Pre-Biased Output Start-Up
The TPS544C20 and TPS544B20 devices prevent current from discharging from the output during start-up, when
a pre-biased output condition exists. No SW pulses occur until the internal soft-start voltage rises above the error
amplifier input voltage (FB pin), if the output is pre-biased. When the soft-start voltage exceeds the error amplifier
input, and SW pulses start, the device limits synchronous rectification time after each SW pulse with a narrow
on-time. The low-side MOSFET on-time slowly increases each switching cycle until it generates 128 pulses. After
128 pulses, the synchronous rectifier runs fully complementary to the high-side MOSFET. This approach
prevents the sinking of current from a pre-biased output, and ensures the output voltage start-up and ramp-toregulation sequences are smooth and monotonic. These devices respond to a pre-biased output over-voltage
condition immediately upon power-up, even during soft-start, while disabled or below the PMBus programmable
undervoltage lockout on-time (UVLOON).
The combination of D-CAP and D-CAP2 mode control and the limited on-time of the low-side MOSFET during
the pre-bias sequence allows these devices to operate at low switching frequencies for the first 128 switching
cycles, after which the device operates using pseudo-constant frequency.
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Feature Description (continued)
8.3.3 Voltage Reference
A 600-mV bandgap cell connects internally to the non-inverting input of the error amplifier. The 0.5% tolerance
on the reference voltage allows for a power supply design that yields very high DC accuracy.
8.3.4 Differential Remote Sense and Output Voltage Setting
The TPS544C20 and TPS544B20 devices implement a differential remote sense amplifier to provide excellent
load regulation by cancelling IR-drop in high current applications. The VOUTS+ and VOUTS– pins should be
kelvin-connected to the output capacitor bank directly at the load, and routed back to the device as a tightly
coupled differential pair. Ensure that these traces are isolated from fast switching signals and high current paths
on the final PCB layout to mitigate differential-mode noise. Optionally, use a small coupling capacitor (330-pF
typical) between the VOUTS+ and VOUTS– pins to improve noise immunity. The output of the differential remote
sense amplifier (DIFFO) sets the output voltage.
A voltage divider from the DIFFO pin to the FB pin sets the nominal output voltage. The output voltage must be
divided down to the nominal reference voltage of 600 mV. The feedback voltage can be adjusted within –30%
and +10% from the nominal 600 mV using PMBus commands, allowing the output voltage to vary by the same
percentage. During the power-up sequence, the feedback reference is 600 mV plus any offset generated by the
MARGIN command or VREF_TRIM command values which were previously stored in EEPROM. The initial
output voltage equals the feedback voltage scaled by the divider ratio. See the PMBus Output Voltage
Adjustment section for further details.
The device enables telemetry by digitizing the voltage at the DIFFO pin, averaging it to reduce measurement
noise, and storing it in the READ_VOUT (8Bh) register.
VOUTS+
DIFFO
+
R1
VOUTSt
FB
RBIAS
COMP
RCOMP
+
CCOMP
VREF
CCOMP_HF
To PWM
Figure 21. Output Voltage Setting
Equation 1 calculates the nominal output voltage. R1 can be arbitrarily selected to be 10-kΩ, with RBIAS being
scaled appropriately.
VOUT = l1 +
8.3.5
R1
p × VFB
RBias
(1)
PMBus Output Voltage Adjustment
The nominal output voltage of the converter can be adjusted by changing the feedback voltage, VFB, using the
VREF_TRIM command. The adjustment range is between –20% and +10% from the nominal output voltage. This
command adjusts the final output voltage of the converter to a high degree of accuracy, without relying on highprecision feedback resistors. The resolution of the adjustment is 7 bits, with a resulting minimum step size of
approximately 2 mV, or 0.4%. The total output voltage adjustable range, including MARGIN and VREF_TRIM is
–30% to + 10%.
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Feature Description (continued)
The TPS544C20 and TPS544B20 devices allow simple output voltage margin testing, by applying a either a
positive or negative offset to the feedback voltage. The STEP_VREF_MARGIN_HIGH and
STEP_VREF_MARGIN_LOW commands control the size of the applied high or low offset respectively. The
OPERATION command toggles the converter between three states:
• Margin none (no output margining). See Equation 2
• Margin high. See Equation 3
• Margin low. See Equation 4
VFB = VREF_TRIM + 0.6 V
VFB = VREF_TRIM + STEP_VREF_MARGIN_HIGH + 0.6 V
VFB = VREF_TRIM + STEP_VREF_MARGIN_LOW + 0.6 V
(2)
(3)
(4)
Figure 22 shows an example of the VREF_TRIM and margin timing.
650 mV
630 mV
600 mV
VFB
600 mV
585 mV
570 mV
Margining Slew Rate:
30 s / 2 mV step
0
VREF_TRIM
+20 mV
0 mV
STEP_VREF_MARGIN_HIGH
+30 mV
STEP_VREF_MARGIN_LOW
-15 mV
OPERATION[5:2]
NONE
LOW
Margin
Low
NONE
HIGH
Margin
High
Margin and
Trim High
-30 mV
Margin
None
Trim
Low
Figure 22. VREF_TRIM and Margin Example
The nominal 600-mV FB pin references the OV fault, UV fault, and PGOOD limits, as defined by
PCT_VOUT_FAULT_PG_LIMIT command, regardless of VREF_TRIM or output margining. These limits remain
fixed percentages of the nominal 600 mV reference, regardless of output margining.
8.3.6 Switching Frequency
A resistor from the RT pin to AGND establishes the switching frequency during the power-up sequence. To
ensure proper detection, select a resistor with 1% tolerance from Table 2.
Table 2. Required RT
Resistors
Copyright © 2014–2016, Texas Instruments Incorporated
NOMINAL
FREQUENCY
(kHz)
1% RESISTOR
VALUE (kΩ)
250
10.0
300
17.8
400
27.4
500
38.3
650
56.2
750
86.6
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Table 2. Required RT
Resistors (continued)
NOMINAL
FREQUENCY
(kHz)
1% RESISTOR
VALUE (kΩ)
850
133
1000
205
The TPS544B20 and TPS544C20 devices detect values that are out-of-range on the RT pin. If the device
detects that RT pin has an out-of-range resistance connected to it, the device selects a frequency setting of
either 250 kHz (if the resistance is less than 5 kΩ) or 1 MHz (if the resistance is greater than 300 kΩ). In this
case, the device also asserts the IVFREQ bit in STATUS_MFR_SPECIFIC. Once VDD is applied, the frequency
latches in memory and RT pin deactives until BP6 falls below VBP6UV. When the device has completed the
Power-on-reset sequence, it latches the frequency in memory and deactivates the RT pin until the BP6 voltage
falls below the BP6 undervoltage threshold setting.
8.3.7 Soft-Start
To control the inrush current needed to charge the output capacitors during the start-up sequence, the
TPS544C20 and TPS544B20 devices implement a soft-start time. When the device is enabled, the feedback
reference voltage, VREF, rises from 0 V to its final value (including output margining or VREF_TRIM value) at a
slew rate defined by the TON_RISE command. The slew rate needed to increase the reference voltage from 0 V
to 600 mV at each given rise time defines the specified rise times. During the soft-start period, the error amplifier
operates as a unity-gain buffer to force the COMP pin voltage to track the internal reference and minimize the
offset between the internal reference and the output voltage. Because D-CAP mode or D-CAP2 mode control
regulates the valley voltage, the average output voltage can exceed the final regulation voltage several millivolts
at the end of the soft-start period See Figure 23.
CNTL
VOUT
VREF
VCOMP
COMP
STATE
Off
EA AMP
TON_DELAY
Off
TON_RISE
NORMAL
Buffer
Integrator
Figure 23. Soft-Start
8.3.8 Linear Regulators BP3 and BP6
Two on-board linear regulators provide suitable power for the internal circuitry of the devices. Externally bypass
pins BP3 and BP6 for the converter to function properly. BP3 requires a minimum of 100 nF of capacitance
connected to AGND. BP6 should be bypassed to GND with a 4.7-µF capacitor.
These devices allow the use of an internal regulator to power other circuits. Ensure that external loads placed on
the regulators do not adversely affect operation of the controller. Avoid loads with heavy transient currents that
can affect the regulator outputs. Transient voltages on these outputs can result in noisy or erratic operation.
Observe the current limits. Shorting the BP3 pin to GND can damage the BP3 regulator. The BP3 regulator input
comes from the BP6 regulator output. The BP6 regulator can supply 120 mA of current and the total current
drawn from both regulators must be less than 120 mA. This total current includes the device operating current
(IVDD) plus the gate-drive current required to drive the power MOSFETs.
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SLUSB69B – MAY 2014 – REVISED JULY 2016
8.3.9 External Bypass (BPEXT)
The BPEXT pin provides an external bypass of the internal BP6 regulator when the application includes an
external bias supply between 4.5 V and 6.5 V. Using an external supply reduces the power dissipation in these
devices and can slightly improve system efficiency. If the input voltage is less than the UVLO threshold, or if the
voltage on the BPEXT pin is lower than the switch-over voltage, VBPEXT(swover), these devices use the internal BP6
regulator. If the voltage on the BPEXT pin exceeds this switch-over voltage, then these devices disable the
internal BP6 regulator and BPEXT outputs to BP6, replacing the internal linear regulator, until the voltage on the
BPEXT pin falls by the BPEXT switch-over hysteresis amount, VHYS(swover). If the application does not require the
BPEXT function, connect the BPEXT pin to GND.
12 V
Level Shift
Logic
VIN OK
BPEXT OK
VDD
6.5 V
6.5 V
4.2 V
VDD
5V
BP6_INT
4.5 V
4.7 V
BP6
BPEXT
6.5 V
BPEXT
5V
VBPEXT(swover)
+
BP6
6.5 V
4.5V
UDG-12251
Figure 24. BP External
Figure 25. BP Crossover Diagram
NOTE
It is not recommended to transition BPEXT across the switch-over voltage, VBPEXT(swover),
during regulation. The transition causes an overshoot or undershoot response on the
output voltage. Instead, the BPEXT voltage should be either fully established to its final
level, or pulled low to GND prior to entering regulation.
8.3.10 Current Monitoring and Low-Side MOSFET Overcurrent Protection
The TPS544C20 and TPS544B20 devices sense average output current using an internal sensefet. A sensefet
conducts a scaled-down version of the power-stage current. Sampling this current in the middle of the low-side
drive signal determines the average output current. This architecture achieves excellent current monitoring and
better overcurrent threshold accuracy than inductor DCR current sensing with minimal temperature variation and
no dependence on power loss in a higher DCR inductor. This enables the use of lower DCR inductors to improve
efficiency. Use the IOUT_CAL_OFFSET command to improve current sensing and overcurrent accuracy by
removing board layout-related systematic errors post assembly. The devices continually digitize the sensed
output current, and average it to reduce measurement noise. The devices then store the current value in the
read-only READ_IOUT register, enabling output current telemetry.
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SW
Seven
Consecutive
Cycle
Counter
LSOC
Current Sense
Amplifier
OCF/OCW
Comparators
Hiccup/
Latch-off
LFET
+
Sensefet
Average
Current
Sensing
IOUT_OC_
FAULT_RESPONSE
OCF
OCW
OCF/OCW
Thresholds
IOUT_CAL_
OFFSET
READ_IOUT
STATUS_IOUT
PMBus Engine
SMBALERT
GND
AGND
AGNDSNS
SenseFET
Figure 26. Sensefet Average Current Sensing and Low-Side Overcurrent Protection
The TPS544C20 and TPS544B20 devices also implement low-side MOSFET overcurrent protection with
programmable fault and warning thresholds. The IOUT_OC_FAULT_LIMIT and IOUT_OC_WARN_LIMIT
commands set the low-side overcurrent thresholds.
As shown in Figure 26, if an overcurrent event is detected in a given switching cycle, the device increments an
overcurrent counter. When the device detects seven consecutive low-side overcurrent events, the converter
responds, flagging the appropriate status registers, triggering SMBALERT if it is not masked, and entering either
continuous restart hiccup, or latch-off according to the IOUT_OC_FAULT_RESPONSE command. In continuous
restart hiccup mode, the devices implement a time-out function that occurs after seven soft-start cycles; followed
by a normal soft-start attempt. When the overcurrent fault clears, normal operation resumes, otherwise, the
device detects overcurrent and the process repeats.
8.3.11 High-Side MOSFET Short-Circuit Protection
The TPS544B20 and devices also implement a fixed high-side MOSFET overcurrent (HSOC) protection to limit
peak current, and prevent inductor saturation in the event of a short circuit. The devices detect an overcurrent
event by sensing the voltage drop across the high-side MOSFET when it is on. If the peak current reaches the
HSOC level on any given cycle, the cycle terminates to prevent the current from increasing any further. For
accurate high-side MOSFET overcurrent protection, the VIN and VDD pins must be at the same voltage; split rail
operation is not supported.
8.3.12 Over-Temperature Protection
An internal temperature sensor protects the devices from thermal runaway. The internal thermal shutdown
threshold, TSD, is fixed at 145°C typical. When the devices sense a temperature above TSD, an over-temperature
fault internal (OTFI) is flagged, and power conversion stops until the sensed junction temperature falls by the
thermal shutdown hysteresis amount, THYST, (25°C typical). Additionally, the OTFI bit in
STATUS_MFR_SPECIFIC setting indicates when the devices detect an internal over-temperature event.
The TPS544C20 and TPS544B20 devices also provide programmable external over-temperature fault and
warning thresholds using measurements from an external temperature sensor connected on the TSNS pin. The
temperature sensor circuit applies two bias currents to an external NPN transistor, and measures ΔVBE to infer
the junction temperature of the sensor. The TPS544C20 and TPS544B20 devices are designed to use a
standard 2N3904 NPN transistor as a temperature sensor. Other sensors may be used, but the devices assume
an ideality factor, n, of 1.008 for use with the 2N3904. The devices then digitize the result and compare it to the
user-configured over-temperature fault and warning thresholds. When an external over-temperature fault (OTF) is
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detected, power conversion stops until the sensed temperature falls by 20°C. The READ_TEMPERATURE_2
(8Eh) register is continually updated with the digitized temperature measurement, enabling temperature
telemetry. The OT_FAULT_LIMIT (4Fh) and OT_WARN_LIMIT (51h) commands set the PMBus overtemperature fault and warning thresholds. When an overtemperature event is detected, the device sets the
appropriate flags in STATUS_TEMPERATURE (7Dh) and triggers SMBALERT if it is not masked.
TI recommends routing a differential pair of AGND and TSNS from the TPS544B20 and TPS544C20 to the
collector-base and emitter terminals of the 2N3904. Include a 330-pF capacitor between the TSNS and AGND
pair traces to reduce temperature measurement noise and associated error. Implement the option to disable
external temperature sensing by terminating TSNS to AGNS with a 0-Ω resistor. This termination forces the
external temperature measurement to –40°C, and prevents external over-temperature faults tripping. The internal
temperature sensor, and internal over-temperature fault remain enabled regardless of the TSNS pin termination.
OT Fault Internal
Thermal
Shutdown
READ_
TEMPERATURE_2
Internal Temp
Sensor
+
145°C
OT_FAULT_LIMIT
OT
Fault
OT_WARN_LIMIT
STATUS_
TEMPERATURE
STATUS_
MFR_SPECIFIC
PMBus Engine
Sampling and
Temperature
Conversion
TSNS
¨9BE
Measurement
QT
CT
SMBALERT
Figure 27. Over-Temperature Protection
8.3.13 Input Undervoltage Lockout (UVLO)
The TPS544C20 and TPS544B20 devices provide flexible user adjustment of the undervoltage lockout threshold
and hysteresis. Two PMBus commands, VIN_ON (35h) and VIN_OFF (36h) allow the user to set these input
voltage turn-on and turn-off thresholds independently, with a minimum of 4-V turn-off to a maximum 16-V turn-on.
See the command descriptions for more details.
8.3.14 Output Overvoltage and Undervoltage Protection
The TPS544C20 and TPS544B20 devices include both output overvoltage protection (OVP) and output
undervoltage (UVP) protection. The devices compare the FB pin voltage to internal selectable pre-set voltages,
as defined by the PCT_VOUT_FAULT_PG_LIMIT (MFR_SPECIFIC_07) (D7h) command. As the output voltage
rises or falls from the nominal voltage, the FB voltage tracks a direct divider ratio of the output voltage. If the FB
voltage rises above the OVP threshold, the device terminates normal switching, declares an OV fault and turns
on the low-side MOSFET to discharge the output capacitor and prevent further increases in the output voltage. If
the FB voltage falls below the OVP threshold, the low-side FET turns off and normal switching resumes.
If the FB voltage falls below the undervoltage protection level after soft-start sequence has completed, the device
terminates normal switching and forces both the high-side and low-side MOSFETs off, and awaits an external
reset or begins a hiccup time-out delay prior to restart, depending on the value of the
IOUT_OC_FAULT_RESPONSE (47h) command. The output undervoltage response is shared with the overcurrent fault response.
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8.3.15 Fault Protection Responses
Table 3 summarizes the various fault protections and associated responses.
Table 3. Fault Protection Summary
FAULT
VDD UV
UV
OV
HSOC
LSOC
OT
TSD (OTFI)
1) High-side short
2) Output short to
GND
1) Low-side short
2) Output
overcurrent
High board
temperature
High device
temperature due to
ambient or power
dissipation
FAULT
CAUSES
1) Input
undervoltage
2) Loss of input
1) Output
overcurrent
2) Low-side short
3) FB short high
1) Pre-biased
output
2) High-side short
3) FB short to
GND
MONITORING
SIGNAL
Voltage on VDD
pin
Voltage on FB pin
Voltage on FB pin
Voltage drop
across high-side
MOSFET
Sensed current in
low-side MOSFET
Voltage on TSNS
pin
Temperature on
internal sensor
Tripping
increments OC
counter; latch off
when counter
overflows
Latch off
Latch off
HIGH-SIDE
MOSFET
Latch off
Latch off
Latch off
Turns off on cycleby-cycle basis,
incrementing OC
counter; latch off
when counter
overflows
LOW-SIDE
MOSFET
Latch off
Latch off
Latch on until
VOUT returns to
within PG window
Latch off when
counter overflows
Latch off when
counter overflows
Latch off
Latch off
HICCUP
No
Yes (1)
No (2)
Yes (1)
Yes (1)
Hiccup after
temperature
below reset
threshold
Hiccup after
temperature below
reset threshold
Enabled
Enabled
Enabled
Enabled
DURING
SOFT-START
Enabled
Disabled
Enabled
Enabled
Enabled during or
after SS once
LDRV pulse width
first exceeds CSA
sampling period
AFTER SOFTSTART
Enabled
Enabled
Enabled
Enabled
Enabled
(1)
(2)
If the device is configured to restart continuously, triggering the fault causes a hiccup.
Hiccup is not triggered if the device can bring the output voltage back to regulation. Hiccup remains enabled if the output reaches the
UV limit following an OV event
8.3.16
PMBus General Description
Timing and electrical characteristics of the PMBus specification can be found in the PMB Power Management
Protocol Specification, Part 1, revision 1.1 available at http://pmbus.org. The TPS544B20 and
TPS544C20devices support both the 100-kHz and 400-kHz bus timing requirements. The TPS544B20 and
TPS544C20 devices do not implement clock stretching when communicating with the master device.
Communication over the PMBus interface can support Packet Error Checking (PEC) if desired. If the PMbus host
supplies clock (CLK pin) pulses for the PEC byte, PEC is used. If the CLK pulses are not present before a
STOP, the PEC is not used.
These devices support a subset of the commands in the PMBus 1.1 Power Management Protocol Specification.
See the Supported PMBus Commands section for more information.
The devices also support the SMBALERT response protocol. The SMBALERT response protocol is a mechanism
by which a slave device (such as the TPS544C20 device or the TPS544B20 device) can alert the master device
that it is available for communication. The master device processes this event and simultaneously accesses all
slave devices on the bus (that support the protocol) through the alert response address (ARA). Only the slave
device that caused the alert acknowledges this request. The host device performs a modified receive byte
operation to ascertain the slave devices address. At this point, the master device can use the PMBus status
commands to query the slave device that caused the alert. By default, these devices implement the auto alert
response, a manufacturer specific improvement to the SMBALERT response protocol, intended to mitigate the
issue of bus hogging. See the Auto ARA (Alert Response Address) Response section for more information. For
more information on the SMBus alert response protocol, see the System Management Bus (SMBus)
specification.
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The devices contain non-volatile memory that stores configuration settings and scale factors. However, the
devices do not save the settings programmed into this non-volatile memory. The STORE_USER_ALL (15h)
command must be used to commit the current settings to non-volatile memory as device defaults. Settings
available for storage in NVM are noted in their detailed descriptions.
8.3.17
PMBus Address
The PMBus specification requires that each device connected to the PMBus have a unique address on the bus.
The TPS544B20 and TPS544C20 devices each have 64 possible addresses (0 through 63 in decimal) that can
be assigned by connecting resistors from the ADDR0 and ADDR1 pins to AGND. The address is set in the form
of two octal (0-7) digits, one digit for each pin. ADDR1 is the high order digit and ADDR0 is the low-order digit.
These address selection resistors must be 1% tolerance or better. Using resistors other than the recommended
values can result in devices responding to adjacent addresses.
The E96 series resistors recommended for each digit value are shown in Table 4.
Table 4. Required Address Resistors
DIGIT
1% RESISTOR VALUE (kΩ)
0
10.0
1
17.8
2
27.4
3
38.3
4
56.2
5
86.6
6
133
7
205
The devices detect values that are out-of-range on the ADDR0 and ADDR1 pins. If the device detects that either
pin has an out-of-range resistance connected to it, the device continues to respond to PMBus commands, but
does so at address 127, which is outside of the possible programmed addresses. It is possible but not
recommended to use the device in this condition, especially if other devices are present on the bus or if another
device could possibly occupy the 127 address.
The device reserves certain addresses in the I2C address space for special functions. The PMBus protocol
allows the address of the device to respond to these addresses. The user is responsible for knowing which of
these reserved addresses are in use in a system and for setting the address of the device accordingly so as not
to interfere with other system operations.
NOTE
These devices can be set to respond to the reserved GLOBAL CALL address or Address
0. Do not set a device to this address unless the design allows no other devices to
respond to this address and that the overall bus is not affected by the presence of such an
address.
8.3.18
PMBus Connections
The TPS544B20 and TPS544C20 devices support both the 100-kHz and 400-kHz bus speeds. Connection for
the PMBus interface should follow the specification given in section 3.1.3 High-Power DC in the SMBus
specification V2.0 for the 400-kHz bus speed or the 3.1.2 Low Power DC section. The complete SMBus
specification is available from the SMBus web site, smbus.org.
8.3.19 Auto ARA (Alert Response Address) Response
By default, the TPS544B20 and TPS544C20 devices implement the auto alert response, a manufacturer specific
improvement to the standard SMBALERT response protocol defined in the SMBus specification. The auto alert
response is designed to prevent SMBALERT monopolizing in the case of a persistent fault condition on the bus.
The user can choose to disable the auto ARA response, and use the standard SMBALERT response as defined
in the SMBus specification, by using bit 8 of the MASK_SMBALERT (MFR_SPECIFIC_23) (E7h) command.
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In the case of a fault condition, the slave device experiencing the fault pulls down the shared SMBALERT line, to
alert the host that a fault condition has occurred. To establish which slave device has experienced the fault, the
host issues a modified receive byte operation to the alert response address (ARA), to which only the slave
device pulling down on SMBALERT should respond. The SMBus protocol provides a method for address
arbitration in the case that multiple slave devices on the same bus are experiencing fault conditions. Once the
host has established the address of the offending device, it must take any necessary action to release the
SMBALERT line. For more information on the standard SMBus alert response protocol, see the System
Management Bus (SMBus) specification.
In the case of a non-persistent fault (for example, a single-time event, such as an invalid command or data byte),
the host can ascertain the address of the slave device experiencing a fault using the standard ARA response,
and simply issue CLEAR_FAULTS (03h) to release the SMBALERT line, and resume normal operation.
However, in the case of a persistent fault (i.e. one which remains active for some time, such as a short-circuit, or
thermal shutdown), once the device issues a CLEAR_FAULTS (03h) command, the fault immediately re-triggers,
and SMBALERT continues to be pulled low. In this case, the device holds low the SMBALERT line until the host
masks the SMBALERT line using MASK_SMBALERT (MFR_SPECIFIC_23) (E7h) and then issues the
CLEAR_FAULTS (03h) command. Because the SMBALERT line remains low, the host cannot be alerted to other
fault conditions on the bus until it clears SMBALERT. This situation is known as bus hogging. Figure 28 and
Figure 29 illustrate an example of this response.
.
SMBALERT is not released until CLEAR_FAULTS
is issued by the host
SMBALERT
STATUS_CML
No Faults
DATA
Invalid Command
No Faults
PAGE
ARA
Slave Address
CLEAR_FAULT
HOST
HOST
SLAVE
HOST
Figure 28. Example Standard ARA Response to Non-Persistent Fault
.
SMBALERT is low until host masks fault, and issues CLEAR_FAULTS
if the fault condition persists
SMBALERT
STATUS_IOUT
No Faults
OC FAULT
DATA
ARA
Slave Address
MASK_SMBALERT
CLEAR_FAULTS
HOST
SLAVE
HOST
HOST
Short
Circuit
Figure 29. Example Standard ARA Response to a Persistent Fault
.
In order to mitigate the problem of bus hogging, these devices implement the Auto ARA response. When Auto
ARA is enabled, the devices release SMBALERT automatically after successfully responding to access from the
host at the alert response address. In this case, even when a device is experiencing a persistent fault, it does not
hold the SMBALERT line low following successful notification of the host, and the host can be alerted to other
faults on the bus in the normal manner. Examples of the auto ARA response are illustrated in Figure 30 and
Figure 31.
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SMBALERT is
released when slave
successfully responds to ARA
SMBALERT
STATUS_CML
DATA
No Faults
Invalid Command
No Faults
PAGE
ARA
Slave Address
CLEAR_FAULT
HOST
HOST
SLAVE
HOST
Figure 30. Example Auto ARA Response to Non-Persistent Fault
SMBALERT is
released when slave
successfully responds to ARA
SMBALERT
STATUS_IOUT
No Faults
Host must mask SMBALERT or it will re-assert when
CLEAR_FAULTS is issued, if the fault condition persists
OC FAULT
DATA
ARA
Slave Address
MASK_SMBALERT
CLEAR_FAULTS
HOST
SLAVE
HOST
HOST
Short
Circuit
Figure 31. Example Auto ARA Response to Persistent Fault
8.4 Device Functional Modes
8.4.1 Continuous Conduction Mode
The TPS544B20 and TPS544C20 devices operate in continuous conduction mode (CCM) at a fixed frequency,
regardless of the output current. For the first 128 switching cycles, the low-side MOSFET on-time is slowly
increased to prevent excessive current sinking when the device starts up with a pre-biased output. Following the
first clock 128 cycles, the low-side MOSFET and the high-side MOSFET on-times are fully complementary.
8.4.2 Operation with Internal BP6 Regulator
The TPS544B20 and TPS544C20 devices include an internal linear regulator to supply bias for internal logic and
the power MOSFET drivers. The BP6 regulator steps down the VDD voltage to approximately 6.5 V when VVDD is
above 6.5 V, or operates with a maximum of 100-mV dropout when VVDD is less than 6.5 V. In this case, the
BPEXT pin should be connected to GND.
8.4.3 Operation with BP External
The TPS544B20 and TPS544C20 devices can operate with an externally supplied voltage applied on the BPEXT
pin to bypass the BP6 regulator, which powers the MOSFET drivers. Using BP External reduces the power
dissipation inside the device, and leads to a small gain in overall efficiency. In this case, the BP6 regulator should
be bypassed as normal, but the BPEXT pin should also have a minimum of 2.2-µF bypass capacitance relative
to GND. See External Bypass (BPEXT) for more information.
8.4.4 Operation with CNTL Signal Control
According to the value in the ON_OFF_CONFIG register, The TPS544B20 and TPS544C20 devices can be
commanded to use the CNTL pin to enable or disable regulation, regardless of the state of the OPERATION
command. The minimum input high threshold for the CNTL signal is 2.1 V, and the maximum input low threshold
for the CNTL signal is 0.8 V. The CNTL pin can be configured as either active high or active low (inverted) logic.
8.4.5 Operation with OPERATION Control
According to the value in the ON_OFF_CONFIG register, these devices can be commanded to use the
OPERATION command to enable or disable regulation, regardless of the state of the CNTL signal.
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Device Functional Modes (continued)
8.4.6 Operation with CNTL and OPERATION Control
According to the value in the ON_OFF_CONFIG register, these devices can be commanded to require both a
signal on the CNTL pin, and the OPERATION command to enable or disable regulation.
8.4.7 Operation with Output Margining
The OPERATION command can be used to toggle the device between three states:
• Margin none
• Margin low
• Margin high
In the margin none state, the feedback reference, VREF, is equal to the nominal 600-mV reference, plus any
offset defined by the VREF_TRIM command. In the margin low state, a negative offset defined by the
STEP_VREF_MARGIN_LOW command is applied to the feedback reference, moving the converter output
voltage down by an equivalent percentage. In the margin high state, a positive offset defined by the
STEP_VREF_MARGIN_HIGH command is applied to the feedback reference, moving the converter output
voltage up by an equivalent percentage. See the PMBus Output Voltage Adjustment section for more
information.
8.5 Programming
8.5.1 Supported PMBus Commands
The commands listed in the Table 5 section are implemented as described to conform to the PMBus 1.1
specification. It also shows default behavior and register values.
Table 5. Supported PMBus Commands and Default Values
CMD
CODE
28
PMBus 1.1
COMMAND NAME
PMBus COMMAND DESCRIPTION
DEFAULT BEHAVIOR
DEFAULT
REGISTER
VALUE
01h
OPERATION
Can be configured via
ON_OFF_CONFIG to be used to turn the Margin None.
output on and off with or without input
OPERATION is not used
from the CTRL pin. Also used to turn on to enable regulation
and off margin high and low.
02h
ON_OFF_CONFIG
Configures the combination of CNTL pin
input and OPERATION command for
turning output on and off.
CNTL only. Active High
16h
03h
CLEAR_FAULTS
Clears all fault status registers to 0x00
and releases SMBALERT.
Write-only
n/a
10h
WRITE_PROTECT
Used to control writing to the device.
Allow writes to all
registers
00h
15h
STORE_USER_ALL
Stores all current storable register
settings into EEPROM as new defaults.
Write-only
n/a
16h
RESTORE_USER_ALL
Restores all storable register settings
from EEPROM.
Write-only
n/a
19h
CAPABILITY
Provides a way for a host system to
determine key PMBus capabilities of the
device.
Read only. PMBus v1.1,
400 kHz, PEC enabled
B0h
20h
VOUT_MODE
Read-only output mode indicator.
Linear, exponent = –9
17h
35h
VIN_ON
Sets value of input voltage at which the
device should start power conversion.
4.25 V
F011h
36h
VIN_OFF
Sets value of input voltage at which the
device should stop power conversion.
4.0V
F010h
39h
IOUT_CAL_OFFSET
Can be set to null out offsets in the
current sensing circuit.
0.0000 A
E000h
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Programming (continued)
Table 5. Supported PMBus Commands and Default Values (continued)
CMD
CODE
PMBus 1.1
COMMAND NAME
PMBus COMMAND DESCRIPTION
DEFAULT BEHAVIOR
DEFAULT
REGISTER
VALUE
F84Eh
(TPS544C20)
F834h
(TPS544B20)
46h
IOUT_OC_FAULT_LIMIT
Sets the value of the output current that
causes an overcurrent fault condition.
39 A (TPS544C20)
26 A (TPS544B20)
47h
IOUT_OC_FAULT_RESPONSE
Sets response to output overcurrent and
undervoltage faults to latch-off or hiccup
mode.
Shutdown and latch-off
4Ah
IOUT_OC_WARN_LIMIT
30 A (TPS544C20)
Sets the value of the output current that
causes an overcurrent warning condition. 20 A (TPS544B20)
4Fh
OT_FAULT_LIMIT
Sets the value of the sensed temperature
that causes an overtemperature fault
150 °C
condition.
0096h
51h
OT_WARN_LIMIT
Sets the value of the sensed temperature
that causes an overtemperature warning 125 °C
condition.
007Dh
61h
TON_RISE
Sets the time from when the output starts
to rise until the voltage has entered the
2.7 ms
regulation band.
E02Bh
78h
STATUS_BYTE
Returns one byte summarizing the most
critical faults.
Read only
Current status
79h
STATUS_WORD
Returns two bytes summarizing fault and
warning conditions.
Read only
Current status
7Ah
STATUS_VOUT
Returns one byte detailing if an output
fault or warning has occurred
Read only
Current status
7Bh
STATUS_IOUT
Retyrns one byte detailing if an
Read only
overcurrent fault or warning has occurred
Current status
7Dh
STATUS_TEMPERATURE
Returns one byte detailing if a sensed
temperature fault or warning has
occurred.
Read only
Current status
7Eh
STATUS_CML
Returns one byte containing PMBus
serial communication faults.
Read only
Current status
80h
STATUS_MFR_SPECIFIC
Returns one byte detailing if internal
overtemperature or frequency detection
fault has occurred.
Read only
Current status
8Bh
READ_VOUT
Returns the output voltage in volts.
Read only
Current status
8Ch
READ_IOUT
Returns the channel current in amps.
Read only
Current status
8Eh
READ_TEMPERATURE_2
Returns the sensed temperature in
degrees Celsius.
Read only
Current status
98h
PMBUS_REVISION
Returns PMBus revision to which the
device is compliant.
Read only
11h
D0h
MFR_SPECIFIC_00
Two bytes dedicated as a user scratch
pad.
00h
00h
D4h
VREF_TRIM
(MFR_SPECIFIC_04)
Used to apply a fixed offset voltage to
the reference voltage.
0.000 V
0000h
D5h
STEP_VREF_MARGIN_HIGH
(MFR_SPECIFIC_05)
Sets the increase to the value of the
reference voltage for shifting the
reference higher.
60 mV
001Eh
D6h
STEP_VREF_MARGIN_LOW
(MFR_SPECIFIC_06)
Sets the decrease to the value of the
reference voltage for shifting the
reference lower.
–60 mV
FFE2h
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07h
F8C3h
(TPS544C20)
F828h
(TPS544B20)
F814h ()
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Programming (continued)
Table 5. Supported PMBus Commands and Default Values (continued)
CMD
CODE
PMBus 1.1
COMMAND NAME
PMBus COMMAND DESCRIPTION
DEFAULT BEHAVIOR
DEFAULT
REGISTER
VALUE
D7h
PCT_VOUT_FAULT_PG_LIMIT
(MFR_SPECIFIC_07)
Sets the PGOOD and output
undervoltage and overvoltage limits as a
percent of nominal.
UV Fault: –16.8%
PGOOD (falling): –12.5%
PGOOD (rising): 12.5%
OV Fault: 16.8 %
00h
D8h
SEQUENCE_TON_TOFF_DELAY
(MFR_SPECIFIC_08)
Sets the delays for turning the output on
and off as a ratio of TON_RISE.
TON_DELAY: 0ms
TOFF_DELAY: 0ms
00h
E5h
OPTIONS
(MFR_SPECIFIC_21)
Sets miscellaneous user selectable
options.
ADC is enabled.
Telemetry is enabled.
0004h
E7h
MASK_SMBALERT
(MFR_SPECIFIC_23)
Used to mask which faults or warnings
assert SMBALERT, and enable Auto
ARA.
Auto ARA is enabled.
No SMBALERT sources
are masked
0100h
FCh
DEVICE_CODE
(MFR_SPECIFIC_44)
Returns a 12-bit unique identifier code
for the device and a 4-bit revision code.
0153h (TPS544C20)
0143h (TPS544B20)
0153h
(TPS544C20)
0143h
(TPS544B20)
8.6 Register Maps
This family of devices supports the following commands from the PMBus 1.1 specification.
8.6.1 OPERATION (01h)
The OPERATION command turns the device output on or off in conjunction with input from the CNTL signal. It
also sets the output voltage to the upper or lower margin voltages. The unit stays in the commanded operating
mode until a subsequent OPERATION command or a change in the state of the CNTL pin instructs the device to
change to another mode.
COMMAND
OPERATION
Format
Bit Position
Unsigned binary
7
6
5
4
3
2
1
Access
r/w
r
r/w
r/w
r/w
r/w
r
r
Function
ON
X
X
X
0
0
X
X
Default Value
Margin
0
0
0
0
0
8.6.1.1 On
This bit is an enable command to the converter.
• 0: output switching is disabled. Both drivers placed in an off or low state.
• 1: output switching is enabled if the input voltage is above undervoltage lockout, OPERATION is configured
as a gating signal in ON_OFF_CONFIG, and no fault conditions exist.
8.6.1.2 Margin
If Margin Low is enabled, the feedback voltage is offset with the value from the STEP_VREF_MARGIN_LOW
command. If Margin High is enabled, the feedback voltage is offset with the value from the
STEP_VREF_MARGIN_HIGH command. (See PMBus specification for more information)
• 00XX: Margin Off
• 0101: Margin Low (Ignore on Fault)
• 0110: Margin Low (Act on Fault)
• 1001: Margin High (Ignore on Fault)
• 1010: Margin High (Act on Fault)
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NOTE
Because the PGOOD, OV and UV thresholds remain referenced to the nominal 600-mV
feedback reference, it is possible to use the Margin High, Margin Low or VREF_TRIM
options to set the reference voltage into a PGOOD or Undervoltage Fault based on the
ranges provided. When using the Ignore Fault option of the OPERATION command, these
faults are masked when entering Margin High or Margin Low, but they PGOOD or Under
Voltage Fault can be triggered when returning to Margin Off.
8.6.2 ON_OFF_CONFIG (02h)
The ON_OFF_CONFIG command configures the combination of CNTL pin input and serial bus commands
needed to turn the unit on and off. The contents of this register can be stored to non-volatile memory using the
STORE_USER_ALL command.
COMMAND
ON_OFF_CONFIG
Format
Unsigned binary
Bit Position
7
6
5
4
3
2
1
Access
r
r
r
r/w
r/w
r/w
r/w
0
r
Function
X
X
X
pu
cmd
cpr
pol
cpa
Default Value
X
X
X
1
0
1
1
0
8.6.2.1 pu
The pu bit sets the default to either operate any time power is present or for power conversion to be controlled by
CNTL pin and PMBus OPERATION command. This bit is used in conjunction with the 'cp', 'cmd', and 'on' bits to
determine start up.
BIT VALUE
ACTION
0
Device powers up any time power is present regardless of state of the CNTL pin.
1
Device does not power up until commanded by the CNTL pin and OPERATION
command as programmed in bits [2:0] of the ON_OFF_CONFIG register.
8.6.2.2 cmd
The cmd bit controls how the device responds to the OPERATION command.
BIT VALUE
ACTION
0
Device ignores the “on” bit in the OPERATION command.
1
Device responds to the “on” bit in the OPERATION command.
8.6.2.3 cpr
The cpr bit sets the CNTL pin response. This bit is used in conjunction with the 'cmd', 'pu', and 'on' bits to
determine start up.
BIT VALUE
ACTION
0
Device ignores the CNTL pin. Power conversion is controlled only by the OPERATION
command.
1
Device requires the CNTL pin to be asserted to start the unit.
8.6.2.4 pol
The pol bit controls the polarity of the CNTL pin. For a change to become effective, the contents of the
ON_OFF_CONFIG register must be stored to non-volatile memory using the STORE_USER_ALL command and
the device power cycled. Simply writing a new value to this bit does not change the polarity of the CNTL pin.
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BIT VALUE
ACTION
0
CNTL pin is active low.
1
CNTL pin is active high.
8.6.2.5 cpa
The cpa bit sets the CNTL pin action when turning the controller off. This bit is read internally and cannot be
modified by the user.
BIT VALUE
0
ACTION
Turn off the output using the programmed delay.
8.6.3 CLEAR_FAULTS (03h)
The CLEAR_FAULTS command is used to clear any fault bits that have been set. This command clears all bits
in all status registers simultaneously. At the same time, the device negates (clears, releases) its SMBALERT
output if the device is asserting SMBALERT. The CLEAR_FAULTS command does not cause a unit that has
latched off for a fault condition to restart. If the fault is still present when the bit is cleared, the fault bit is
immediately reset and the host notified by the usual means.
8.6.4 WRITE_PROTECT (10h)
The WRITE_PROTECT command is used to control writing to the PMBus device. The intent of this command is
to provide protection against accidental changes. This command is not intended to provide protection against
deliberate or malicious changes to the device configuration or operation. All supported command parameters
may have their parameters read, regardless of the WRITE_PROTECT settings. Write protection also prevents
protected registers from being updated in the event of a RESTORE_USER_ALL. The contents of this register
can be stored to non-volatile memory using the STORE_USER_ALL command.
COMMAND
WRITE_PROTECT
Format
Unsigned binary
Bit Position
7
6
5
4
3
2
1
0
Access
r/w
r/w
r/w
X
X
X
X
X
Function
bit7
bit6
bit5
X
X
X
X
X
0
0
0
X
X
X
X
X
Default Value
8.6.4.1 bit5
BIT VALUE
ACTION
0
Enable all writes as permitted in bit6 or bit7
1
Disable all writes except the WRITE_PROTECT, OPERATION and ON_OFF_CONFIG.
(bit6 and bit7 must be 0 to be valid data)
8.6.4.2 bit6
BIT VALUE
ACTION
0
Enable all writes as permitted in bit5 or bit7
1
Disable all writes except for the WRITE_PROTECT, and OPERATION commands. (bit5
and bit7 must be 0 to be valid data)
8.6.4.3 bit7
BIT VALUE
32
ACTION
0
Enable all writes as permitted in bit5 or bit6
1
Disable all writes except for the WRITE_PROTECT command. (bit5 and bit6 must be 0
to be valid data)
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In any case, only one of the three bits may be set at any one time. Attempting to set more than one bit results in
an alert being generated and the cml bit is STATUS_WORD being set. An invalid setting of the
WRITE_PROTECT command results in no write protection.
8.6.5 STORE_USER_ALL (15h)
The STORE_USER_ALL command stores all of the current storable register settings in the EEPROM memory as
the new defaults on power up.
It is permissible to use this command while the device is switching. Note however that the device continues to
switch but ignores all fault conditions until the internal store process has completed.
EEPROM programming faults cause the device to NACK and set the 'cml' bit in the STATUS_BYTE and the 'oth'
bit in the STATUS_CML registers.
The following registers can be stored to EEPROM memory using STORE_USER_ALL:
• ON_OFF_CONFIG
• WRITE_PROTECT
• VIN_ON
• VIN_OFF
• IOUT_CAL_OFFSET
• IOUT_OC_FAULT_LIMIT
• IOUT_OC_WARN_LIMIT
• IOUT_OC_FAULT_RESPONSE
• OT_FAULT_LIMIT
• OT_WARN_LIMIT
• TON_RISE
• MFR_SPECIFIC_00
• VREF_TRIM
• STEP_VREF_MARGIN_HIGH
• STEP_VREF_MARGIN_LOW
• PCT_VOUT_FAULT_PG_LIMIT
• SEQUENCE_TON_TOFF_DELAY
• OPTIONS
• MASK_SMBALERT
8.6.6 RESTORE_USER_ALL (16h)
The RESTORE_USER_ALL command restores all of the storable register settings from EEPROM memory.
Do not use this command while the device is actively switching, this causes the device to stop switching and the
output voltage to fall during the restore event. Depending on loading conditions, the output voltage could reach
an undervoltage level and trigger an undervoltage fault response if programmed to do so. The command can be
used while the device is switching, but it is not recommended as it results in a restart that could disrupt power
sequencing requirements in more complex systems. It is strongly recommended that the device be stopped
before issuing this command.
NOTE
A VIN_UV fault may be triggered when RESTORE_USER_ALL command is set. The
firmware workaround is accomplished by verifying that, upon completion of a
RESTORE_USER_ALL command, the sole source asserting SMBALERT is the VIN_UV
bit in STATUS_BYTE. If so, issue a CLEAR_FAULTS command. Any other source
asserting
SMBALERT
under
these
circumstances
(i.e.
completion
of
RESTORE_USER_ALL) would indicate an actual fault condition.
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8.6.7 CAPABILITY (19h)
The CAPABILITY command provides a way for a host system to determine some key capabilities of this PMBus
device.
COMMAND
CAPABILITY
Format
Unsigned binary
Bit Position
7
6
5
4
3
2
1
0
Access
r
r
r
r
r
r
r
r
0
0
0
0
Function
PEC
Default Value
1
SPD
0
ALRT
1
1
Reserved
The default values indicate that the device supports Packet Error Checking (PEC), a maximum bus speed of 400
kHz (SPD) and the SMBus Alert Response Protocol using SMBALERT.
8.6.8 VOUT_MODE (20h)
The PMBus specification dictates that the data word for the VOUT_MODE command is one byte that consists of
a 3-bit mode and 5-bit exponent parameter, as shown below. The 3-bit mode sets whether the device uses the
Linear or Direct modes for output voltage related commands. The 5-bit parameter sets the exponent value for the
linear data mode. The mode and exponent parameters are fixed and do not permit the user to change the
values.
COMMAND
VOUT_MODE
Bit Position
7
6
5
4
3
2
1
0
Access
r
r
r
r
r
r
r
r
0
1
0
1
1
Function
Mode
Default Value
0
0
Exponent
1
8.6.8.1 Mode:
Value fixed at 000, linear mode.
8.6.8.2 Exponent
Value fixed at 10111, Exponent for Linear mode values is –9.
8.6.9 VIN_ON (35h)
The VIN_ON command sets the value of the input voltage at which the unit should start operation assuming all
other required startup conditions are met. Values are mapped to the nearest supported increment. Values
outside the supported range are treated as invalid data and cause the device set the CML bit in the
STATUS_BYTE and the invalid data (ivd) bit in the STATUS_CML registers. The value of VIN_ON remains
unchanged on an out-of-range write attempt. The contents of this register can be stored to non-volatile memory
using the STORE_USER_ALL command.
The supported VIN_ON values are shown in Table 6:
Table 6. Supported VIN_ON Values
VIN_ON Values (V)
4.25 (default)
4.5
4.75
5
5.25
5.5
5.75
6
6.25
6.5
6.75
7
7.25
7.5
8
8.25
8.5
8.75
9
9.25
9.5
10
10.5
11
11.5
12
12.5
13
14
15
16
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VIN_ON must be set higher than VIN_OFF. Attempting to write either VIN_ON lower than VIN_OFF or VIN_OFF
higher than VIN_ON results in the new value being rejected, SMBALERT being asserted along with the CML bit
in STATUS_BYTE and the invalid data bit in STATUS_CML.
The data word that accompanies this command is divided into a fixed 5-bit exponent and an 11-bit mantissa. The
four most significant bits of the mantissa are fixed, while the lower 7 bits may be altered.
COMMAND
VIN_ON
Format
Linear, two's complement binary
Bit Position
7
6
5
4
3
2
1
0
7
6
5
4
3
2
1
0
Access
r
r
r
r
r
r
r
r
r
r/w
r/w
r/w
r/w
r/w
r/w
r/w
1
0
0
0
1
Function
Exponent
Default Value
1
1
1
Mantissa
1
0
0
0
0
0
0
0
8.6.9.1 Exponent
–2 (dec), fixed.
8.6.9.2 Mantissa
The upper four bits are fixed at 0.
The lower seven bits are programmable with a default value of 17 (dec), corresponding to a default of 4.25 V.
8.6.10 VIN_OFF (36h)
The VIN_OFF command sets the value of the input voltage at which the unit should stop operation. Values are
mapped to the nearest supported increment. Values outside the supported range is treated as invalid data and
causes the device to set the CML bit in the STATUS_BYTE and the invalid data (ivd) bit in the STATUS_CML
registers. The value of VIN_OFF remains unchanged during an out-of-range write attempt. The contents of this
register can be stored to non-volatile memory using the STORE_USER_ALL command.
The supported VIN_OFF values are shown in Table 7:
Table 7. Supported VIN_OFF Values
VIN_OFF Values (V)
4 (default)
4.25
4.5
4.75
5
5.25
5.5
5.75
6
6.25
6.5
6.75
7
7.25
7.5
8
8.25
8.5
8.75
9
9.25
9.75
10.25
10.75
11.25
11.75
12
13.75
14.75
15.75
VIN_ON must be set higher than VIN_OFF. Attempting to write either VIN_ON lower than VIN_OFF or VIN_OFF
higher than VIN_ON results in the new value being rejected, SMBALERT being asserted along with the cml bit in
STATUS_BYTE and the invalid data bit in STATUS_CML.
The data word that accompanies this command is divided into a fixed 5 bit exponent and an 11 bit mantissa. The
4 most significant bits of the mantissa are fixed, while the lower 7 bits may be altered.
COMMAND
VIN_OFF
Format
Linear, two's complement binary
Bit Position
7
6
5
4
3
2
1
0
7
6
5
4
3
2
1
0
Access
r
r
r
r
r
r
r
r
r
r/w
r/w
r/w
r/w
r/w
r/w
r/w
1
0
0
0
0
Function
Default Value
Exponent
1
1
1
Mantissa
1
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0
0
0
0
0
0
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8.6.10.1 Exponent
–2 (dec), fixed.
8.6.10.2 Mantissa
The upper four bits are fixed at 0.
The lower seven bits are programmable with a default value of 16 (dec). This corresponds to a default value of
4.0 V.
8.6.11 IOUT_CAL_OFFSET (39h)
The IOUT_CAL_OFFSET is used to compensate for offset errors in the READ_IOUT results and the
IOUT_OC_FAULT_LIMIT and IOUT_OC_WARN_LIMIT thresholds. The units are amperes. The default setting is
0 A. The resolution of the argument for this command is 62.5 mA and the range is +3937.5 mA to -4000 mA.
Values written outside of this range alias into the supported range. This occurs because the read-only bits are
fixed. The exponent is always –4 and the 5 msb bits of the Mantissa are always equal to the sign bit. The
contents of this register can be stored to non-volatile memory using the STORE_USER_ALL command.
COMMAND
IOUT_CAL_OFFSET
Format
Linear, two's complement binary
Bit Position
7
6
5
4
3
2
1
0
7
6
5
4
3
2
1
0
Access
r
r
r
r
r
r/w
r
r
r
r
r/w
r/w
r/w
r/w
r/w
r/w
1
1
0
0
0
0
0
0
0
0
0
0
0
0
Function
Default Value
Exponent
1
Mantissa
0
8.6.11.1 Exponent
–4 (dec), fixed.
8.6.11.2 Mantissa
MSB is programmable with sign, next 4 bits are sign extend only.
Lower six bits are programmable with a default value of 0 (dec).
8.6.12 IOUT_OC_FAULT_LIMIT (46h)
The IOUT_OC_FAULT_LIMIT command sets the value of the output current, in amperes, that causes the
overcurrent detector to indicate an overcurrent fault condition. The IOUT_OC_FAULT_LIMIT should be set equal
to or greater than the IOUT_OC_WARN_LIMIT. Writing a value to IOUT_OC_FAULT_LIMIT less than
IOUT_OC_WARN_LIMIT causes the device to set the CML bit in the STATUS_BYTE and the invalid data (ivd)
bit in the STATUS_CML registers as well as assert SMBALERT. The contents of this register can be stored to
non-volatile memory using the STORE_USER_ALL command.
The IOUT_OC_FAULT_LIMIT takes a two-byte data word formatted as shown below:
COMMAND
IOUT_OC_FAULT_LIMIT
Format
Linear, two's complement binary
Bit Position
7
6
5
4
3
2
1
0
7
6
5
4
3
2
1
0
Access
r
r
r
r
r
r
r
r
r
r/w
r/w
r/w
r/w
r/w
r/w
r/w
Function
Exponent
Default Value
Mantissa
See Below
8.6.12.1 Exponent
–1 (dec), fixed.
8.6.12.2 Mantissa
The upper four bits are fixed at 0.
The lower seven bits are programmable.
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The actual output current for a given mantissa and exponent is shown in Equation 5.
Mantissa
IOUT(oc) = Mantissa ´ 2Exponent =
2
(5)
The default values and allowable ranges for each device are summarized below:
OC_FAULT_LIMIT
DEVICE
UNIT
MIN
DEFAULT
MAX
TPS544C20
5
39
45
A
TPS544B20
5
26
30
A
8.6.13 IOUT_OC_FAULT_RESPONSE (47h)
The IOUT_OC_FAULT_RESPONSE command instructs the device on what action to take in response to an
IOUT_OC_FAULT_LIMIT or a VOUT undervoltage (UV) fault. The device also:
• Sets the IOUT_OC bit in the STATUS_BYTE
• Sets the IOUT or POUT bit in the STATUS_WORD
• Sets the IOUT OC Fault bit in the STATUS_IOUT register
• Notifies the PMBus host by asserting SMBALERT
The contents of this register can be stored to non-volatile memory using the STORE_USER command.
COMMAND
IOUT_OC_FAULT_RESPONSE
Format
Unsigned binary
Bit Position
7
6
5
4
3
2
1
Access
r
r
r/w
r/w
r/w
r
r
0
r
Function
X
X
RS[2]
RS[1]
RS[0]
X
X
X
Default Value
0
0
0
0
0
1
1
1
8.6.13.1 RS[2:0]
000:
A zero value for the Retry Setting means that the unit does not attempt to restart. The output
remains disabled until the fault is cleared (See section 10.7 of the PMBus spec.)
111:
A one value for the Retry Setting means that the unit goes through a normal startup (Soft start)
continuously, without limitation, until it is commanded off or bias power is removed or another fault
condition causes the unit to shutdown.
Any value other than 000 or 111 is not accepted. Attempting to write any other value is rejected, causing
the device to assert SMBALERT along with the CML bit in STATUS_BYTE and the invalid data bit in
STATUS_CML.
8.6.14 IOUT_OC_WARN_LIMIT (4Ah)
The IOUT_OC_WARN_LIMIT command sets the value of the output current, in amperes, that causes the overcurrent detector to indicate an over-current warning. When this current level is exceeded the device:
• Sets the OTHER bit in the STATUS_BYTE
• Sets the IOUT or POUT bit in the STATUS_WORD
• Sets the IOUT overcurrent Warning (OCW) bit in the STATUS_IOUT register, and
• Notifies the host by asserting SMBALERT
The IOUT_OC_WARN_LIMIT threshold should always be set to less than or equal to the
IOUT_OC_FAULT_LIMIT. Writing a value to IOUT_OC_WARN_LIMIT greater than IOUT_OC_FAULT_LIMIT
causes the device to set the CML bit in the STATUS_BYTE and the invalid data (ivd) bit in the STATUS_CML
registers as well as assert SMBALERT. The contents of this register can be stored to non-volatile memory using
the STORE_USER_ALL command.
The IOUT_OC_WARN_LIMIT takes a two byte data word formatted as shown below:
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COMMAND
IOUT_OC_WARN_LIMIT
Format
Linear, two's complement binary
Bit Position
7
6
5
4
3
2
1
0
7
6
5
4
3
2
1
0
Access
r
r
r
r
r
r
r
r
r
r/w
r/w
r/w
r/w
r/w
r/w
r/w
Function
Exponent
Mantissa
Default Value
See Below
8.6.14.1 Exponent
–1 (dec), fixed.
8.6.14.2 Mantissa
The upper four bits are fixed at 0.
Lower seven bits are programmable.
The actual output warning current level for a given mantissa and exponent is:
Mantissa
2
IOUT (OCW ) = Mantissa × 2Exponent =
(6)
The default values and allowable ranges for each device are summarized below:
OC_WARN_LIMIT
DEVICE
UNIT
MIN
DEFAULT
MAX
TPS544C20
4
30
45
A
TPS544B20
4
20
30
A
8.6.15 OT_FAULT_LIMIT (4Fh)
The OT_FAULT_LIMIT command sets the value of the temperature, in degrees Celsius, that causes an overtemperature fault condition, when the sensed temperature from the external sensor exceeds this limit. Upon
triggering the over-temperature fault, the device takes the following actions:
• Sets the TEMPERATURE bit in the STATUS_BYTE
• Sets the OT Fault bit in the STATUS_TEMPERATURE
• Notifies the host by asserting SMBALERT
Once the over-temperature fault is tripped, the output is latched off until the external sensed temperature falls
20°C from the OT_FAULT_LIMIT, at which point the output goes through a normal startup (soft-start).
The OT_FAULT_LIMIT must always be greater than the OT_WARN_LIMIT. Writing a value to OT_FAULT_LIMIT
less than or equal to OT_WARN_LIMIT causes the device to set the CML bit in the STATUS_BYTE and the
invalid data (ivd) bit in the STATUS_CML registers as well as asserts SMBALERT. The contents of this register
can be stored to non-volatile memory using the STORE_USER_ALL command.
The OT_FAULT_LIMIT takes a two byte data word formatted as shown below.
COMMAND
OT_FAULT_LIMIT
Format
Unsigned binary
Bit Position
7
6
Access
r
r
Function
Default Value
38
5
4
3
2
1
0
7
6
r
r
r
r
r
r
r/w
r/w
Exponent
0
0
0
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5
4
3
2
1
0
r/w
r/w
r/w
r/w
r/w
r/w
1
0
1
1
0
Mantissa
0
0
0
0
0
1
0
0
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8.6.15.1 Exponent
0 (dec), fixed.
8.6.15.2 Mantissa
The upper three bits are fixed at 0.
Lower eight bits are programmable with a default value of 150 (dec).
The default over-temperature fault setting is 150°C. Values can range from 120°C to 165°C in 1°C increments.
8.6.16 OT_WARN_LIMIT (51h)
The OT_ WARN _LIMIT command sets the value of the temperature, in degrees Celsius, that causes an overtemperature warning condition, when the sensed temperature from the external sensor exceeds this limit. Upon
triggering the over-temperature warning, the device takes the following actions:
• Sets the TEMPERATURE bit in the STATUS_BYTE
• Sets the OT Warning bit in the STATUS_TEMPERATURE
• Notifies the host by asserting SMBALERT
Once the over-temperature warning is tripped, the warning flag is latched until the external sensed temperature
falls 20°C from the OT_WARN_LIMIT.
The OT_WARN_LIMIT must always be less than the OT_FAULT_LIMIT. Writing a value to OT_WARN_LIMIT
greater than or equal to OT_FAULT_LIMIT causes the device to set the CML bit in the STATUS_BYTE and the
invalid data (ivd) bit in the STATUS_CML registers as well as assert SMBALERT. The contents of this register
can be stored to non-volatile memory using the STORE_USER_ALL command.
The OT_WARN_LIMIT takes a two byte data word formatted as shown below:
COMMAND
OT_WARN_LIMIT
Format
Unsigned binary
Bit Position
7
6
5
4
3
2
1
0
7
6
5
4
3
2
1
0
Access
r
r
r
r
r
r
r
r
r/w
r/w
r/w
r/w
r/w
r/w
r/w
r/w
0
0
0
0
0
0
0
0
1
1
1
1
0
1
Function
Default Value
Exponent
0
Mantissa
1
8.6.16.1 Exponent
0 (dec), fixed.
8.6.16.2 Mantissa
The upper three bits are fixed at 0.
Lower eight bits are programmable with a default value of 125 (dec).
The default over-temperature fault setting is 125°C. Values can range from 100°C to 140°C in 1°C increments.
8.6.17 TON_RISE (61h)
The TON_RISE command sets the time in ms, from when the reference starts to rise until the voltage has
entered the regulation band. It also determines the rate of the transition of the reference voltage (either due to
VREF_TRIM or STEP_VREF_MARGIN_x commands) when this transition is executed during the soft-start
period. There are several discrete settings that this command supports. Commanding a value other than one of
these values results in the nearest supported value being selected.
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The supported TON_RISE times over PMBus are shown in Table 8:
Table 8. Supported TON_RISE Values
TON_RISE VALUES (ms)
0.6
0.9
1.2
4.2
6.0
9.0
1.7
2.7 (default)
A value of 0 ms instructs the unit to bring its output voltage to the programmed regulation value as quickly as
possible. The contents of this register can be stored to non-volatile memory using the STORE_USER_ALL
command.
The TON_RISE command is formatted as a linear mode two’s complement binary integer.
COMMAND
TON_RISE
Format
Linear, two's complement binary
Bit Position
7
6
5
4
3
2
1
0
7
6
5
4
3
2
1
0
Access
r
r
r
r
r
r
r
r
r/w
r/w
r/w
r/w
r/w
r/w
r/w
r/w
1
1
0
0
0
0
0
0
0
0
1
0
1
1
Function
Exponent
Default Value
Mantissa
1
1
8.6.17.1 Exponent
–4 (dec), fixed.
8.6.17.2 Mantissa
The upper two bits are fixed at 0.
The lower eight bits are programmable with a default value of 43 (dec).
8.6.18 STATUS_BYTE (78h)
The STATUS_BYTE command returns one byte of information with a summary of the most critical device faults.
COMMAND
STATUS_BYTE
Format
Unsigned binary
Bit Position
7
6
5
4
3
2
1
0
Access
r
r
r
r
r
r
r
r
Function
X
OFF
VOUT_OV
IOUT_OC
VIN_UV
TEMPERATURE
CML
NONE OF THE ABOVE
Default Value
0
0
0
0
0
0
0
0
A "1" in any of these bit positions indicates that:
OFF:
The device is not providing power to the output, regardless of the reason. In this family of devices,
this flag means that the converter is not enabled.
VOUT_OV:
An output overvoltage fault has occurred.
IOUT_OC:
An output over current fault has occurred.
VIN_UV:
An input undervoltage fault has occurred.
TEMPERATURE:
A temperature fault or warning has occurred. Check STATUS_TEMPERATURE.
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CML:
A Communications, Memory or Logic fault has occurred. Check STATUS_CML.
NONE OF THE ABOVE:
A fault or warning not listed in bit1 through bits 1-7 has occurred, for example an undervoltage
condition or an over current warning condition. Check other status registers.
8.6.19 STATUS_WORD (79h)
The STATUS_WORD command returns two bytes of information with a summary of the device fault and warning
conditions. The low byte is identical to the STATUS_BYTE above. The additional byte reports the warning
conditions for output overvoltage and overcurrent, as well as the power good status of the converter.
COMMAND
STATUS_WORD (low byte) = STATUS_BYTE
Format
Unsigned binary
Bit Position
7
6
5
4
3
2
1
Access
r
r
r
r
r
r
r
0
r
Function
X
OFF
VOUT_OV
IOUT_OC
VIN_UV
TEMPERATURE
CML
NONE OF THE ABOVE
Default Value
0
x
0
0
0
0
0
0
A "1" in any of the low byte (STATUS_BYTE) bit positions indicates that:
OFF:
The device is not providing power to the output, regardless of the reason. In this family of devices
this flag means that the converter is not enabled.
VOUT_OV:
An output overvoltage fault has occurred.
IOUT_OC:
An output over current fault has occurred.
VIN_UV:
An input undervoltage fault has occurred.
TEMPERATURE:
A temperature fault or warning has occurred. Check STATUS_TEMPERATURE.
CML:
A Communications, Memory or Logic fault has occurred. Check STATUS_CML.
NONE OF THE ABOVE:
A fault or warning not listed in bits 1-7 has occurred. See other status registers.
COMMAND
STATUS_WORD (high byte)
Format
Unsigned binary
Bit Position
7
6
5
4
3
2
1
0
Access
r
r
r
r
r
r
r
r
VOUT
IOUT or
POUT
X
MFR
POWER_GOOD
X
X
X
0
0
0
0
0
0
0
0
Function
Default Value
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A "1" in any of the high byte bit positions indicates that:
VOUT:
An output voltage fault or warning has occurred. Check STATUS_VOUT.
IOUT/POUT:
An output current warning or fault has occurred. The PMBus specification states that this warning
also applies to output power. This family of devices does not support output power warnings or
faults. Check STATUS_IOUT.
MFR:
An internal thermal shutdown (TSD) fault has occurred in the device. Check
STATUS_MFR_SPECIFIC.
POWER_GOOD:
The power good signal has not transitioned from high-to-low.
8.6.20 STATUS_VOUT (7Ah)
The STATUS_VOUT command returns one byte of information relating to the status of the output voltage related
faults. The only bits of this register supported are:
• VOUT_OV Fault
• VOUT_UV Fault
COMMAND
STATUS_VOUT
Format
Unsigned binary
Bit Position
7
6
5
4
3
2
1
Access
r
r
r
r
r
r
r
r
VOUT OV Fault
X
X
VOUT UV Fault
X
X
X
X
0
0
0
0
0
0
0
0
Function
Default Value
0
A "1" in any of these bit positions indicates that:
VOUT OV Fault:
The device has seen the output voltage rise above the output overvoltage threshold.
VOUT UV Fault:
The device has seen the output voltage fall below the output undervoltage threshold.
8.6.21 STATUS_IOUT (7Bh)
The STATUS_IOUT command returns one byte of information relating to the status of the output current related
faults. The only bits of this register supported are:
• IOUT_OC Fault
• IOUT_OC Warning
COMMAND
STATUS_IOUT
Format
Unsigned binary
Bit Position
7
6
5
4
3
2
1
Access
r
r
r
r
r
r
r
r
IOUT_OC Fault
X
IOUT_OC Warning
X
X
X
X
X
0
0
0
0
0
0
0
0
Function
Default Value
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A "1" in any of these bit positions indicates that:
IOUT_OC Fault:
The device has seen the output current rise above the level set by IOUT_OC_FAULT_LIMIT.
IOUT_OC Warn:
The device has seen the output current rise relating to the level set by IOUT_OC_WARN_LIMIT.
8.6.22 STATUS_TEMPERATURE (7Dh)
The STATUS_TEMPERATURE command returns one byte of information relating to the status of the external
temperature related faults. The only bits of this register supported are:
• OT Fault
• OT Warning
COMMAND
STATUS_TEMPERATURE
Format
Unsigned binary
Bit Position
7
Access
Function
6
5
4
3
2
1
0
r
r
r
r
r
r
r
r
OT Fault
OT Warning
X
X
X
X
X
X
0
0
0
0
0
0
0
0
Default Value
A "1" in any of these bit positions indicates that:
OT Fault:
The measured external temperature has exceeded the level set by OT_FAULT_LIMIT.
OT Warning:
The measured external temperature has exceeded the level set by OT_WARN_LIMIT.
8.6.23 STATUS_CML (7Eh)
The STATUS_CML command returns one byte of information relating to the status of the converter’s
communication related faults. The bits of this register supported by the this family of devices are:
• Invalid or Unsuppported Command
• Invalid or Unsupported Data
• Packet Error Check Failed
• Memory Fault Detected
• Other Communication Fault.
COMMAND
STATUS_CML
Format
Unsigned binary
Bit Position
7
6
5
4
3
2
1
0
Access
r
r
r
r
r
r
r
r
Invalid or
Unsupported
Command
Invalid or
Unsupported
Data
Packet Error
Check Failed
Memory Fault
Detected
X
X
Other
Communication
Fault
X
0
0
0
0
0
0
0
0
Function
Default Value
A "1" in any of these bit positions indicates that:
Invalid or Unsupported Command:
An invalid or unsupported command has been received.
Invalid or Unsupported Data
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Invalid or unsupported data has been received
Packet Error Check Failed
A packet has failed the CRC checksum error check.
Memory Fault Detected
A fault has been detected with the internal memory.
Other Communication Fault
Some other communication fault or error has occurred
8.6.24 STATUS_MFR_SPECIFIC (80h)
The STATUS_MFR_SPECIFIC command returns one byte of information relating to the status of manufacturerspecific faults or warnings.
COMMAND
STATUS_MFR_SPECIFIC
Format
Unsigned binary
Bit Position
7
Access
Function
Default Value
6
5
4
3
2
1
0
r
r
r
r
r
r
r
r
OTFI
X
X
IVFREQ
X
X
X
X
0
0
0
0
0
0
0
0
A "1" in any of these bit positions indicates that:
OTFI:
The internal temperature is above the thermal shutdown (TSD) fault threshold
IVFREQ:
The switching frequency detection circuit is not resolving to a valid selection based on the RT
resistor.
8.6.25 READ_VOUT (8Bh)
The READ_VOUT commands returns two bytes of data in the linear data format that represent the output voltage
of the controller. The output voltage is sensed at the remote sense amplifier output pin so voltage drop to the
load is not accounted for. The data format is as shown below:
COMMAND
READ_VOUT
Format
Linear, two's complement binary
Bit Position
7
6
5
4
3
2
1
0
7
6
5
4
3
2
1
0
Access
r
r
r
r
r
r
r
r
r
r
r
r
r
r
r
r
0
0
0
0
0
0
0
Function
Default Value
Mantissa
0
0
0
0
0
0
0
0
0
The setting of the VOUT_MODE affects the results of this command as well. In this family of devices,
VOUT_MODE is set to linear mode with an exponent of –9 and cannot be altered. The output voltage calculation
is shown in Equation 7.
VOUT = Mantissa ´ 2Exponent
(7)
8.6.26 READ_IOUT (8Ch)
The READ_IOUT commands returns two bytes of data in the linear data format that represent the output current
of the controller. The average output current is sensed according to the method described in Low-Side MOSFET
Current Sensing and Overcurrent Protection. The data format is as shown below:
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COMMAND
READ_IOUT
Format
Linear, two's complement binary
Bit Position
7
6
5
4
3
2
1
0
7
6
5
4
3
2
1
0
Access
r
r
r
r
r
r
r
r
r
r
r
r
r
r
r
r
0
0
0
0
0
Function
Default Value
Exponent
1
1
1
Mantissa
0
0
0
0
0
0
0
0
The device scales the output current before it reaches the internal analog to digital converter so that resolution of
the output current read is 62.5 mA. The maximum value that can be reported is 64 A. The user must set the
IOUT_CAL_OFFSET parameter correctly in order to obtain accurate results. Calculate the output current using
Equation 8.
IOUT = Mantissa ´ 2Exponent
(8)
8.6.26.1 Exponent
Fixed at -4.
8.6.26.2 Mantissa
The lower 10 bits are the result of the ADC conversion of the average output current, as indicated by the output
of the internal current sense amplifier. The 11th bit is fixed at 0 because only positive numbers are considered
valid. Any computed negative current is reported as 0 A.
8.6.27 READ_TEMPERATURE_2 (8Eh)
The READ_TEMPERATURE_2 command returns the external temperature in degrees Celsius of the current
channel.
COMMAND
READ_TEMPERATURE_2
Format
Linear, two's complement binary
Bit Position
7
6
Access
r
r
Function
Default Value
5
4
3
2
1
0
7
6
r
r
r
r
r
r
r
r
Exponent
0
0
0
5
4
3
2
1
0
r
r
r
r
r
r
1
1
0
0
1
Mantissa
0
0
0
0
0
0
0
0
8.6.27.1 Exponent
0 (dec), fixed.
8.6.27.2 Mantissa
The lower 11 bits are the result of the ADC conversion of the external temperature. The default reading is 25
(dec) corresponding to a temperature of 25°C.
8.6.28 PMBUS_REVISION (98h)
The PMBUS_REVISION command returns a single, unsigned binary byte that indicates that these devices are
compatible with the 1.1 revision of the PMBus specification.
COMMAND
PMBUS_REVISION
Format
Unsigned binary
Bit Position
7
6
5
4
3
2
1
Access
r
r
r
r
r
r
r
r
Default Value
0
0
0
1
0
0
0
1
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8.6.29 MFR_SPECIFIC_00 (D0h)
The MFR_SPECIFIC_00 register is dedicated as a user scratch pad.
COMMAND
MFR_SPECIFIC_00
Format
Unsigned binary
Bit Position
Access
7
6
5
4
3
2
1
0
r/w
r/w
r/w
r/w
r/w
r/w
r/w
r/w
Function
7
6
5
4
3
2
1
0
r/w
r/w
r/w
r/w
r/w
r/w
r/w
r/w
0
0
0
0
0
0
User scratch pad
Default Value
0
0
0
0
0
0
0
0
0
0
The contents of this register can be stored to non-volatile memory using the STORE_USER_ALL command.
8.6.30 VREF_TRIM (MFR_SPECIFIC_04) (D4h)
The VREF_TRIM command applies a fixed offset voltage to the reference voltage. It is most typically used to trim
the output voltage at the time the PMBus device is assembled into the final application design. The contents of
this register can be stored to non-volatile memory using the STORE_USER_ALL command.
the settings of the VOUT_MODE command determine the effect of VREF_TRIM command. In this device, the
VOUT_MODE is fixed to Linear with an exponent of –9 (decimal).
VREF :offset ; = VREF_TRIM × 2 mV
(9)
The maximum trim ranges between –20% to +10% of the nominal reference voltage (600 mV) in 2 mV steps.
Permissible values range from –120 mV to +60 mV. If a value outside this range is given with this command, the
device sets the reference voltage to the upper or lower limit depending on the direction of the setting, asserts
SMBALERT and sets the CML bit in STATUS_BYTE and the invalid data bit in STATUS_CML.
Including settings from both VREF_TRIM and STEP_VREF_MARGIN_x commands, the net permissible
reference voltage adjustment range is –180 mV to +60 mV (-30% to +10%). If a value outside this range is given
with this command, the device sets the reference voltage to the upper or lower limit depending on the direction of
the setting, asserts SMBALERT and sets the CML bit in STATUS_BYTE and the invalid data bit in
STATUS_CML.
The reference voltage transition occurs at the rate determined by the TON_RISE command if the transition is
executed during the soft-start period. Any transition in the reference voltage after soft-start is complete occurs at
the slew rate defined by the slowest soft-start time, or 0.067 mV/µs. For example, a trim which moves the
reference by 10%, occurs in approximately 900 µs.
COMMAND
VREF_TRIM
Format
Linear, two’s complement binary
Bit Position
Access
7
6
5
4
3
2
1
0
7
6
5
4
3
2
1
0
r/w
r
r
r
r
r
r
r
r
r
r/w
r/w
r/w
r/w
r/w
r/w
0
0
0
Function
Default
Value
High Byte
0
0
0
0
0
Low Byte
0
0
0
0
0
0
0
0
8.6.31 STEP_VREF_MARGIN_HIGH (MFR_SPECIFIC_05) (D5h)
The STEP_VREF_MARGIN_HIGH command sets the target voltage which the reference voltage changes to
when the OPERATION command is set to "Margin High". The contents of this register can be stored to nonvolatile memory using the STORE_USER_ALL command.
The effect of this command is determined by the settings of the VOUT_MODE command. In this device, the
VOUT_MODE is fixed to Linear with an exponent of –9 (decimal). The actual reference voltage commanded by a
margin high command can be found by:
VREF :MH ; = (STEP_VREF_MARGIN_HIGH + VREF_TRIM) × 2 mV
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The margin high range is between 0% and 10% of the nominal reference voltage (600 mV) in 2-mV steps.
Permissible values range from 0 mV to 60 mV. If a value outside this range is given with this command, the
device sets the reference voltage to the upper or lower limit depending on the direction of the setting, asserts
SMBALERT and sets the CML bit in STATUS_BYTE and the invalid data bit in STATUS_CML.
Including settings from both VREF_TRIM and STEP_VREF_MARGIN_x commands, the net permissible
reference voltage adjustment range is –180 mV to 60 mV (-30% to 10%). If a value outside this range is given
with this command, the device sets the reference voltage to the upper or lower limit depending on the direction of
the setting, asserts SMBALERT and sets the CML bit in STATUS_BYTE and the invalid data bit in
STATUS_CML.
The reference voltage transition occurs at the rate determined by the TON_RISE command if the transition is
executed during soft-start. Any transition in the reference voltage after soft-start is complete occurs at the slew
rate defined by the slowest soft-start time, or 0.067 mV/µs. For example, a trim which moves the reference by
10%, occurs in approximately 900 µs.
COMMAND
STEP_VREF_MARGIN_HIGH
Format
Linear, two's complement binary
Bit Position
7
6
5
4
3
2
1
0
7
6
5
4
3
2
1
0
Access
r
r
r
r
r
r
r
r
r
r
r
r/w
r/w
r/w
r/w
r/w
0
0
0
0
0
0
0
0
0
0
1
1
1
0
Function
Default Value
High Byte
Low Byte
0
1
The default value of STEP_VREF_MARGIN_HIGH is 30 (dec), corresponding to a default margin high voltage of
60 mV (+10%) .
8.6.32 STEP_VREF_MARGIN_LOW (MFR_SPECIFIC_06) (D6h)
The STEP_VREF_MARGIN_LOW command sets the target voltage which the reference voltage changes to
when the OPERATION command is set to Margin Low. The contents of this register can be stored to non-volatile
memory using the STORE_USER_ALL command.
The effect of this command is determined by the settings of the VOUT_MODE command. In this device, the
VOUT_MODE is fixed to Linear with an exponent of –9 (decimal). Equation 11 shows the actual output voltage
commanded by a margin high command.
VREF :ML; = (STEP_VREF_MARGIN_LOW + VREF_TRIM) × 2 mV
(11)
The margin low ranges between –20% and 0% of the nominal reference voltage (600 mV) in 2-mV steps.
Permissible values range from –120 mV to 0 mV. If a value outside this range is given with this command, the
device sets the reference voltage to the upper or lower limit depending on the direction of the setting, asserts
SMBALERT and sets the CML bit in STATUS_BYTE and the invalid data bit in STATUS_CML.
Including settings from both VREF_TRIM and STEP_VREF_MARGIN_x commands, the net permissible
reference voltage adjustment range is –180 mV to 60 mV (–30% to +10%). If a value outside this range is given
with this command, the device sets the reference voltage to the upper or lower limit depending on the direction of
the setting, asserts SMBALERT and sets the CML bit in STATUS_BYTE and the invalid data bit in
STATUS_CML.
The reference voltage transition occurs at the rate determined by the TON_RISE command if the transition is
executed during the soft-start period. Any transition in the reference voltage after soft-start is complete occurs at
the slew rate defined by the slowest soft-start time, or 0.067 mV/µs. For example, a trim which moves the
reference by 10%, occurs in approximately 900 µs.
COMMAND
STEP_VREF_MARGIN_LOW
Format
Bit Position
Access
Linear, two's complement binary
7
6
5
4
3
2
1
0
7
6
5
4
3
2
1
0
r/w
r
r
r
r
r
r
r
r
r
r/w
r/w
r/w
r/w
r/w
r/w
1
1
1
1
1
1
1
1
1
0
1
0
Function
Default Value
High Byte
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1
Low Byte
0
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The default value of STEP_VREF_MARGIN_LOW is –30 (dec), corresponding to a default margin low voltage of
–60 mV (–10%).
8.6.33 PCT_VOUT_FAULT_PG_LIMIT (MFR_SPECIFIC_07) (D7h)
The PCT_VOUT_FAULT_PG_LIMIT command is used to set the PGOOD, VOUT_UNDER_VOLTAGE (UV) and
VOUT_OVER_VOLTAGE (OV) limits as a percentage of nominal.
The PCT_VOUT_FAULT_PG_LIMIT takes a one byte data word formatted as shown below:
COMMAND
PCT_VOUT_FAULT_PG_LIMIT
Format
Unsigned binary
Bit Position
7
6
5
4
3
2
1
0
Access
r
r
r
r
r
r
r/w
r/w
Function
X
X
X
X
X
X
PCT_MSB
PCT_LSB
Default Value
0
0
0
0
0
0
0
0
The PGOOD, VOUT_UNDER_VOLTAGE (UV) and VOUT_OVER_VOLTAGE (OV) settings are shown in
Table 9, as a percentage of nominal reference voltage on the FB pin.
Table 9. Protection Settings (typical)
PCT_MSB
PCT_LSB
UV
PGL LOW
PGH HIGH
OV
0
0
-16.8%
-12.5%
12.5%
16.8%
0
1
-12.0%
-7.0%
7.0%
12.0%
1
0
-28.0%
-22.0%
7.0%
12.0%
1
1
-42.0%
-36.0%
7.0%
12.0%
The PGOOD pin may trip if the output voltage is too high (using PGH high) or too low (using PGL low).
Additionally, the PGOOD pin has hysteresis.
Additionally, when output overvoltage (OV) is tripped, the output must lower below the PGH high threshold minus
the hysteresis, before PGOOD and OV are reset. Likewise, when output undervoltage (UV) is tripped, the output
must rise above the PGOOD high threshold plus the hysteresis, before PGOOD and UV are reset.
8.6.34 SEQUENCE_TON_TOFF_DELAY (MFR_SPECIFIC_08) (D8h)
The SEQUENCE_TON_TOFF_DELAY command is used to set the delay for turning on the device and turning
off the device as a ratio of TON_RISE.
The SEQUENCE_TON_TOFF_DELAY takes a one byte data word formatted as shown below:
COMMAND
SEQUENCE_TON_TOFF_DELAY
Format
Unsigned binary
Bit Position
7
Access
r/w
Function
6
5
r/w
r/w
TON_DELAY
Default Value
0
0
4
3
r
r/w
X
0
0
2
1
r/w
r/w
TOFF_DELAY
0
0
0
r
X
0
0
TON_DELAY:
This parameter selects the delay from when the output is enabled until soft-start beings, as an
integer multiple of the TON_RISE time. The default value is 0. Values can range from 0 to 7 in
increments of 1. When TON_DELAY = 0, the device imposes a minimum delay of 50 µs.
TOFF_DELAY:
This parameter selects the delay from when the output is disabled until the output stops switching,
as an integer multiple of the TON_RISE time. The default value is 0. Values can range from 0 to 7 in
increments of 1.
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8.6.35 OPTIONS (MFR_SPECIFIC_21) (E5h)
The OPTIONS register can be used for setting user selectable options, as shown below.
COMMAND
OPTIONS
Format
Unsigned binary
Bit Position
7
6
5
4
3
2
1
0
7
6
5
4
3
2
1
0
Access
r
r
r
r
r
r
r
r
r
r
r
r
r
r/w
r
r
Function
X
X
X
X
X
X
X
X
X
X
X
X
X
EN_ADC_CNTL
X
X
Default Value
0
0
0
0
0
0
0
0
0
1
1
1
0
1
0
0
The contents of this register can be stored to non-volatile memory using the STORE_USER_ALL command.
A “1” in any of these bit positions indicates that:
EN_ADC_CNTL:
Enables ADC operation used for voltage, current and temperature monitoring.
NOTE
The EN_ADC_CNTL bit must be set in order to enable output voltage, current and
temperature telemetry. When the EN_ADC_CNTL bit is zero, the READ_VOUT,
READ_IOUT and READ_TEMPERATURE_2 registers do not update continuously, and
retain their previous values from the last time EN_ADC_CNTL was set.
8.6.36 MASK_SMBALERT (MFR_SPECIFIC_23) (E7h)
The MASK SMBALERT command may be used to prevent a warning or fault condition from asserting
SMBALERT.
COMMAND
MASK_SMBALERT (High Byte)
Format
Unsigned Binary
Bit Position
7
6
5
4
3
2
1
0
r/w
r/w
r/w
r/w
r/w
r/w
r/w
r/w
mOTFI
mPRTCL
mSMBTO
mIVC
mIVD
mPEC
mMEM
Auto_ARA
0
0
0
0
0
0
0
1
Access
Function
Default Value
COMMAND
MASK_SMBALERT (Low Byte)
Format
Bit Position
Access
Function
Default Value
Unsigned binary
7
6
5
4
3
2
1
0
r/w
r/w
r/w
r/w
r/w
r/w
r/w
r/w
mOTF
mOTW
mOCF
mOCW
mOVF
mUVF
mPGOOD
mVIN_UV
0
0
0
0
0
0
0
0
8.6.36.1 mOTFI
This bit controls whether an internal overtemperature fault (OTFI) asserts SMBALERT.
• 0: OTFI (STATUS_MFR_SPECIFIC[7]) asserts SMBALERT.
• 1: OTFI does not assert SMBALERT.
8.6.36.2 mPRTCL
This bit controls whether an SMBus Protocol Error causes SMBALERT to assert.
• 0: SMBus Protocol Errors assert SMBALERT.
• 1: SMBus Protocol Errors do not assert SMBALERT.
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8.6.36.3 mSMBTO
This bit controls whether an SMBus Timeout causes SMBALERT to assert.
• 0: SMBus Timeout asserts SMBALERT.
• 1: SMBus Timeout does not assert SMBALERT.
8.6.36.4 mIVC
This bit controls whether an invalid command (IVC) causes SMBALERT to assert.
• 0: Issuing an invalid command asserts SMBALERT.
• 1: Issuing an invalid command does not assert SMBALERT.
8.6.36.5 mIVD
This bit controls whether an invalid or unsupported data (IVD) causes SMBALERT to assert.
• 0: Issuing invalid or unsupported data asserts SMBALERT.
• 1: Issuing invalid or unsupported data does not assert SMBALERT.
8.6.36.6 mPEC
This bit controls whether an invalid packet error check (PEC) byte causes SMBALERT to assert.
• 0: Invalid PEC byte asserts SMBALERT.
• 1: Invalid PEC byte does not assert SMBALERT.
8.6.36.7 mMEM
This bit controls whether a memory error (MEM) causes SMBALERT to assert.
• 0: Memory error (MEM) asserts SMBALERT.
• 1: Memory error (MEM) does not assert SMBALERT.
8.6.36.8 Auto_ARA
This bit controls whether the Auto ARA Response is enabled.
• 0: Auto ARA is disabled. Host must take all action necessary to clear SMBALERT
• 1: Auto ARA is enabled. The device releases SMBALERT after successfully responding to an ARA from the
host.
8.6.36.9 mOTF
This bit controls whether an overtemperature fault (OTF) causes SMBALERT to assert.
• 0: Overtemperature fault (OTF) asserts SMBALERT.
• 1: Overtemperature fault does not assert SMBALERT.
8.6.36.10 mOTW
This bit controls whether an overtemperature warning (OTW) causes SMBALERT to assert.
• 0: Overtemperature warning (OTW) asserts SMBALERT.
• 1: Overtemperature warning (OTW) does not assert SMBALERT.
8.6.36.11 mOCF
This bit controls whether an overcurrent fault (OCF) causes SMBALERT to assert.
• 0: Overcurrent fault (OCF) asserts SMBALERT to assert.
• 1: Overcurrent fault (OCF) does not assert SMBALERT.
8.6.36.12 mOCW
This bit controls whether an overcurrent warning (OCW) causes SMBALERT to assert.
• 0: Overcurrent warning (OCW) asserts SMBALERT.
• 1: Overcurrent warning (OCW) does not assert SMBALERT.
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8.6.36.13 mOVF
This bit controls whether an output overvoltage (OVF) causes SMBALERT to assert.
• 0: Output overvoltage fault (OVF) causes SMBALERT to assert.
• 1: Mask SMBALERT assertion due to STATUS_VOUT[7].
8.6.36.14 mUVF
This bit controls whether an output undervoltage (UVF) causes SMBALERT to assert.
• 0: Output undervoltage fault (UVF) asserts SMBALERT.
• 1: Output undervoltage fault does not assert SMBALERT.
8.6.36.15 mPGOOD
This bit controls whether a PGOOD transition from high-to-low causes SMBALERT to assert.
• 0: PGOOD transition from high-to-low asserts SMBALERT.
• 1: PGOOD transition from high to low does not assert SMBALERT.
8.6.36.16 mVIN_UV
This bit controls whether an input undervoltage fault (VIN_UV) causes SMBALERT to assert.
• 0: Input undervoltage fault (VIN_UV) asserts SMBALERT.
• 1: Input undervoltage fault (VIN_UV) does not assert SMBALERT.
8.6.37 DEVICE_CODE (MFR_SPECIFIC_44) (FCh)
The DEVICE_CODE command returns a two byte unsigned binary 12-bit device identifier code and 4-bit revision
code in the following format.
COMMAND
MFR_SPECIFIC_44
Format
Linear, two's complement binary
Bit Position
7
6
5
4
3
2
1
0
7
6
5
4
3
2
1
0
Access
r
r
r
r
r
r
r
r
r
r
r
r
r
r
r
r
Function
Identifier Code
Default Value
Revision Code
See Below.
This command provides similar information to the DEVICE_ID command but for devices that do not support block
read and write functions.
The fixed, read-only values for each device are summarized below:
IDENTIFIER CODE
REVISION CODE
REGISTER VALUE
TPS544C20
DEVICE
015h
3h
0153h
TPS544B20
014h
3h
0143h
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9 Applications and Implementation
9.1 Application Information
The TPS544B20 and TPS544C20 devices are highly-integrated synchronous step-down DC-DC converters.
These devices are used to convert a higher DC input voltage to a lower DC output voltage, with a maximum
output current of 20 A and 30 A respectively.
9.2 Typical Application
Use the following design procedure to select key component values for this family of devices, and set the
appropriate behavioral options according to the PMBus protocol.
VIN
CI2
100 PF
CI3
CI4
CI5
CI6
22 PF
22 PF
22 PF
22 PF
CI7
4.7 nF
RVDD
VOUTS+
0Ÿ
VOUTS-
4.99 NŸ
10 NŸ
C2
RA0
38.3 NŸ
RA1
38.3 NŸ
VIN 25
VIN 24
38 AGND
28 BP6
38.3 NŸ
26
PGND
14 GND
15 GND
16 GND
17 GND
20
4.7 PF
18 GND
GND
CB6
19 GND
AGND
VOUTS+
10 Ÿ
L1
RSP
VOUT
410 nH
CSB
1 nF
SW 10
11
SW
12
SW
30
BPEXT
6
SMBALERT
5
CLK
4
DATA
36
PGOOD
37
TSNS
39 MODE
1
CNTL
27
BP3
3
ADDR0
2
ADDR1
40 RT
RT
CB3
0.1 PF
CB
0.1 PF
BOOT 7
8
SW
SW 9
33 DIFFO
34
FB
35
COMP
8.2 nF
RB
0Q
13 AGNDSNS
R1
U1
TPS544C20RVF
VOUTS+ 31
VOUTS- 32
RBias
VIN 23
VDD 29
GND
VIN 22
CVDD
1.0 PF
GND
VIN 21
CI1
100 PF
CO1
CO2
220 PF
220 PF
CO3
22 PF
CO4
CO5
22 PF
22 PF
RSB
3Ÿ
RSN
10 Ÿ
VOUTSGND
GND
SMBALERT
PMBus
Interface
CLK
DATA
PGOOD
CT
1 nF
QT
AGND
AGND
GND
Copyright © 2016, Texas Instruments Incorporated
Figure 32. TPS544C20 4.5-V to 18-V Input, 1.8-V Output, 30-A Converter
9.2.1 Design Requirements
For this design example, use the following input parameters.
Table 10. Design Example Specifications
PARAMETER
VI
Input voltage
VI(ripple)
Input ripple voltage
VO
Output voltage
TEST CONDITION
MIN
TYP
MAX
UNIT
4.5
12.0
18.0
V
0.4
V
IOUT = 30 A
1.8
V
Line regulation
4.5 V ≤ VI ≤ 18 V
0.5%
Load regulation
0 V ≤ IO ≤ 30 A
0.5%
V(PP)
Output ripple voltage
IO = 30 A
18
mV
V(OVER)
Transient response overshoot
I(STEP) = 10 A
36
mV
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Typical Application (continued)
Table 10. Design Example Specifications (continued)
PARAMETER
TEST CONDITION
V(UNDER)
Transient response undershoot
I(STEP) = 10 A
IO
Output current
5 V ≤ VI ≤ 18 V
tSS
Soft-start time
VI = 12 V
IOC
Overcurrent trip point
η
Efficiency
fSW
Switching frequency
MIN
TYP
MAX
-36
0
IO = 20 A, VI = 12 V
UNIT
mV
20
30
A
2.7
ms
40
A
90%
500
kHz
9.2.2 Detailed Design Procedure
9.2.2.1 Switching Frequency Selection
There is a trade-off between higher and lower switching frequencies. Higher switching frequencies may produce
smaller a solution size using lower valued inductors and smaller output capacitors compared to a power supply
that switches at a lower frequency. However, the higher switching frequency produce higher switch losses, which
decrease efficiency and impact thermal performance. In this design, a moderate switching frequency of 500 kHz
achieves both a balance between a small solution size and high-efficiency operation. With the frequency
selected, use Table 2 to select the timing resistor. For a frequency of 500 kHz RRT is 38.2 kΩ.
9.2.2.2 Inductor Selection
To calculate the value of the output inductor, use Equation 12. The coefficient KIND represents the amount of
peak-to-peak inductor ripple current relative to the maximum output current. The output capacitor filters the
inductor ripple current; therefore, choosing a high inductor ripple current impacts the selection of the output
capacitor because the output capacitor must have a ripple current rating equal to or greater than the inductor
ripple current. To achieve balanced performance, maintain a KIND coefficient between 0.3 and 0.4. Using this
target ripple current, the required inductor size can be calculated as shown in Equation 12.
L1 =
VOUT
VIN F VOUT
1.8 V × (18 V F 1.8 V)
×
=
= 360 nH
VIN(max ) × fSW IOUT :max ; × KIND 18 V × 500 kHz × 30 A × 0.3
(12)
Selecting KIND = 0.3, the target inductance L1 = 360 nH. Using the next standard value, the 320 nH Pulse (brand)
PG077.321NL is chosen in this application for its high current rating, low DCR, and small size. The inductor
ripple current, RMS current, and peak current can be calculated using Equation 13, Equation 14 and
Equation 15. These values should be used to select an inductor with approximately the target inductance value,
and current ratings that allow normal operation with some margin.
IRIPPLE =
VIN :max ; F VOUT
VOUT
1.8 V × (18 V F 1.8 V)
×
=
= 10.1 A
VIN (max ) × fSW
L1
18 V × 500 kHz × 320 nH
2
IL(rms ) = ¨IOUT
(max ) +
IL
peak
= IOUT
1 2
1
IRIPPLE = ¨:30 A;2 + :10. 1 A;2 = 30.14 A
12
12
1
1
+ IRIPPLE = 30 A + × 10.1A = 35.1 A
2
2
(13)
(14)
(15)
The Pulse PG077.321NL is rated for 45 A RMS current, and 48-A saturation. Using this inductor, the ripple
current IRIPPLE= 10.1 A, the RMS inductor current IL(rms)= 30.14 A, and peak inductor current IL(peak)= 35 A.
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9.2.2.3 Output Capacitor Selection
There are three primary considerations for selecting the value of the output capacitor. The output capacitor
affects three criteria:
• how the regulator responds to a load transition
• the output voltage ripple
• the minimum output capacitance needed to maintain stable D-CAP2 mode control
The output capacitance needs to be selected based on the most stringent of these three criteria.
9.2.2.3.1 Response to a Load Transition
The desired response to a load transition is the first criterion. The output capacitor must supply the load with the
required current when not immediately provided by the regulator. When the output capacitor supplies load
current, the impedance of the capacitor greatly affects the magnitude of voltage deviation during the transient.
These devices use Adaptive Constant On-Time (COT) control. During a transient, the ON-time remains
unchanged from normal operation, but the off-time shortens to allow a rapid increase in the inductor current in
order to meet the demands of the load transition. To estimate the time required to respond to a load increase,
calculate the number of switching cycles required to change the inductor current using Equation 16.
#cycles N
ITRAN
10 A
=
=1
IRIPPLE
10.1 A
(16)
And estimate the time needed to produce that number of cycles during a transient as Equation 17:
TTRANS N
#cycle
VOUT
1
1.8 V
l1 +
p = 1.4 Js
F1 +
G=
VIN :min ;
2 × 500 kHz
2 × fSW
4.5 V
(17)
The output capacitor must support the full change in output current for half of the time, so the minimum output
capacitance can be estimated by Equation 18:
Cundershoot =
ITRAN × TTRANS
10 A × 1.4 µs
=
= 193 µF
2 × VUnder
2 × 36 mV
(18)
The output capacitor must also absorb the full change in output current for half of the time needed to remove the
excess current from the inductor during a rapid load decrease. This minimum output capacitance can be
estimated using Equation 19:
Covershoot =
:ITRAN ;2 × L1 :10 A;2 × 320 nH
=
= 494 JF
VOUT × VOVER
1.8 V × 36 mV
(19)
In order to meet the transient response requirements, the output capacitance must be greater than the larger of
Cundershoot and Covershoot.
In this case, the highest minimum output capacitance (COUT(min)) to meet the response to a load transition is the
overshoot requirement, which dictates the minimum output capacitance. Therefore, using Equation 19, the
minimum output capacitance required to meet the transient requirement is 494 µF.
9.2.2.3.2 Output Voltage Ripple
The output voltage ripple is the second criterion. Equation 20 calculates the minimum output capacitance
required to meet the output voltage ripple specification. This criterion is the requirement when the impedance of
the output capacitance is dominated by ESR.
Cripple =
1
IRIPPLE
10.1 A
×
=
= 140 JF
8 × fSW VOUT :ripple ; 8 × 500 kHz × 18 mV
(20)
In this case, the maximum output voltage ripple is 18 mV. Under this requirement, the minimum output
capacitance for ripple (as calculated in Equation 20) yields 140 μF. Because this capacitance value is smaller
than the output capacitance required to meet the transient response, select the output capacitance value based
on the transient requirement. For this application, two 220-µF, low-ESR polymer bulk capacitors, three 47-µF
capacitors and three 22-µF ceramic capacitors are selected to meet the transient specification with at least 80%
margin. Therefore COUT equals 647 µF.
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With the target output capacitance value chosen, Equation 21 calculates the maximum ESR the output capacitor
bank can have to meet the output voltage ripple specification. Equation 21 indicates the ESR should be less than
1.4 mΩ. The six ceramic capacitors each contribute approximately 2 mΩ, making the effective ESR of the output
capacitor bank approximately 0.33 mΩ, meeting the specification with sufficient margin.
VOUT
ESRMAX =
ripple
-
IRIPPLE
8 × fSW × COUT
IRIPPLE
18 mV =
10.1 A
8 × 500 kHz × 647 JF
= 1.4 m3
10.1 A
(21)
Additional capacitance de-ratings for aging, temperature and DC bias should be factored in, which increases the
minimum required capacitance value. Capacitors generally have limits to the amount of ripple current they can
handle without failing or producing excess heat. An output capacitor that can support the inductor ripple current
must be specified. Some capacitor data sheets specify the RMS (root mean square) value of the maximum ripple
current. Equation 22 can be used to calculate the RMS ripple current the output capacitor needs to support. For
this application, Equation 22 yields 2.28 A.
ICO(rms ) =
VOUT × kVIN :max ; F VOUT o
¾12 × VIN :max ; × L1 × fSW
=
1.8 V × :18 V F 1.8 V;
¾12 × 18 V × 320 nH × 500 kHz
= 2.92 A
(22)
9.2.2.4 D-CAP Mode and D-CAP2 Mode Stability
D-CAP mode control requires that the ESR ripple at the FB pin be at least 15 mV (or 2.5%) of the output voltage
and the ESR-zero frequency of the output capacitor is less than 1/4 the switching frequency. Because this design
requires output voltage ripple less than 2.5% of the output voltage and uses low-ESR, specialty polymer, and
ceramic output capacitors, this design uses D-CAP2 mode control. Because D-CAP2 mode control uses an
internally generated ramp to emulate the ESR of the output capacitor, D-CAP2 mode requires sufficient output
capacitance to maintain an effective ESR-zero frequency less than 1/4 of the nominal switching frequency with
this emulated ESR. The minimum capacitance for stability can be calculated in Equation 23 using τIem from
Table 11:
Cstability =
2 × Vref × RIem
2 × 600 mV × 76 µs
=
= 100 JF
N × VOUT × L1 × fSW 3.14 × 1.8 V × 320 nH × 500 kHz
(23)
Table 11. D-CAP2 Mode Current Emulation Time
Constants
NOMINAL FREQUENCY (kHz)
τIem(µs)
250
104
300
98
400
87
500
76
650
60
750
52
850
44
1000
33
9.2.2.5 Input Capacitor Selection
The TPS544B20 and TPS544C20 devices require a capacitor with these features:
• high-quality
• ceramic
• type X5R or X7R
• input decoupling feature
• a value of 0.1 μF to 1.0 μF of effective capacitance on the VDD pin, relative to GND
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The power stage input decoupling capacitance (effective capacitance at the VIN and GND pins) must be
sufficient to supply the high switching currents demanded when the high-side MOSFET switches on, while
providing minimal input voltage ripple as a result. This effective capacitance includes any DC bias effects. The
voltage rating of the input capacitor must be greater than the maximum input voltage. The capacitor must also
have a ripple current rating greater than the maximum input current ripple to the device during full load. The input
ripple current can be calculated using Equation 24.
kVIN :min ; F VOUT o
VOUT
1.8 V :4.5 V F 1.8 V;
ICIN :rms ; = IOUT (max ) × ¨
×
= 30 A × ¨
×
= 14.7 Arms
4.5 V
4.5 V
VIN :min ;
VIN :min ;
(24)
The minimum input capacitance and ESR values for a given input voltage ripple specification, VIN(ripple), are
shown in Equation 25 and Equation 26. The input ripple is composed of a capacitive portion, VRIPPLE(cap), and a
resistive portion, VRIPPLE(esr).
CIN:min ; =
ESR CIN
max
IOUT (max ) × VOUT
30 A × 1.8 V
=
= 60 JF
Vripple :cap ; × VIN:max ; × fSW 100 mV × 18 V × 500 kHz
VRIPPLE
=
IOUT
max
ESR
1
+ 2 IRIPPLE
0.1 V
=
= 2.8 m3
1
30 A + 2 × 10.1 A
(25)
(26)
The value of a ceramic capacitor varies significantly with temperature and the amount of DC bias applied to the
capacitor. The capacitance variations due to temperature can be minimized by selecting a dielectric material that
is stable over temperature. X5R and X7R ceramic dielectric capacitors are usually selected for power regulator
capacitors because they have a high capacitance-to-volume ratio and are fairly stable during temperature
changes. The input capacitor must also be selected with the DC bias taken into account. To support the
maximum input voltage, this design requires a ceramic capacitor with a rating of at least 25 V. Allow 0.1-V input
ripple for VRIPPLE(cap), and 0.3-V input ripple for VRIPPLE(esr). Using Equation 25 and Equation 26, the minimum
input capacitance for this design is 60 µF, and the maximum ESR is 2.8 mΩ. Four 22-μF, 25-V ceramic
capacitors and two additional 100-μF, 25-V low-ESR polymer capacitors in parallel were selected for the power
stage. For the VDD pin, one 1.0-μF, 25-V ceramic capacitor was selected. The input voltage (VIN) and power
input voltage (PVIN) pins must be tied together. The input capacitance value determines the input ripple voltage
of the regulator. Using the design example values, IOUT(max) = 30 A, CIN = 288 μF, fSW = 500 kHz, yields a
maximum RMS input ripple current of 14.7 Arms.
9.2.2.6 Bootstrap Capacitor and Resistor Selection
A ceramic capacitor with a value of 0.1 μF must be connected between the BOOT and SW pins for proper
operation. It is recommended to use a ceramic capacitor with X5R or better grade dielectric. The capacitor
should have voltage rating of 25 V or higher. To reduce the dV/dt of the rising edge of the SW node, reduce
ringing and EMI, a resistor RBOOT up to 5 Ω can be placed in series with the bootstrap capacitor.
9.2.2.7 BP6, BP3 and BPEXT
This design does not include an auxiliary 5-V supply, so BPEXT is terminated to GND. According to the
recommendations in , BP3 is bypassed to AGND with 100 nF of capacitance, and BP6 is bypassed to GND with
4.7-µF of capacitance. In order for the regulator to function properly, it is important that these capacitors be
located close to the TPS544C20, with low-impedance return paths to AGND or GND as appropriate. See
Figure 45 for more information.
9.2.2.8 R-C Snubber and VIN Pin High-Frequency Bypass
Although it is possible to operate the TPS544C20 within absolute maximum ratings without including any ringing
reduction techniques, some designs may require external components to further reduce ringing levels. This
example uses two approaches:
• a high frequency power stage bypass capacitor on the VIN pins
• an R-C snubber between the SW and GND
56
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Including a high-frequency bypass capacitor is a lossless ringing reduction technique which helps minimizes the
outboard parasitic inductances in the power stage. These capacitors store energy during the low-side MOSFET
on-time, and discharge once the high-side MOSFET is turned on. For this example a 4.7-nF, 25-V, 0402 sized
high-frequency capacitor is selected. The placement of this capacitor (shown in Figure 46) is critical to its
effectiveness.
Additionally, an R-C snubber circuit is added to this example. To balance efficiency and spike levels, a 1-nF
capacitor and a 3-Ω resistor are chosen. In this example an 0805 resistor is chosen, which is rated for 0.125 W,
nearly twice the estimated power dissipation. Figure 33 and Figure 34 show the effect of the R-C snubber on the
rising edge of the SW pin. See SLUP100 for more information about snubber circuits.
VIN
VIN
SW
SW
VIN = 12 V
IOUT = 20 A
Snubber = 1nF + 3Ω
Figure 33. SW Rising Edge
VIN = 12 V
IOUT = 20 A
Snubber = Open
Figure 34. SW Rising Edge
9.2.2.9 Temperature Sensor
This application design uses a surface-mount MMBT3904SL for the temperature sensor, QT. In this example, the
sensor monitors the PCB temperature where it is generally the highest, next to the power inductor. Placement of
the temperature sensor and routing back to the TSNS pin are critical design features to reduce noise its
temperature measurements. In this example, the temperature sensor is placed on the VOUT side of the power
inductor to avoid switching noise from the SW plane, and routed back to the TSNS and AGND pin. Additionally, a
330-pF capacitor, CT, is placed from TSNS to AGND near the TSNS pin.
Disable external temperature sensing by terminating TSNS to AGND with a 0-Ω resistor. This termination forces
the temperature readings to –40 °C, and prevents external over-temperature fault trips.
9.2.2.10 Key PMBus Parameter Selection
Several of the key design parameters for the TPS544B20 and TPS544C20 device can be configured according
to the PMBus protocol, and stored to its non-volatile memory (NVM) for future use.
9.2.2.10.1 Enable, UVLO and Sequencing
Use the ON_OFF_CONFIG (02h) command to select the turn-on behavior of the converter. For this example, the
CNTL pin was used to enable or disable the converter, regardless of the state of OPERATION (01h), as long as
input voltage is present, and above the UVLO threshold.
The minimum input voltage, VIN(min) , for this example is 4.5 V. The VIN_ON command was set to 4.25 V, and the
VIN_OFF command was set to 4.0 V, giving 250 mV of hysteresis. If VIN falls below VIN_OFF, power conversion
stops, until it is raised above VIN_ON.
This example lacks specific turn-on or turn-off delay requirements, so SEQUENCE_TON_TOFF_DELAY was
used to set both the turn-on and turn-off delays to 0 × the soft-start time, the delay between enabling power
conversion, and the rise of the output voltage is approximately 400 µs. See the Soft-Start section for more
information.
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9.2.2.10.2 Soft-Start Time
The TON_RISE command sets the soft-start time. When selecting the soft-start time, consider the charging
current for the output capacitors. In some applications (for example those with large amounts of output
capacitance) this current can lead to problems with nuisance tripping of the overcurrent protection circuitry. To
avoid nuisance tripping, the output capacitor charging current should be included when choosing a soft-start
time, and overcurrent threshold. The capacitor charging current can be calculated using Equation 27.
ICAP =
VOUT × COUT 1.8 V × 647 JF
=
= 432 mA
t SS
2.7 ms
(27)
After calculating the charging current, the overcurrent threshold can then be calibrated to the sum of the
maximum load current and the output capacitor charging current plus some margin.
In this example, the soft-start time is arbitrarily selected to be the default value, 2.7 ms. In this case, the charging
current, ICAP = 337 mA.
9.2.2.10.3 Overcurrent Threshold and Response
The IOUT_OC_FAULT_LIMIT command sets the overcurrent threshold. The current limit should be set to the
maximum load current, plus the output capacitor charging current during start-up, plus some margin for load
transitions and component variation. The amount of margin required depends on the individual application, but a
suggested starting point is 30%. More or less may be required. For this application, the maximum load current is
30 A, the output capacitor charging current is 337 mA. This design uses the factory default overcurrent threshold
of 39 A.
The IOUT_OC_FAULT_RESPONSE command sets the desired response to an overcurrent event. In this
example, the converter is configured to latch-off in the event of an overcurrent. TPS544C20 device can also be
configured to hiccup, (continuously restart waiting for a 7 x soft-start time-out between re-trials. )
9.2.2.10.4 Power Good, Output Overvoltage and Undervoltage Protection
The PCT_VOUT_FAULT_PG_LIMIT command configures the PGOOD, and regulation windows. This example
includes a moderate threshold setting. The resulting power good window is ±12.5%, and the resulting
overvoltage and undervoltage window is ±16.8%. More or less aggressive protection levels can be selected
according to the PMBus protocol.
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9.2.2.11 Output Voltage Setting and Frequency Compensation Selection
A feedback divider from DIFFO to AGND sets the output voltage. This design arbitrarily selects an R1 value of
20 kΩ. Using R1 and the desired output voltage, and calculate RBIAS using Equation 28 to be 10 kΩ.
RBias =
VFB
0.6 V
× R1 =
× 20 k3 = 10 k3
VOUT - VFB
1.8 V - 0.6 V
(28)
The TPS544B20 and TPS544C20 devices use D-CAP2 mode control with a transconductance error amplifier to
eliminate the output voltage error introduced by valley voltage regulation. To stabilize the error amplifer, TI
recommends a 10-nF capacitor from COMP to AGND. To improve transient response and increase phase
margin, a series resistor, RCOMP, can be added. When using RCOMP, add a 1.0-nF capacitor from COMP to AGND
to limit the error amplifier gain at high frequency. Use Equation 29 to calculate the value of RCOMP.
R COMP = 3 ×
VOUT × L1
COUT
1.8 V × 320 nH 647 JF
×
=3×
×
= 2.45 k3
Vref × RIem CCOMP
0.600 V × 76 Js 10 nF
(29)
Alternatively, for output voltages 1.2 V and higher, a feedforward capacitor, C1, can be added in parallel with R1
from DIFFO to FB to provide similar improvement to transient response and phase margin. Use Equation 30 to
calculate the value of C1.
C1 =
VOUT × L1 COUT
1.8 V × 320 nH 647 JF
×
=
×
= 409 pF
R1
0.600 V × 76 Js 20 k3
Vref × RIem
(30)
The resulting design example frequency compensation values are:
• R1 = 20 kΩ
• RBIAS = 10 kΩ
• C1 = 420 pF
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Application Curves
100
100
95
95
90
90
Efficiency (%)
Efficiency (%)
9.2.3
www.ti.com
85
80
75
Output Voltage
70
65
0.6 V
0.8 V
1.0 V
1.2 V
1.8 V
2.5 V
0
5
10
15
75
Output Voltage
65
20
25
30
0
5
TA = 25 °C
RBOOT = 0 Ω
Figure 35. Power Efficiency vs. Load Current
0.8 V
1.0 V
1.2 V
1.8 V
2.5 V
10
15
20
25
Load Current (A)
C003
fSW = 500 kHz
Snubber = Open
0.6 V
3.3 V
60
Load Current (A)
VIN = 5 V
L = 410 nH
RDCR = 0.3 mΩ
80
70
3.3 V
60
85
VIN = 12 V
L = 410 nH
RDCR = 0.3 mΩ
fSW = 500 kHz
Snubber = Open
30
C003
TA = 25 °C
RBOOT = 0 Ω
Figure 36. Power Efficiency, VIN = 12 V
1.818
Output Voltage (V)
1.812
1.806
1.800
Input Voltage
1.794
1.788
5V
8V
12 V
15 V
18 V
1.782
0
5
10
15
20
25
Load Current (A)
Figure 37. Load Regulation
IOUT = 20 A
Figure 39. Shutdown from CNTL
60
C005
VIN = 12 V
VIN = 12 V
VIN = 12 V
30
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IOUT = 20 A
Figure 38. Startup from CNTL
VIN = 12 V
IOUT = 20 A
tRISE = 2.0 µs
Figure 40. Load Transition 10-A to 20-A
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VIN = 12 V
IOUT = 20 A
tFALL = 2.0 µs
VIN = 12 V
Figure 41. Load Transition 20-A to 10-A
VIN = 12 V
IOUT = 0 A
VPRE-BIAS= 900 mV
Figure 43. 50% Pre-Biased Start-Up
IOUT = 20 A
Figure 42. DC Ripple
VIN = 12 V
Natural Convection
IOUT = 20 A
fSW = 500 kHz
Figure 44. Thermal Image
10 Power Supply Recommendations
These devices operate from an input voltage supply between 4.5 V and 18 V. These devices are not designed
for split-rail operation. The VIN and VDD pins must be the same voltage for accurate high-side short circuit
protection. Proper bypassing of input supplies and internal regulators is also critical for noise performance, as is
PCB layout and grounding scheme. See the recommendations in the Layout section.
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11 Layout
11.1 Layout Guidelines
Layout is a critical portion of good power supply design. The following layout recommendations will help guide
you through a good layout of the TPS544B20 and TPS544C20 Devices. Figure 45 shows the recommended
PCB layout configuration for additional reference.
•
•
•
•
•
•
•
•
•
•
•
•
62
As with any switching regulator, there are several signal paths that conduct fast switching voltages or
currents. Minimize the loop area formed by these paths and their bypass connections.
Bypass the VIN pins to GND with a low-impedance path. Power-stage input bypass capacitors should be as
close as physically possible to the VIN and GND pins. Additionally, a high-frequency bypass capacitor on the
VIN pins can help to reduce switching spikes. See Figure 46 for placement recommendation.
The AGNDSNS pin must be kelvin connected to the AGND pin, with a low-noise, low-impedance path to
ensure accurate current monitoring. This connection must be made on an internal or bottom layer. It should
not segment the thermal tab copper area. This connection serves as the only connection between AGND and
GND for this device.
Signal components should be terminated or bypassed to a separate analog ground (AGND) copper area,
which is isolated from fast switching voltage and current paths. This copper area should not be connected to
the thermal tab, or to an internal ground plane, and should be reserved for this regulator only.
Minimize the SW copper area for best noise performance. Route sensitive traces away from SW and BOOT,
as these nets contain fast switching voltages, and lend easily to capacitive coupling.
Snubber component placement is critical to its effectiveness of ringing reduction. These components should
be on the same layer as the devices, and be kept as close as possible to the SW and GND copper areas.
Keep signal components and regulator bypass capacitors local to the device, and place them as close as
possible to the pins to which they are connected. These components include the feedback resistors,
frequency compensation, the RRT resistor, ADDR0 and ADDR1 resistors, as well as bypass capacitors for
BP3, BP6, VDD, and optionally BPEXT.
The VIN and VDD pins must be the same voltage for accurate short circuit protection, but high frequency
switching noise on the VDD pin can degrade performance. VDD should be connected to VIN through a trace
from the input copper area. To avoid high frequency noise on VDD, TI recommends keeping the VDD to VIN
connection as short as possible to keep the parasitic inductance low. Optionally form a small low-pass R-C
between VIN and VDD, with the VDD bypass capacitor (0.1 µF to 1.0 µF) and a 0-Ω to 2-Ω resistor between
VIN and VDD. See Figure 45.
The VDD bypass capacitor can conduct high frequency switching currents. Thus in practice, TI recommends
grounding the VDD bypass capacitor to GND or AGNDSNS rather than AGND. If AGNDSNS is used, to avoid
injecting noise into the regulation path, it is important to route the ground return of the bypass capacitor to
AGNDSNS through a dedicated trace to avoid sharing a path to AGND between the VDD capacitor and the
FB to AGND (Rbias) resistor and COMP to AGND (Ccomp) capacitor.
The TPS544B20 and TPS544C20 devices have several pins which require good local bypassing. Place
bypass capacitors as close as possible to the device pins, with a minimum return loop back to ground. Poor
bypassing on VDD, BP3 and BP6 can degrade the performance of the regulator.
Route the VOUTS+ and VOUTS– lines from the output capacitor bank at the load back to the device pins as
a tightly coupled differential pair. It is critical that these traces be kept away from switching or noisy areas
which can add differential-mode noise.
Routing of the temperature sensor traces is critical to the noise performance of temperature monitoring. Keep
these traces away from switching areas or high current paths on the layout. It is also recommended to use a
small 1-nF capacitor from TSNS to AGND to improve the noise performance of temperature readings.
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11.2 Layout Example
(Not to scale)
GND
AGND
AGND
VIN
DIFFO
VIN
VIN
VIN
VIN
VIN
BP3
C
C
FB
C
PGND
BP6
VDD
BPEXT
VOUTS-
R
VOUTS+
C
R
C
C
C
C
C
C
GND
Thermal Tab
GND
AGND
GND
MODE
GND
AGNDS
NS
GND
C
R
C
C
C
C
SW
SW
SW
SW
SW
BOOT
CLK
DATA
ADDR0
CNTL
ADDR1
SMBALERT
RT
R
R
GND
TSNS
R
SW
R
AGND is not connected to the
thermal tab or internal ground
plane. Kelvin connect to
AGNDSNS on another layer
C
GND
COMP
PGOOD
C
C
GND
C
Route to VOUTS+
and VOUTS- as a
differential pair
C
R R
VOUT
L
PMBus
Communication
QT
Minimize SW area. Keep
sensitive traces away from SW
and BOOT
Bottom-side
component
Figure 45. PCB Layout Recommendation
Vias connect
multiple VIN layers
TPS544B20/C20
No GND plane under SW node
2.2 nF to 4.7 nF 0402 VIN to
GND capacitor(s)
underneath VIN pins
Multiple vias connect to
wide ground plane(s)
Figure 46. High-Frequency Bypass Capacitor Placement
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Layout Example (continued)
11.2.1 Mounting and Thermal Profile Recommendation
Proper mounting technique adequately covers the exposed thermal tab with solder. Excessive heat during the
reflow process can affect electrical performance. Figure 47 shows the recommended reflow oven thermal profile.
Proper post-assembly cleaning is also critical to device performance. See SLUA271 for more information.
tP
Temperature (°C)
TP
TL
TS(max)
tL
TS(min)
rRAMP(up)
tS
rRAMP(down)
t25P
25
Time (s)
Figure 47. Recommended Reflow Oven Thermal Profile
Table 12. Recommended Thermal Profile Parameters
PARAMETER
MIN
TYP
MAX
UNIT
RAMP UP AND RAMP DOWN
rRAMP(up)
Average ramp-up rate, TS(max) to TP
3
°C/s
rRAMP(down)
Average ramp-down rate, TP to TS(max)
6
°C/s
PRE-HEAT
TS
Pre-Heat temperature
150
200
°C
tS
Pre-heat time, TS(min) to TS(max)
60
180
s
REFLOW
TL
Liquidus temperature
TP
Peak temperature
tL
Time maintained above liquidus temperature, TL
60
tP
Time maintained within 5 °C of peak temperature, TP
20
t25P
Total time from 25 °C to peak temperature, TP
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217
°C
260
°C
150
s
40
s
480
s
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12 Device and Documentation Support
12.1 Device Support
12.1.1 Development Support
12.1.1.1 Texas Instruments Fusion Digital Power™ Designer
The TPS544B20 and TPS544C20 devices are fully supported by Texas Instruments Digital Power Designer.
Fusion Digital Power Designer is a graphical user interface (GUI) used to configure and monitor the TPS544B20
and TPS544C20 devices according to the PMBus interface protocol via a Texas Instruments USB-to-GPIO
adapter.
Click this link to download the Texas Instruments Fusion Digital Power Designer software package.
Figure 48. Device Monitoring with Fusion Digital Power Designer
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Figure 49. Device Configuration with Fusion Digital Power Designer
12.1.2 Device Nomenclature
BUS HOGGING occurs when the operation of a device on a shared communication bus prevents the normal
communication of other devices on the shared bus for an excessive period of time.
12.2 Related Links
The table below lists quick access links. Categories include technical documents, support and community
resources, tools and software, and quick access to sample or buy.
Table 13. Related Links
PARTS
PRODUCT FOLDER
SAMPLE & BUY
TECHNICAL
DOCUMENTS
TOOLS &
SOFTWARE
SUPPORT &
COMMUNITY
TPS544B20
Click here
Click here
Click here
Click here
Click here
TPS544C20
Click here
Click here
Click here
Click here
Click here
12.3 Trademarks
SWIFT, NexFET, D-CAP, D-CAP2, Fusion Digital Power, E2E are trademarks of Texas Instruments.
PMBus is a trademark of SMIF, Inc..
All other trademarks are the property of their respective owners.
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12.4 Receiving Notification of Documentation Updates
To receive notification of documentation updates, navigate to the device product folder on ti.com. In the upper
right corner, click on Alert me to register and receive a weekly digest of any product information that has
changed. For change details, review the revision history included in any revised document.
12.5 Community Resources
The following links connect to TI community resources. Linked contents are provided "AS IS" by the respective
contributors. They do not constitute TI specifications and do not necessarily reflect TI's views; see TI's Terms of
Use.
TI E2E™ Online Community TI's Engineer-to-Engineer (E2E) Community. Created to foster collaboration
among engineers. At e2e.ti.com, you can ask questions, share knowledge, explore ideas and help
solve problems with fellow engineers.
Design Support TI's Design Support Quickly find helpful E2E forums along with design support tools and
contact information for technical support.
12.6 Electrostatic Discharge Caution
These devices have limited built-in ESD protection. The leads should be shorted together or the device placed in conductive foam
during storage or handling to prevent electrostatic damage to the MOS gates.
12.7 Glossary
SLYZ022 — TI Glossary.
This glossary lists and explains terms, acronyms, and definitions.
13 Mechanical, Packaging, and Orderable Information
The following pages include mechanical packaging and orderable information. This information is the most
current data available for the designated devices. These data is subject to change without notice and revision of
this document. For browser-based versions of this data sheet, refer to the left-hand navigation.
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PACKAGE OPTION ADDENDUM
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19-Jun-2021
PACKAGING INFORMATION
Orderable Device
Status
(1)
Package Type Package Pins Package
Drawing
Qty
Eco Plan
(2)
Lead finish/
Ball material
MSL Peak Temp
Op Temp (°C)
Device Marking
(3)
(4/5)
(6)
TPS544B20RVFR
ACTIVE
LQFN-CLIP
RVF
40
2500
RoHS-Exempt
& Green
NIPDAU
Level-2-260C-1 YEAR
-40 to 125
TPS544B20
TPS544B20RVFT
ACTIVE
LQFN-CLIP
RVF
40
250
RoHS-Exempt
& Green
NIPDAU
Level-2-260C-1 YEAR
-40 to 125
TPS544B20
TPS544C20RVFR
ACTIVE
LQFN-CLIP
RVF
40
2500
RoHS-Exempt
& Green
NIPDAU
Level-2-260C-1 YEAR
-40 to 125
TPS544C20
TPS544C20RVFT
ACTIVE
LQFN-CLIP
RVF
40
250
RoHS-Exempt
& Green
NIPDAU
Level-2-260C-1 YEAR
-40 to 125
TPS544C20
(1)
The marketing status values are defined as follows:
ACTIVE: Product device recommended for new designs.
LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect.
NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design.
PREVIEW: Device has been announced but is not in production. Samples may or may not be available.
OBSOLETE: TI has discontinued the production of the device.
(2)
RoHS: TI defines "RoHS" to mean semiconductor products that are compliant with the current EU RoHS requirements for all 10 RoHS substances, including the requirement that RoHS substance
do not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, "RoHS" products are suitable for use in specified lead-free processes. TI may
reference these types of products as "Pb-Free".
RoHS Exempt: TI defines "RoHS Exempt" to mean products that contain lead but are compliant with EU RoHS pursuant to a specific EU RoHS exemption.
Green: TI defines "Green" to mean the content of Chlorine (Cl) and Bromine (Br) based flame retardants meet JS709B low halogen requirements of