TPS54973PWP

Typical Size 6,4 mm X 9,7 mm TPS54973 www.ti.com SLVS453A − FEBRUARY 2003 − REVISED FEBRUARY 2005 3-V TO 4-V INPUT, 9-A OUTPUT SYNCHRONOUS BUCK SWITCHER WITH DISABLED SINKING DURING START-UP FEATURES D 15-mΩ MOSFET Switches for High Efficiency D D D D APPLICATIONS D Low-Voltage, High-Density Distributed Power D Systems Point of Load Regulation for High Performance DSPs, FPGAs, ASICs and Microprocessors Broadband, Networking and Optical Communications Infrastructure Power PC Series Processors D D TYPICAL APPLICATION I/O Supply VIN * As a member of the SWIFT™ family of dc/dc regulators, the TPS54973 low-input voltage high-output current synchronous buck PWM converter integrates all required active components. Included on the substrate with the listed features are a true, high performance, voltage error amplifier that enables maximum performance and flexibility in choosing the output filter L and C components; an undervoltage-lockout circuit to prevent start-up until the input voltage reaches 3 V; an internally or externally set slow-start circuit to limit in-rush currents; and a power good output useful for processor/logic reset, fault signaling, and supply sequencing. For reliable power up in output precharge applications, the TPS54973 is designed to only source current during startup. The TPS54973 is available in a thermally enhanced 28-pin TSSOP (PWP) PowerPAD™ package, which eliminates bulky heatsinks. TI provides evaluation modules and the SWIFT™ designer software tool to aid in quickly achieving high-performance power supply designs to meet aggressive equipment development cycles. * PH TPS54973 BOOT PGND VSENSE VBIAS AGND COMP * Optional START-UP WAVEFORM RL = 1 Ω Core Supply VI/O = 3.3 V 1 V/div D D at 9-A Continuous Output Source or Sink Current Disabled Current Sinking During Start-Up 0.9-V to 2.5-V Adjustable Output Voltage Range With 1.0% Accuracy Wide PWM Frequency: Fixed 350 kHz, 550 kHz or Adjustable 280 kHz to 700 kHz Synchronizable to 700 kHz Load Protected by Peak Current Limit and Thermal Shutdown Integrated Solution Reduces Board Area and Component Count DESCRIPTION V(core) = 1.8 V t − Time − 10 ms/div Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet. PowerPAD and SWIFT are trademarks of Texas Instruments. PRODUCTION DATA information is current as of publication date. Products conform to specifications per the terms of Texas Instruments standard warranty. Production processing does not necessarily include testing of all parameters. Copyright © 2002−2003, Texas Instruments Incorporated TPS54973 www.ti.com SLVS453A − FEBRUARY 2003 − REVISED FEBRUARY 2005 These devices have limited built-in ESD protection. The leads should be shorted together or the device placed in conductive foam during storage or handling to prevent electrostatic damage to the MOS gates. ORDERING INFORMATION TA OUTPUT VOLTAGE PACKAGE PART NUMBER −40°C to 85°C 0.9 V to 2.5 V Plastic HTSSOP (PWP)(1) TPS54973PWP (1) The PWP package is also available taped and reeled. Add an R suffix to the device type (i.e., TPS54973PWPR). See the application section of the data sheet for PowerPAD drawing and layout information. (2) For the most current package and ordering information, see the Package Option Addendum at the end of this document, or see the TI website at www.ti.com. ABSOLUTE MAXIMUM RATINGS over operating free-air temperature range unless otherwise noted(1) TPS54973 VIN Input voltage range, VI −0.3 V to 4.5 V SS/ENA, SYNC −0.3 V to 7 V RT −0.3 V to 6 V VSENSE Output voltage range, range VO Source current, current IO −0.3 V to 4V BOOT −0.3 V to 10 V VBIAS, COMP, PWRGD −0.3 V to 7 V PH −0.6 V to 6 V PH Internally limited COMP, VBIAS Sink current, IS Voltage differential 6 mA PH 16 A COMP 6 mA SS/ENA, PWRGD 10 mA AGND to PGND ±0.3 V Operating virtual junction temperature range, TJ −40°C to 125°C Storage temperature, Tstg −65°C to 150°C Lead temperature 1,6 mm (1/16 inch) from case for 10 seconds (1) 300°C Stresses beyond those listed under “absolute maximum ratings” may cause permanent damage to the device. These are stress ratings only, and functional operation of the device at these or any other conditions beyond those indicated under “recommended operating conditions” is not implied. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability. RECOMMENDED OPERATING CONDITIONS MIN MAX UNIT 3 4 V −40 125 °C Input voltage, VI Operating junction temperature, TJ NOM DISSIPATION RATINGS(1)(2) (1) PACKAGE THERMAL IMPEDANCE JUNCTION-TO-AMBIENT TA = 25°C POWER RATING TA = 70°C POWER RATING TA = 85°C POWER RATING 28 Pin PWP with solder 14.4 °C/W 6.94 W(3) 3.81 W 2.77 W 28 Pin PWP without solder 27.9 °C/W 3.58 W 1.97 W 1.43 W For more information on the PWP package, refer to TI technical brief, literature number SLMA002. (2) Test board conditions: 1. 3” x 3”, 4 layers, thickness: 0.062” 2. 1.5 oz. copper traces located on the top of the PCB 3. 1.5 oz. copper ground plane on the bottom of the PCB 4. 0.5 oz. copper ground planes on the two internal layers 5. 12 thermal vias (see “Recommended Land Pattern” in applications section of this data sheet) (3) Maximum power dissipation may be limited by over current protection. 2 TPS54973 www.ti.com SLVS453A − FEBRUARY 2003 − REVISED FEBRUARY 2005 ELECTRICAL CHARACTERISTICS TJ = −40°C to 125°C, VI = 3 V to 4 V (unless otherwise noted) PARAMETER TEST CONDITIONS MIN TYP MAX UNIT SUPPLY VOLTAGE, VIN Input voltage range, VIN I(Q) 3.0 Quiescent current 4.0 fs = 350 kHz, SYNC ≤ 0.8 V, RT open, PH pin open 9.8 17 fs = 550 kHz, SYNC ≥ 2.5 V, RT open, PH pin open 14 23 1 1.4 2.95 3.0 Shutdown, SS/ENA = 0 V V mA UNDER VOLTAGE LOCK OUT Start threshold voltage, UVLO V Stop threshold voltage, UVLO 2.70 2.80 V Hysteresis voltage, UVLO 0.14 0.16 V 2.5 µs Rising and falling edge deglitch, UVLO(1) BIAS VOLTAGE Output voltage, VBIAS I(VBIAS) = 0 2.70 2.80 Output current, VBIAS (2) 2.90 V 100 µA CUMULATIVE REFERENCE Vref Accuracy 0.882 0.891 0.900 V REGULATION Line regulation(1)(3) Load regulation(1)(3) IL = 3 A, fs = 350 kHz, TJ = 85°C 0.04 IL = 3 A, fs = 550 kHz, TJ = 85°C 0.04 IL = 0 A to 6 A, fs = 350 kHz, TJ = 85°C 0.03 IL = 0 A to 6 A, fs = 550 kHz, TJ = 85°C 0.03 %/V %/A OSCILLATOR Internally set—free set free running frequency Externally set set—free free running frequency range High level threshold, SYNC SYNC ≤ 0.8 V, RT open 280 350 420 SYNC ≥ 2.5 V, RT open 440 550 660 RT = 180 kΩ (1% resistor to AGND) 252 280 308 RT = 100 kΩ (1% resistor to AGND) 460 500 540 RT = 68 kΩ (1% resistor to AGND) 663 700 762 2.5 Frequency range, SYNC(1) 0.8 50 Ramp amplitude (peak-to-peak)(1) Minimum controllable on time(1) Maximum duty cycle V ns 330 Ramp valley(1) kHz V Low level threshold, SYNC Pulse duration, external synchronization, SYNC(1) kHz 700 kHz 0.75 V 1 V 200 ns 90% (1) Specified by design Static resistive loads only (3) Specified by the circuit used in Figure 9 (2) 3 TPS54973 www.ti.com SLVS453A − FEBRUARY 2003 − REVISED FEBRUARY 2005 ELECTRICAL CHARACTERISTICS (continued) TJ = −40°C to 125°C, VI = 3 V to 4 V (unless otherwise noted) PARAMETER TEST CONDITIONS MIN TYP MAX UNIT ERROR AMPLIFIER Error amplifier open loop voltage gain 1 kΩ COMP to AGND(1) 90 110 Error amplifier unity gain bandwidth Parallel 10 kΩ, 160 pF COMP to AGND(1) 3 5 Error amplifier common mode input voltage range Powered by internal LDO(1) 0 Input bias current, VSENSE VSENSE = Vref Output voltage slew rate (symmetric), COMP VBIAS 60 1.0 dB MHz 250 1.4 V nA V/µs PWM COMPARATOR PWM comparator propagation delay time, PWM comparator input to PH pin (excluding deadtime) 10-mV overdrive(1) 70 85 ns 1.20 1.40 V SLOW-START/ENABLE Enable threshold voltage, SS/ENA 0.82 Enable hysteresis voltage, SS/ENA Falling edge deglitch, 0.03 SS/ENA(1) V 2.5 Internal slow-start time Charge current, SS/ENA SS/ENA = 0 V Discharge current, SS/ENA SS/ENA = 1.3 V, VI = 1.5 V µs 2.6 3.35 4.1 ms 3 5 8 µA 2.0 2.3 4.0 mA POWER GOOD Power good threshold voltage VSENSE falling Power good hysteresis voltage(1) Power good falling edge deglitch(1) Output saturation voltage, PWRGD I(sink) = 2.5 mA Leakage current, PWRGD VI = 5.5 V 90 %Vref 3 %Vref 35 µs 0.18 0.3 V 1 µA CURRENT LIMIT Current limit trip point VI = 3.3 V Output shorted(1) 15 A Current limit leading edge blanking time 11 100 ns Current limit total response time 200 ns THERMAL SHUTDOWN Thermal shutdown trip point(1) Thermal shutdown 135 hysteresis(1) 150 165 10 °C °C OUTPUT POWER MOSFETS rDS(on) (1) P Power MOSFET switches it h VI = 3.0 V(4) 15 30 VI = 3.6 V(4) 14 28 Specified by design Static resistive loads only (3) Specified by the circuit used in Figure 9 (4) Matched MOSFETs low-side r DS(on) production tested, high-side rDS(on) specified by design (2) 4 mΩ Ω TPS54973 www.ti.com SLVS453A − FEBRUARY 2003 − REVISED FEBRUARY 2005 PWP PACKAGE (TOP VIEW) AGND VSENSE COMP PWRGD BOOT PH PH PH PH PH PH PH PH PH 1 2 3 4 5 6 7 8 9 10 11 12 13 14 28 27 26 25 24 23 THERMAL 22 PAD 21 20 19 18 17 16 15 RT SYNC SS/ENA VBIAS VIN VIN VIN VIN VIN PGND PGND PGND PGND PGND TERMINAL FUNCTIONS TERMINAL NAME NO. DESCRIPTION AGND 1 Analog ground. Return for compensation network/output divider, slow-start capacitor, VBIAS capacitor, RT resistor and SYNC pin. Connect PowerPAD to AGND. BOOT 5 Bootstrap output. 0.022-µF to 0.1-µF low-ESR capacitor connected from BOOT to PH generates floating drive for the high-side FET driver. COMP 3 Error amplifier output. Connect frequency compensation network from COMP to VSENSE PGND 15−19 Power ground. High current return for the low-side driver and power MOSFET. Connect PGND with large copper areas to the input and output supply returns, and negative terminals of the input and output capacitors. A single point connection to AGND is recommended. PH 6−14 Phase output. Junction of the internal high-side and low-side power MOSFETs, and output inductor. PWRGD 4 Power good open drain output. High when VSENSE ≥ 90% Vref, otherwise PWRGD is low. Note that output is low when SS/ENA is low, or the internal shutdown signal is active. RT 28 Frequency setting resistor input. Connect a resistor from RT to AGND to set the switching frequency. When using the SYNC pin, set the RT value for a frequency at or slightly lower than the external oscillator frequency. SS/ENA 26 Slow-start/enable input/output. Dual function pin which provides logic input to enable/disable device operation and capacitor input to externally set the start-up time. SYNC 27 Synchronization input. Dual function pin which provides logic input to synchronize to an external oscillator or pin select between two internally set switching frequencies. When used to synchronize to an external signal, a resistor must be connected to the RT pin. VBIAS 25 Internal bias regulator output. Supplies regulated voltage to internal circuitry. Bypass VBIAS pin to AGND pin with a high quality, low-ESR 0.1-µF to 1.0-µF ceramic capacitor. 20−24 Input supply for the power MOSFET switches and internal bias regulator. Bypass VIN pins to PGND pins close to device package with a high quality, low-ESR 10-µF ceramic capacitor. VIN VSENSE 2 Error amplifier inverting input. Connect to output voltage through compensation network/output divider. 5 TPS54973 www.ti.com SLVS453A − FEBRUARY 2003 − REVISED FEBRUARY 2005 INTERNAL BLOCK DIAGRAM VBIAS AGND VIN Enable Comparator SS/ENA 1.2 V Hysteresis: 0.03 V Falling Edge Deglitch 2.5 µs VIN UVLO Comparator VIN 2.95 V Hysteresis: 0.16 V ILIM Comparator Thermal Shutdown 150°C Internal/External Slow-Start (Internal Slow-Start Time = 3.35 ms 100 ns SHUTDOWN BOOT 15 mΩ Start-Up Driver Suppression SS_DIS PH + − R Q Error Amplifier Reference VREF = 0.891 V VIN Leading Edge Blanking Falling and Rising Edge Deglitch 2.5 µs REG VBIAS SHUTDOWN S PWM Comparator CO Adaptive Dead-Time and Control Logic VIN 15 mΩ PGND OSC Powergood Comparator VSENSE 0.90 Vref TPS54973 Hysteresis: 0.03 Vref VSENSE 6 COMP RT SYNC SHUTDOWN LOUT Falling Edge Deglitch 35 µs PWRGD VO TPS54973 www.ti.com SLVS453A − FEBRUARY 2003 − REVISED FEBRUARY 2005 25 20 INTERNALLY SET OSCILLATOR FREQUENCY vs JUNCTION TEMPERATURE DRAIN-SOURCE ON-STATE RESISTANCE vs JUNCTION TEMPERATURE VIN = 3.0 V IO = 9 A 15 10 5 0 −40 0 25 85 TJ − Junction Temperature − °C 125 f − Internally Set Oscillator Frequency − kHz Drain Source On-State Reststance − m Ω TYPICAL CHARACTERISTICS 750 650 SYNC ≥ 2.5 V 550 450 SYNC ≤ 0.8 V 350 250 −40 0 25 Figure 1 VI = 3.3 V TJ = 125°C 7 RT = 68 k 600 500 RT = 100 k 400 300 0.893 Device Power Losses − W 700 0.891 0.889 0.887 6 5 4 3 2 1 RT = 180 k 0.885 25 85 125 0 −40 0 25 85 TJ − Junction Temperature − °C Figure 3 140 RL = 10 kΩ, CL = 160 pF, TA = 25°C 120 0.893 100 Gain − dB 0.891 0.889 Phase 6 Gain 0.885 3.5 3.6 −20 −80 −140 −180 10 100 −200 1 k 10 k 100 k 1 M 10 M f − Frequency − Hz Figure 7 12 14 16 3.80 −40 −160 1 10 −20 −120 40 8 INTERNAL SLOW-START TIME vs JUNCTION TEMPERATURE 0 −100 60 0 Figure 6 4 Figure 5 −60 80 20 0.887 3.2 3.3 3.4 VI − Input Voltage − V 2 IL − Load Current − A ERROR AMPLIFIER OPEN LOOP RESPONSE 0.895 3.1 0 Figure 4 OUTPUT VOLTAGE REGULATION vs INPUT VOLTAGE 3 125 Phase − Degrees 0 Internal Slow-Start Time − ms 200 −40 TJ − Junction Temperature − °C VO − Output Voltage Regulation − V DEVICE POWER LOSSES vs LOAD CURRENT 8 0.895 800 125 Figure 2 VOLTAGE REFERENCE vs JUNCTION TEMPERATURE V ref − Voltage Reference − V f − Externally Set Oscillator Frequency − kHz EXTERNALLY SET OSCILLATOR FREQUENCY vs JUNCTION TEMPERATURE 85 TJ − Junction Temperature − °C 3.65 3.50 3.35 3.20 3.05 2.90 2.75 −40 0 25 85 125 TJ − Junction Temperature − °C Figure 8 7 TPS54973 www.ti.com SLVS453A − FEBRUARY 2003 − REVISED FEBRUARY 2005 APPLICATION INFORMATION Figure 9 shows the schematic diagram for a typical TPS54973 application. The TPS54973 (U1) can provide up to 9 A of output current at a nominal output voltage of 0.9 V to 2.5 V, and for this application, the output voltage U1 TPS54973 R6 28 71.5 kΩ 27 C6 1 µF VIN R1 R3 10 kΩ C1 470 pF R2 26 0.047 µF C3 10 kΩ C2 is set at 2.5 V and the input voltage is 3.3 V. For proper operation, the PowerPAD underneath the integrated circuit TPS54973 must be soldered properly to the printed-circuit board. 25 10 kΩ R5 C4 4 3 RT VIN VIN SYNCH VIN VIN SS/ENA VIN PH VBIAS PH PH PWRGD PH PH PH COMP PH 470 pF PH 12 pF PH 2 301 Ω VSENSE BOOT PGND R4 5.49 kΩ PGND 1 PGND AGND PGND PGND PwrPad 24 23 22 21 C5 C7 C8 0.1 µF 22 µF 22 µF 22 µF C12 10 µF 10 µF VIN 3.3 V 20 14 13 12 11 10 9 8 7 6 19 1 A, 200 V D1 C9 5 0.047 µF 18 17 1 A, 200 V D2 16 15 VOUT 2.5 V C13 C10 R7 L1 0.65 µH 2.4 kΩ C11 3300 pF Figure 9. Application Circuit COMPONENT SELECTION The values for the components used in this design example are selected for low output ripple and small PCB area. Ceramic capacitors are utilized in the output filter circuit. A small size, small value output inductor is also used. Compensation network components are chosen to maximize closed loop bandwidth and provide good transient response characteristics. Additional design information is available at www.ti.com. INPUT VOLTAGE The input voltage is a nominal 3.3 VDC. The input filter (C12) is a 10-µF ceramic capacitor (Taiyo Yuden). C10, also a 10-µF ceramic capacitor (Taiyo Yuden) that provides high frequency decoupling of the TPS54973 from 8 the input supply, must be located as close as possible to the device. Ripple current is carried in both C10 and C12, and the return path to PGND should avoid the current circulating in the output capacitors C5, C7, C8 and C13. FEEDBACK CIRCUIT The values for these components are selected to provide fast transient response times. R1, R2, R3, R4, C1, C2, and C4 forms the loop-compensation network for the circuit. For this design, a Type 3 topology is used. The transfer function of the feedback network is chosen to provide maximum closed loop gain available with open loop characteristics of the internal error amplifier. Closed loop crossover frequency is typically between 80 kHz at 3.3 V input. TPS54973 www.ti.com SLVS453A − FEBRUARY 2003 − REVISED FEBRUARY 2005 OPERATING FREQUENCY In the application circuit, the RT pin is grounded through a 71.5-kΩ resistor (R6) to select the operating frequency of 700 kHz. To set a different frequency, place a 68-kΩ to 180-kΩ resistor between RT (pin 28) and analog ground or leave RT floating to select the default of 350 kHz. The resistance can be approximated using the following equation: R+ 500 kHz Switching Frequency 100 [kW] (1) OUTPUT FILTER The output filter is composed of a 0.65-µH inductor (L1) and 3 x 22-µF capacitors (C5, C7, and C8). The inductor is a low dc resistance (.017 Ω) type, Pulse PA0277 0.65 µH. The capacitors used are 22-µF, 6.3-V ceramic types with X5R dielectric. An additional high frequency bypass capacitor, C13 is also used. PRECHARGE CIRCUIT VIN precharges the output of the application circuit through series diodes (D1 and D2) during start-up. As the input voltage increases at start-up, the output is precharged to VIN minus the forward bias voltage of the two diodes. When the internal reference has ramped up to a value greater than the voltage fed back to the VSENSE pin, the output of the internal error amplifier begins to increase. When this output reaches the maximum ramp amplitude, the output of the PWM comparator reaches 100 percent duty cycle, and the internal logic enables the high-side FET driver, and switching begins. The output tracks the internal reference until the preset output voltage is reached. Under no circumstances should the precharge voltage be allowed to increase above the preset output value. PCB LAYOUT Figure 10 shows a generalized PCB layout guide for the TPS54973 The VIN pins are connected together on the printed-circuit board (PCB) and bypassed with a low-ESR ceramic-bypass capacitor. Care should be taken to minimize the loop area formed by the bypass capacitor connections, the VIN pins, and the TPS54873 ground pins. The minimum recommended bypass capacitance is 10-µF ceramic capacitor with a X5R or X7R dielectric and the optimum placement is closest to the VIN pins and the PGND pins. The TPS54973 has two internal grounds (analog and power). Inside the TPS54973, the analog ground ties to all of the noise sensitive signals, while the power ground ties to the noisier power signals. Noise injected between the two grounds can degrade the performance of the TPS54973, particularly at higher output currents. Ground noise on an analog ground plane can also cause problems with some of the control and bias signals. For these reasons, separate analog and power ground traces are recommended. There is an area of ground on the top layer directly under the IC, with an exposed area for connection to the PowerPAD. Use vias to connect this ground area to any internal ground planes. Additional vias are also used at the ground side of the input and output filter capacitors. The AGND and PGND pins are tied to the PCB ground by connecting them to the ground area under the device as shown. The only components that tie directly to the power ground plane are the input capacitors, the output capacitors, the input voltage decoupling capacitor, and the PGND pins of the TPS54973. Use a separate wide trace for the analog ground signal path. The analog ground is used for the voltage set point divider, timing resistor RT, slow-start capacitor and bias capacitor grounds. Connect this trace directly to AGND (Pin 1). The PH pins are tied together and routed to the output inductor. Since the PH connection is the switching node, the inductor is located close to the PH pins. The area of the PCB conductor is minimized to prevent excessive capacitive coupling. Connect the boot capacitor between the phase node and the BOOT pin as shown Keep the boot capacitor close to the IC and minimize the conductor trace lengths. Connect the output filter capacitor(s) as shown between the VOUT trace and PGND. It is important to keep the loop formed by the PH pins, LOUT, COUT and PGND as small as practical. Place the compensation components from the VOUT trace to the VSENSE and COMP pins. Do not place these components too close to the PH trace. Due to the size of the IC package and the device pin-out, they must be routed close, but maintain as much separation as possible while still keeping the layout compact. Connect the bias capacitor from the VBIAS pin to analog ground using the isolated analog ground trace. If a slow-start capacitor or RT resistor is used, or if the SYNC pin is used to select 350-kHz operating frequency, connect them to this trace. If pre−charge diodes are used, keep the path from the voltage source to the output filter capacitor short. Make sure the etch is wide enough to carry the pre−charge current. 9 TPS54973 www.ti.com SLVS453A − FEBRUARY 2003 − REVISED FEBRUARY 2005 OPTIONAL PRE−CHARGE DIODES ANALOG GROUND TRACE FREQUENCY SET RESISTOR AGND RT SYNC VSENSE COMPENSATION NETWORK COMP SLOW START CAPACITOR SS/ENA BIAS CAPACITOR PWRGD BOOT CAPACITOR BOOT PH VOUT PH OUTPUT INDUCTOR OUTPUT FILTER CAPACITOR VBIAS VIN EXPOSED POWERPAD AREA VIN PH VIN PH VIN PH VIN PH PGND PH PGND PH PGND PH PGND PH PGND VIN INPUT BYPASS CAPACITOR INPUT BULK FILTER TOPSIDE GROUND AREA VIA to Ground Plane Figure 10. TPS54973 PCB Layout 10 TPS54973 www.ti.com SLVS453A − FEBRUARY 2003 − REVISED FEBRUARY 2005 LAYOUT CONSIDERATIONS FOR THERMAL PERFORMANCE For operation at full rated load current, the analog ground plane must provide adequate heat dissipating area. A 3 inch by 3 inch plane of 1 ounce copper is recommended, though not mandatory, depending on ambient temperature and airflow. Most applications have larger areas of internal ground plane available, and the PowerPAD should be connected to the largest area available. Additional areas on the top or bottom layers also help dissipate heat, and 8 PL Ø 0.0130 4 PL Ø 0.0180 Connect Pin 1 to Analog Ground Plane in This Area for Optimum Performance any area available should be used when 9 A or greater operation is desired. Connection from the exposed area of the PowerPAD to the analog ground plane layer should be made using 0.013 inch diameter vias to avoid solder wicking through the vias. Eight vias should be in the PowerPAD area with four additional vias located under the device package. The size of the vias under the package, but not in the exposed thermal pad area, can be increased to 0.018. Additional vias beyond the ten recommended that enhance thermal performance should be included in areas not under the device package. Minimum Recommended Thermal Vias: 8 x 0.013 Diameter Inside Powerpad Area 4 x 0.018 Diameter Under Device as Shown. Additional 0.018 Diameter Vias May Be Used if Top Side Analog Ground Area Is Extended. 0.06 0.0150 0.0339 0.0650 0.0500 0.3820 0.3478 0.0500 0.0500 0.2090 0.0256 0.0650 0.0339 0.1700 Minimum Recommended Top Side Analog Ground Area 0.1340 Minimum Recommended Exposed Copper Area for Powerpad. 5-mil Stencils May Require 10 Percent Larger Area 0.0630 0.0400 Figure 11. Recommended Land Pattern for 28-Pin PWP PowerPAD 11 TPS54973 www.ti.com SLVS453A − FEBRUARY 2003 − REVISED FEBRUARY 2005 PERFORMANCE GRAPHS Data shown is for the circuit in Figure 9 with precharge disabled (D1 and D2 removed) except for slow-start timing of Figure 18. All data is for VI = 3.3 V, VO = 2.5 V, fs = 700 kHz and TA = 25°C, unless otherwise specified. EFFICIENCY vs OUTPUT CURRENT 100 1.81 VI = 3.3 V 80 75 70 65 60 1.806 1.804 1.802 1.8 1.798 1.796 1.794 55 1.792 50 1.79 0 2 4 6 8 VI = 3.3 V 10 1.8 IO = 4.5 A 1.798 1.796 IO = 9 A 1.794 2 4 6 8 IO − Output Current − A 10 3 3.25 180 Phase 60 10 30 0 0 105 95 85 75 65 −10 −30 −20 −60 −30 −90 35 −40 −120 1M 25 10 k 100 k 55 2 V/div 90 OUTPUT AND INPUT RIPPLE fs = 700 kHz, TJ = 125°C, VI = 3.3 V, VO = 1.8 V 115 120 45 0 f − Frequency − Hz 2 4 6 8 10 12 14 IO − Output Current − A Figure 15 16 t − Time − 1 µs/div Figure 16 Figure 17 LOAD TRANSIENT RESPONSE SLOW-START TIMING 20 mV/div I = 2.25 A to 6.75 A 1 V/div VI/O = 3.3 V 2 V/div V(core) = 1.8 V t − Time −100 µs/div Figure 18 (1) 12 4 210 mV/div 30 150 Ambient Temperature − ° C Gain 40 Phase − Degrees 50 125 3.75 Figure 14 AMBIENT TEMPERATURE vs LOAD CURRENT(1) LOOP RESPONSE 3.5 VI − Input Voltage − V Figure 13 60 Gain − dB IO = 0 A 1.802 1.79 0 Figure 12 1k 1.804 1.792 IO − Output Current − A 100 1.806 100 mV/div 85 20 1.81 VO − Output Voltage − V VO − Output Voltage − V 90 OUTPUT VOLTAGE vs INPUT VOLTAGE 1.808 1.808 95 Efficiency − % OUTPUT VOLTAGE vs OUTPUT CURRENT Safe operating area is applicable to the test board conditions in the Dissipation Ratings t − Time − 10 ms/div Figure 19 TPS54973 www.ti.com SLVS453A − FEBRUARY 2003 − REVISED FEBRUARY 2005 DETAILED DESCRIPTION DISABLED SINKING DURING START-UP (DSDS) The DSDS feature enables minimal voltage drooping of output precharge capacitors at start-up. The TPS54973 is designed to disable the low-side MOSFET to prevent sinking current from a precharge output capacitor during start-up. Once the high-side MOSFET has been turned on to the maximum duty cycle limit, the low-side MOSFET is allowed to switch. Once the maximum duty cycle condition is met, the converter functions as a sourcing converter until the SS/ENA is pulled low. UNDERVOLTAGE LOCK OUT (UVLO) The TPS54973 incorporates an undervoltage lockout circuit to keep the device disabled when the input voltage (VIN) is insufficient. During power up, internal circuits are held inactive until VIN exceeds the nominal UVLO threshold voltage of 2.95 V. Once the UVLO start threshold is reached, device start-up begins. The device operates until VIN falls below the nominal UVLO stop threshold of 2.8 V. Hysteresis in the UVLO comparator and a 2.5-µs rising and falling edge deglitch circuit reduce the likelihood of shutting the device down due to noise on VIN. SLOW-START/ENABLE (SS/ENA) The slow-start/enable pin provides two functions. First, the pin acts as an enable (shutdown) control by keeping the device turned off until the voltage exceeds the start threshold voltage of approximately 1.2 V. When SS/ENA exceeds the enable threshold, device start-up begins. The reference voltage fed to the error amplifier is linearly ramped up from 0 V to 0.891 V in 3.35 ms. Similarly, the converter output voltage reaches regulation in approximately 3.35 ms. Voltage hysteresis and a 2.5-µs falling edge deglitch circuit reduce the likelihood of triggering the enable due to noise. The second function of the SS/ENA pin provides an external means of extending the slow-start time with a low-value capacitor connected between SS/ENA and AGND. Adding a capacitor to the SS/ENA pin has two effects on start-up. First, a delay occurs between release of the SS/ENA pin and start-up of the output. The delay is proportional to the slow-start capacitor value and lasts until the SS/ENA pin reaches the enable threshold. The start-up delay is approximately: t +C d (SS) (2) 1.2 V 5 mA Second, as the output becomes active, a brief ramp-up at the internal slow-start rate may be observed before the externally set slow-start rate takes control and the output rises at a rate proportional to the slow-start capacitor. The slow-start time set by the capacitor is approximately: t (SS) +C (SS) (3) 0.7 V 5 mA The actual slow-start time is likely to be less than the above approximation due to the brief ramp-up at the internal rate. The low side MOSFET is off during the slow-start sequence. VBIAS REGULATOR (VBIAS) The VBIAS regulator provides internal analog and digital blocks with a stable supply voltage over variations in junction temperature and input voltage. A high quality, low-ESR, ceramic bypass capacitor is required on the VBIAS pin. X7R or X5R grade dielectrics are recommended because their values are more stable over temperature. The bypass capacitor must be placed close to the VBIAS pin and returned to AGND. External loading on VBIAS is allowed, with the caution that internal circuits require a minimum VBIAS of 2.70 V, and external loads on VBIAS with ac or digital switching noise may degrade performance. The VBIAS pin may be useful as a reference voltage for external circuits. VOLTAGE REFERENCE The voltage reference system produces a precise Vref signal by scaling the output of a temperature stable bandgap circuit. During manufacture, the bandgap and scaling circuits are trimmed to produce 0.891 V at the output of the error amplifier, with the amplifier connected as a voltage follower. The trim procedure adds to the high precision regulation of the TPS54973, since it cancels offset errors in the scale and error amplifier circuits. OSCILLATOR AND PWM RAMP The oscillator frequency can be set to internally fixed values of 350 kHz or 550 kHz using the SYNC pin as a static digital input. If a different frequency of operation is required for the application, the oscillator frequency can be externally adjusted from 280 to 700 kHz by connecting a resistor between the RT pin and AGND and floating the SYNC pin. The switching frequency is approximated by the following equation, where R is the resistance from RT to AGND: Switching Frequency + 100 kW R 500 [kHz] (4) 13 TPS54973 www.ti.com SLVS453A − FEBRUARY 2003 − REVISED FEBRUARY 2005 External synchronization of the PWM ramp is possible over the frequency range of 330 kHz to 700 kHz by driving a synchronization signal into SYNC and connecting a resistor from RT to AGND. Choose a resistor between the RT and AGND which sets the free running frequency to 80% of the synchronization signal. The following table summarizes the frequency selection configurations: SWITCHING FREQUENCY SYNC PIN RT PIN 350 kHz, internally set Float or AGND Float 550 kHz, internally set ≥ 2.5 V Float Externally set 280 kHz to 700 kHz Float R = 180 kΩ to 68 kΩ Externally synchronized frequency Synchronization signal R = RT value for 80% of external synchronization frequency ERROR AMPLIFIER The high performance, wide bandwidth, voltage error amplifier sets the TPS54973 apart from most dc/dc converters. The user is given the flexibility to use a wide range of output L and C filter components to suit the particular application needs. Type 2 or type 3 compensation can be employed using external compensation components. PWM CONTROL Signals from the error amplifier output, oscillator, and current limit circuit are processed by the PWM control logic. Referring to the internal block diagram, the control logic includes the PWM comparator, OR gate, PWM latch, and portions of the adaptive dead-time and control logic block. During steady-state operation below the current limit threshold, the PWM comparator output and oscillator pulse train alternately reset and set the PWM latch. Once the PWM latch is reset, the low-side FET remains on for a minimum duration set by the oscillator pulse width. During this period, the PWM ramp discharges rapidly to its valley voltage. When the ramp begins to charge back up, the low-side FET turns off and high-side FET turns on. As the PWM ramp voltage exceeds the error amplifier output voltage, the PWM comparator resets the latch, thus turning off the high-side FET and turning on the low-side FET. The low-side FET remains on until the next oscillator pulse discharges the PWM ramp. During transient conditions, the error amplifier output could be below the PWM ramp valley voltage or above the PWM peak voltage. If the error amplifier is high, the PWM 14 latch is never reset, and the high-side FET remains on until the oscillator pulse signals the control logic to turn the high-side FET off and the low-side FET on. The device operates at its maximum duty cycle until the output voltage rises to the regulation set-point, setting VSENSE to approximately the same voltage as VREF. If the error amplifier output is low, the PWM latch is continually reset and the high-side FET does not turn on. The low-side FET remains on until the VSENSE voltage decreases to a range that allows the PWM comparator to change states. The TPS54973 is capable of sinking current continuously until the output reaches the regulation set-point. If the current limit comparator trips for longer than 100 ns, the PWM latch resets before the PWM ramp exceeds the error amplifier output. The high-side FET turns off and low-side FET turns on to decrease the energy in the output inductor and consequently the output current. This process is repeated each cycle in which the current limit comparator is tripped. DEAD-TIME CONTROL AND MOSFET DRIVERS Adaptive dead-time control prevents shoot-through current from flowing in both N-channel power MOSFETs during the switching transitions by actively controlling the turnon times of the MOSFET drivers. The high-side driver does not turn on until the voltage at the gate of the low-side FET is below 2 V. While the low-side driver does not turn on until the voltage at the gate of the high-side MOSFET is below 2 V. The high-side and low-side drivers are designed with 300-mA source and sink capability to quickly drive the power MOSFETs gates. The low-side driver is supplied from VIN, while the high-side drive is supplied from the BOOT pin. A bootstrap circuit uses an external BOOT capacitor and an internal 2.5-Ω bootstrap switch connected between the VIN and BOOT pins. The integrated bootstrap switch improves drive efficiency and reduces external component count. OVERCURRENT PROTECTION The cycle-by-cycle current limiting is achieved by sensing the current flowing through the high-side MOSFET and comparing this signal to a preset overcurrent threshold. The high side MOSFET is turned off within 200 ns of reaching the current limit threshold. A 100-ns leading edge blanking circuit prevents current limit false tripping. Current limit detection occurs only when current flows from VIN to PH when sourcing current to the output filter. Load protection during current sink operation is provided by thermal shutdown. TPS54973 www.ti.com SLVS453A − FEBRUARY 2003 − REVISED FEBRUARY 2005 THERMAL SHUTDOWN POWER-GOOD (PWRGD) The device uses the thermal shutdown to turn off the power MOSFETs and disable the controller if the junction temperature exceeds 150°C. The device is released from shutdown automatically when the junction temperature decreases to 10°C below the thermal shutdown trip point, and starts up under control of the slow-start circuit. Thermal shutdown provides protection when an overload condition is sustained for several milliseconds. With a persistent fault condition, the device cycles continuously; starting up by control of the soft-start circuit, heating up due to the fault condition, and then shutting down upon reaching the thermal shutdown trip point. This sequence repeats until the fault condition is removed. The power good circuit monitors for undervoltage conditions on VSENSE. If the voltage on VSENSE is 10% below the reference voltage, the open-drain PWRGD output is pulled low. PWRGD is also pulled low if VIN is less than the UVLO threshold or SS/ENA is low, or a thermal shutdown occurs. When VIN ≥ UVLO threshold, SS/ENA ≥ enable threshold, and VSENSE > 90% of Vref, the open drain output of the PWRGD pin is high. A hysteresis voltage equal to 3% of Vref and a 35 µs falling edge deglitch circuit prevent tripping of the power good comparator due to high frequency noise. 15 PACKAGE OPTION ADDENDUM www.ti.com 10-Dec-2020 PACKAGING INFORMATION Orderable Device Status (1) Package Type Package Pins Package Drawing Qty Eco Plan (2) Lead finish/ Ball material MSL Peak Temp Op Temp (°C) Device Marking (3) (4/5) (6) TPS54973PWP ACTIVE HTSSOP PWP 28 50 RoHS & Green NIPDAU Level-2-260C-1 YEAR -40 to 85 TPS54973 TPS54973PWPR ACTIVE HTSSOP PWP 28 2000 RoHS & Green NIPDAU Level-2-260C-1 YEAR -40 to 85 TPS54973 (1) The marketing status values are defined as follows: ACTIVE: Product device recommended for new designs. LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect. NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design. PREVIEW: Device has been announced but is not in production. Samples may or may not be available. OBSOLETE: TI has discontinued the production of the device. (2) RoHS: TI defines "RoHS" to mean semiconductor products that are compliant with the current EU RoHS requirements for all 10 RoHS substances, including the requirement that RoHS substance do not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, "RoHS" products are suitable for use in specified lead-free processes. TI may reference these types of products as "Pb-Free". RoHS Exempt: TI defines "RoHS Exempt" to mean products that contain lead but are compliant with EU RoHS pursuant to a specific EU RoHS exemption. Green: TI defines "Green" to mean the content of Chlorine (Cl) and Bromine (Br) based flame retardants meet JS709B low halogen requirements of