TPS6734ID

TPS6734I FIXED 12-V 120-mA BOOST-CONVERTER SUPPLY SLVS127A – AUGUST 1995 – REVISED JANUARY 1999 D D D D D D D D D D OR P PACKAGE (TOP VIEW) Pin-for-Pin Compatible With MAX734 Programming Voltage for Flash Memory 2.7-V to 11-V Input Operating Range Output Current of 120 mA or Greater From 3.75-V or Higher Input 3-µA Maximum Supply Current in Shutdown Only 5 External Components Required High Efficiency . . . 85% Typical (5-V Input, 120-mA Output) 8-Pin SOIC and DIP Packages – 40°C to 85°C Free-Air Operating Temperature Range EN REF SS COMP 1 8 2 7 3 6 4 5 VCC FB OUT GND description The TPS6734 is a fixed 12-V output boost converter capable of delivering 120 mA from inputs as low as 3.75 V. The device is pin-for-pin compatible with the MAX734 regulator and offers the following advantages: lower supply current, wider operating input-voltage range, and higher output currents. As shown in Figure 1, the only external components required are: an inductor, a Schottky rectifier, an output filter capacitor, an input filter capacitor, and a small capacitor for loop compensation. The entire converter occupies less than 0.7 in2 of PCB space when implemented with surface-mount components. An enable input is provided to shut down the converter and reduce the supply current to 3 µA when 12 V is not needed. The TPS6734 is a 170-kHz current-mode PWM ( pulse-width modulation) controller with an n-channel MOSFET power switch. Gate drive for the switch is derived from the 12-V output after start-up to minimize the die area needed to realize the 0.7-Ω MOSFET and improve efficiency at input voltages below 5 V. Soft start is accomplished with the addition of one small capacitor. A 1.22-V reference (pin 2) is brought out for external use. High efficiency at low supply voltages and low supply current in shutdown make the TPS6734 particularly attractive for flash memory programming supplies, PCMCIA cards, and operational amplifiers in battery-powered equipment. The TPS6734 is available in 8-pin DIP and SOIC packages and operates over a free-air temperature range of – 40°C to 85°C. VI 3.75 V to 12 V ENABLE TPS6734 1 2 3 4 EN VCC REF SS FB OUT COMP GND 8 18 µH 7 1A, 20 V 6 + 5 33 µF 0.001 µF VO 12 V, 120 mA Figure 1. Typical Operating Circuit Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet. Copyright  1999, Texas Instruments Incorporated PRODUCTION DATA information is current as of publication date. Products conform to specifications per the terms of Texas Instruments standard warranty. Production processing does not necessarily include testing of all parameters. POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 1 TPS6734I FIXED 12-V 120-mA BOOST-CONVERTER SUPPLY SLVS127A – AUGUST 1995 – REVISED JANUARY 1999 AVAILABLE OPTIONS PACKAGE TA SMALL OUTLINE (D) – 40°C to 85°C TPS6734ID PLASTIC DIP (P) TPS6734IP The D package is available taped and reeled. Add the suffix R to the device type (e.g., TPS6734IDR). TPS6734 chip information Thermal compression or ultrasonic bonding can be used on the doped-aluminum bonding pad. Chips can be mounted with conductive epoxy or a gold-silicon preform. Contact factory for die sales. BONDING PAD ASSIGNMENTS (1) 1 (8) 8 EN REF 7 (7) SS (2) 2 COMP 1 8 2 7 3 4 TPS6734 6 5 VCC FB OUT GND (7) 7 92 CHIP THICKNESS: 15 TYPICAL (6) 6 BONDING PADS: 4X4 MINIMUM TJmax = 150°C TOLERANCES ARE ±10% ALL DIMENSIONS ARE IN MILS. (3) 3 (4) 4 (5) 5 (5) 5 75 2 POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 TPS6734I FIXED 12-V 120-mA BOOST-CONVERTER SUPPLY SLVS127A – AUGUST 1995 – REVISED JANUARY 1999 functional block diagram EN 1 8 VCC EN VCC EN FB 7 170-kHz Oscillator COMP 6 _ R Error Amplifier Voltage Reference 2 1 MΩ SS OUT S + REF Power Switch 4 Q Drive Latch PWM Comparator x6 Driver Σ Current Sense Amplifier 5 3 GND x3.5 SS Clamp Overcurrent Comparator + – Terminal Functions TERMINAL NAME DESCRIPTION NO. EN 1 Enable. EN ≥ 2 V turns on the TPS6734. EN ≤ 0.4 V turns it off and reduces the supply current to 3 µA max. REF 2 1.22-V reference voltage output. REF can source 100 µA for external loads. SS 3 Soft Start. A capacitor between SS and GND brings the output voltage up slowly at power-up. COMP 4 Compensation connection. A 0.001-µF capacitor between COMP and FB stabilizes the feedback loop. GND 5 Ground OUT 6 N-channel MOSFET drain connection FB 7 Feedback voltage. FB is connected to the converter output for the feedback loop. VCC 8 Supply voltage input POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 3 TPS6734I FIXED 12-V 120-mA BOOST-CONVERTER SUPPLY SLVS127A – AUGUST 1995 – REVISED JANUARY 1999 detailed description The following descriptions refer to the functional block diagram. reference The internal 1.22-V reference is brought out on REF and can source 100 µA maximum to external loads. A 0.01-µF to 0.1-µF decoupling capacitor connected between REF and GND is recommended to minimize noise pickup. oscillator and ramp generator The oscillator circuit provides a 170-kHz clock, to set the converter operating frequency, and a timing ramp for slope compensation. The clock waveform is a pulse, a few hundred nanoseconds in duration, that is used to limit the maximum power-switch duty cycle to 95%. The timing ramp is summed with the current-sense signal at the input to the current-sense amplifier. driver latch The latch, which consists of a set/reset flip-flop and associated logic, is used to control the state of the power switch by turning the driver on and off. A high output from the latch turns the switch on; a low output from the latch turns it off. In normal operation, the flip-flop is set high during the clock pulse, but gating keeps the latch output low until the clock pulse is over. The latch is reset when the PWM comparator output goes high. current-sense amplifier The current-sense amplifier has a fixed gain of 6. It amplifies the slope-compensated current-sense voltage (a summation of the voltage on the current-sense resistor and the oscillator ramp) and feeds it to the PWM comparator. error amplifier The error amplifier is a high-gain differential amplifier used to regulate the converter output voltage. The amplifier generates an error signal, which is fed to the PWM comparator. The error signal is generated when a sample of the output voltage is compared to the internal reference and the difference is amplified. The output sample is obtained from a resistive divider connected between FB and GND. FB is externally connected to the converter output, and the divider output is connected to both the error amplifier input and COMP. A 0.001-µF capacitor connected between FB and COMP stabilizes the voltage control loop. PWM comparator The PWM comparator resets the drive latch and turns off the power switch whenever the slope-compensated current-sense signal from the current-sense amplifier exceeds the error signal. power switch The power switch is a 0.7-Ω n-channel MOSFET with current-sensing. The drain is connected to OUT and the current sense is connected to a resistor. The voltage across the resistor is proportional to the current in the power switch and is tied to the overcurrent comparator and the current-sense amplifier. In normal operation, the power switch is turned on at the start of each clock cycle and turned off when the PWM comparator resets the drive latch. SS clamp The SS (soft-start) clamp circuit limits the signal level on error-amplifier output during start-up. The voltage on SS is amplified and used to momentarily override the error-amplifier output until it rises above that output, at which point the error-amplifier takes over. This prevents the input to the PWM comparator from exceeding its common-mode range (the error-amplifier output too high to be reached by the current ramp) by limiting the maximum voltage on the error-amplifier output during start-up. 4 POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 TPS6734I FIXED 12-V 120-mA BOOST-CONVERTER SUPPLY SLVS127A – AUGUST 1995 – REVISED JANUARY 1999 soft start Soft start causes the output voltage to increase to the regulation point at a controlled rate of rise. The voltage on the charging soft-start capacitor gradually raises the clamp on the error-amplifier output voltage, limiting surge currents at power-up by increasing the current-limit threshold on a cycle-by-cycle basis. Even if SS has no capacitor installed, some distributed capacitance will always be present. A soft-start cycle is initiated when either the enable signal (EN) is switched high, or an overcurrent fault condition triggers the discharge of the soft-start capacitor. overcurrent comparator The overcurrent comparator monitors the current in the power switch. The comparator trips and initiates a soft-start cycle if the power-switch current exceeds 1.5-A peak. On each clock cycle, the power switch turns on and attempts to deliver current until the overcurrent limits are exceeded. enable (EN) A logic low on EN puts the TPS6734 in shutdown mode. In shutdown, the output power switch, voltage reference, and other functions are shut off, the supply current is reduced to 3 µA maximum, and the soft-start capacitor is discharged through a 1-MΩ resistance. The output voltage falls to a diode drop below the input voltage because of the current path from input to output through the inductor and diode. DISSIPATION RATING TABLE PACKAGE TA ≤ 25°C POWER RATING DERATING FACTOR ABOVE TA = 25°C TA = 70°C POWER RATING TA = 85°C POWER RATING D 725 mW 5.8 mW/°C 464 mW 377 mW P 1175 mW 9.4 mW/°C 752 mW 611 mW absolute maximum ratings over operating free-air temperature range (unless otherwise noted)† Pin voltages: VCC, OUT (see Note 1) . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . – 0.3 V to 15 V SS, COMP, EN (see Note 1) . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . – 0.3 V to VCC+ 0.3 V Peak switch current . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1.5 A Reference current . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 2.5 mA Continuous power dissipation . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . See Dissipation Rating Table Operating free-air temperature range, TA . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . – 40°C to 85°C Storage temperature range, Tstg . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . – 65°C to 150°C Lead temperature 1,6 mm (1/16 inch) from case for 10 s . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 260°C † Stresses beyond those listed under “absolute maximum ratings” may cause permanent damage to the device. These are stress ratings only, and functional operation of the device at these or any other conditions beyond those indicated under “recommended operating conditions” is not implied. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability. NOTE 1: All voltage values are with respect to network terminal ground. POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 5 TPS6734I FIXED 12-V 120-mA BOOST-CONVERTER SUPPLY SLVS127A – AUGUST 1995 – REVISED JANUARY 1999 recommended operating conditions Supply voltage MIN NOM MAX 2.7 5 12 Compensation capacitor 0 Reference capacitor 100 – 40 µA µF 0.01 Operating free-air temperature, TA V µF 0.001 Output current at REF UNIT 85 °C electrical characteristics over recommended operating free-air temperature range, VCC = 5 V, IO(LOAD) = 0 mA, EN = 5 V, typical values are at TA = 25°C (unless otherwise noted) (refer to circuit shown in Figure 13) PARAMETER Operating Supply current Standby TEST CONDITIONS MIN Entire circuit TYP MAX 1.2 2.5 mA EN = 0.4 V, entire circuit 3 µA EN = 0.4 V, into VCC 3 µA High-level input threshold voltage at EN 2 V Low-level input threshold voltage at EN Shutdown input leakage current at EN –1 On resistance at OUT Current at OUT = 500 mA Leakage current at OUT VDS = 12 V Reference voltage Reference drift UNITS TA = – 40°C to 85°C Oscillator frequency Compensation pin impedance 0.4 V 1 µA 0.7 Ω 1 µA 1.22 V 6.7 ppm/°C 170 kHz 7500 Ω performance characteristics over recommended operating free-air temperature range, typical circuit connected as shown in Figure 13, typical values are at TA = 25°C (unless otherwise noted) PARAMETER Output voltage Load current Line regulation Load regulation Efficiency 6 TEST CONDITIONS VCC = 4.75 V, VCC = 3.75 V 0 mA < IO(LOAD) < 120 mA VCC = 3.0 V, VCC = 5 V to 12 V, Figure 11 IO(LOAD) = 50 mA IO(LOAD) = 0 mA to 120 mA VCC = 5 V, IO(LOAD) = 120 mA POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 MIN TYP MAX UNITS 11.64 12.12 12.6 V 120 150 150 0.20% 0.0042% 86% mA TPS6734I FIXED 12-V 120-mA BOOST-CONVERTER SUPPLY SLVS127A – AUGUST 1995 – REVISED JANUARY 1999 TYPICAL CHARACTERISTICS I L – Load Current – mA LOAD TRANSIENT RESPONSE 200 150 VI = 5 V VO = 12 V IL = 0 mA to 120 mA 100 50 12.1 12 11.9 0 2 4 6 8 10 12 14 16 VO – Output Voltage – V 0 18 t – Time – ms Figure 2 ÁÁ 6 4 2 0 12.05 12 11.95 0 2 4 6 8 10 12 14 16 VO – Output Voltage – V VI – Input Voltage – V LINE TRANSIENT RESPONSE 8 18 t – Time – ms Figure 3 POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 7 TPS6734I FIXED 12-V 120-mA BOOST-CONVERTER SUPPLY SLVS127A – AUGUST 1995 – REVISED JANUARY 1999 TYPICAL CHARACTERISTICS OSCILLATOR FREQUENCY vs SUPPLY VOLTAGE EN RESPONSE TIME 200 Fosc – Oscillator Frequency – kHz 14 VI = 5 V VO = 5 V to 12 V IL = 120 mA at 12 V Voltage – V 12 Output Voltage 10 8 190 180 170 ÁÁ ÁÁ ÁÁ 6 4 EN Voltage 2 160 150 140 0 0 1 2 3 4 5 6 7 8 3 9 4 5 6 7 8 9 10 VCC – Supply Voltage – V t – Time – mS Figure 4 Figure 5 MAXIMUM OUTPUT CURRENT vs SUPPLY VOLTAGE INPUT SUPPLY CURRENT vs SUPPLY VOLTAGE 18 180 IO = 0 Á Á I O – Maximum Output Current – mA I CC – Input Supply Current – mA 16 14 Bootstrap 12 10 8 6 4 2 0 0.1 0.5 160 140 120 100 80 60 40 20 Typical 0 0.9 1.3 1.7 2.1 2.5 2.9 4.5 VCC – Supply Voltage – V 6.5 8.5 3 Figure 6 8 4.5 3.5 4 VCC – Supply Voltage – V Figure 7 POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 5 TPS6734I FIXED 12-V 120-mA BOOST-CONVERTER SUPPLY SLVS127A – AUGUST 1995 – REVISED JANUARY 1999 APPLICATION INFORMATION The TPS6734 operates in a boost circuit as shown in Figures 1 and 11. Figure 1 shows the typical application circuit, which generates 12 V from a nominal 5-V source. The circuit is ideal for processor interface for energy management, because EN can be controlled by logic signals to place the 12-V source into the shutdown mode (3-µA current drain) when 12 V is not needed. An example of such an application is a flash memory device that requires 12 V for the erase cycle. discontinuous mode The circuit shown in Figure 1 operates in discontinuous mode over most of the range of input voltage and output current. In discontinuous mode, current through the inductor begins at zero, rises to a peak value, then ramps down to zero each cycle as shown by the voltage and current waveforms in Figure 8. The ringing in the voltage waveform on OUT results from a resonance between the inductor and the power switch capacitance and is normal for discontinuous operation. DISCONTINUOUS MODE 15 VI = 5 V VO = 12 V IL = 50 mA 10 5 0 1 0.5 0 0 2 4 6 8 10 12 14 16 I – Inductor Current – A Voltage at Out – V 20 18 t – Time – µs Figure 8 POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 9 TPS6734I FIXED 12-V 120-mA BOOST-CONVERTER SUPPLY SLVS127A – AUGUST 1995 – REVISED JANUARY 1999 APPLICATION INFORMATION continuous mode When the converter is delivering heavy loads from low voltage sources, it operates in continuous mode. As shown in Figure 9, the inductor current does not drop to zero and the ringing is gone from the OUT voltage waveform. CONTINUOUS MODE Voltage at Out – V 20 15 VI = 5 V VO = 12 V IL = 150 mA 10 5 1 0.5 0 0 2 4 6 8 10 12 14 16 I– Inductor Current – A 0 18 t – Time –µs Figure 9 pulse-skipping mode At very light load currents, the TPS6734 cannot generate drive pulses sufficiently narrow to maintain regulation and operate at 170 kHz. Under these circumstances, the converter operates in a pulse-skipping mode, in which cycles are skipped. In pulse-skipping mode, the waveforms are irregular and the output ripple contains a low-frequency component that may exceed 50 mV peak-to-peak. 10 POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 TPS6734I FIXED 12-V 120-mA BOOST-CONVERTER SUPPLY SLVS127A – AUGUST 1995 – REVISED JANUARY 1999 APPLICATION INFORMATION efficiency Typical efficiency for the converter circuit shown in Figure 13 is plotted in Figure 10. The efficiency falls off rapidly at very light currents because the supply current is a significant percentage of the load. EFFICIENCY vs OUTPUT CURRENT 88 VCC = 5.5 V 86 % – Efficiency 84 VCC = 4.5 V VCC = 5 V 82 80 78 76 74 10 20 30 40 50 60 70 80 90 100 110 120 130 140 IO – Output Current – mA Figure 10 inductor selection Inductance value is directly proportional to the input voltage and inversely proportional to the output power. The 18 µH shown in the typical circuit is the proper value for operation from 5-V sources up to 2-W loads. A lower inductance value should be used when operating from 3-V sources. Operation from 7 V and higher sources may require inductance values greater than 18 µH. The inductor’s saturation current rating should be greater than three times the dc load current for 5-V inputs and five times the dc load for 3-V inputs. output filter capacitor selection The output filter capacitor should be selected for minimum ESR (equivalent series resistance). Capacitor ESR × ∆IL (change in inductor current) determines the amplitude of the high-frequency ripple on the output voltage. The ESR of the capacitor should be less than 0.25 Ω to keep the output ripple less than 50 mV peak-to-peak over the entire current range (using 18-µH inductor). diode A Schottky diode or a high-speed silicon rectifier should be used. The continuous current rating of the diode should be at least 300 mA for full load (120 mA) operation. POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 11 TPS6734I FIXED 12-V 120-mA BOOST-CONVERTER SUPPLY SLVS127A – AUGUST 1995 – REVISED JANUARY 1999 APPLICATION INFORMATION soft-start capacitor Soft-start timing is controlled by the value of the SS capacitor. Table 1 lists soft-start time intervals for selected capacitor values and circuit conditions. If the circuit starts up with no load (e.g. in flash-memory programming supplies), no soft start is needed. Omitting the soft-start capacitor provides a minimum output-voltage rise time from the shutdown state, improving the output start-up time. Table 1. Typical Soft-Start Times SOFT-START TIME† (ms) VERSUS CAPACITANCE (µF) SUPPLY VOLTAGE (V) NO. CAP 0.047 0.1 0.47 1.0 5 0.70 22 42 220 400 7 0.46 15 37 185 225 9 0.38 10 17 88 155 † Soft-start times are ±35% printed-circuit layout Printed-circuit-board (PCB) layout is critical to quiet operation. A ground plane is recommended. Special attention should be given to minimizing the lengths of the switching loops. The first loop is formed by OUT, the diode, the output capacitor, and GND, the length of which can be minimized by connecting the anode of the diode close to OUT. The output capacitor should be connected directly between the diode cathode and GND with the shortest possible path. The second loop is formed by OUT, the inductor, the input capacitor, and GND. This loop is less critical than the first; however, the connection of OUT, the inductor and the anode of the diode must be minimized. Bypass capacitors should be located as close to the device as possible to prevent instability and noise pickup. If a large VCC-to-GND bypass capacitor cannot be placed adjacent to the IC pins, the pins should be bypassed directly with a small ceramic capacitor (e.g., 0.1 µF). The recommended layout, shown in Figures 14 through 17, can provide guidance for PCB configuration (the ground plane beneath the TPS6734 and the short loops should be noted). Plastic plug-in-type proto boards, or any construction scheme that allows long leads and the possibility of noise pickup, should not be used when assembling a breadboard or prototype application circuit implementing the TPS6734. 12 POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 TPS6734I FIXED 12-V 120-mA BOOST-CONVERTER SUPPLY SLVS127A – AUGUST 1995 – REVISED JANUARY 1999 APPLICATION INFORMATION bootstrapped output circuit For operation below 2.7 V, the TPS6734 may be connected in a bootstrap configuration as shown in Figure 11. The bootstrap configuration is less efficient (requires more supply current and suffers a loss in efficiency at voltages below 5 V; see Figure 12) and is not recommended except for very low voltage operating conditions. Because the output-driver stage, which benefits most from higher voltages, is diode-coupled to the output voltage (see Figure 2), the bootstrapped configuration provides no benefit except at very low voltages. In the shutdown mode (EN = low), no-load quiescent current is unchanged (3 µA max) whether in the bootstrap or the typical configuration. VI 2 V to 12 V TPS6734 1 ENABLE 2 3 4 EN VCC REF SS FB OUT COMP GND 8 7 18 µH 1 A, 20 V 6 + 5 0.0047 µF 33 µF VO 12 V, 120 mA 0.001 µF Figure 11. TPS6734 Bootstrap Configuration EFFICIENCY vs OUTPUT CURRENT FOR TYPICAL AND BOOTSTRAP 86 Typical 84 VCC = 5 V 82 Bootstrap % – Efficiency 80 78 76 74 72 70 68 66 10 20 30 40 50 60 70 80 90 100 110 120 130 140 IO – Output Current – mA Figure 12 POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 13 TPS6734I FIXED 12-V 120-mA BOOST-CONVERTER SUPPLY SLVS127A – AUGUST 1995 – REVISED JANUARY 1999 APPLICATION INFORMATION TPS6734 converter design with recommended layout The following schematic (Figure 13) and a required-components table are provided for a 12-V-output boost converter. The converter is capable of delivering 120 mA of output current over an input voltage range of 3.75 V to 12 V. Recommended layout and detailed artwork for a PCB are provided in Figures 14 through 17. P1 VI GND GND ENABLE 1 2 R1 10 kΩ TPS6734 1 3 C1 33 µF, 20 V 4 EN VCC + 2 FB REF 8 7 U1 3 SS OUT COMP C2 0.01 µF D1 6 5 4 GND C3 0.047 µF P2 1 L1 18 µH VO SS12 2 VO C5 3 + 33 µF, 20 V GND 4 GND C4 0.001 µF NOTE A: A jumper between pins P1-3 and P1-4 shuts off the TPS7634. Remove the jumper to resume normal operation. Figure 13. Schematic for Printed Circuit Board (shown in Figures 14 through 17) Required Components QTY. 14 DESCRIPTION REF DES MANUFACTURER’S PART NO. MANUFACTURER 1 IC, power supply, 12 V for flash memory U1 TPS6734ID Texas Instruments 1 Diode, Schottky D1 SS12 General Instruments 1 Inductor, 18 µH, 150 mΩ, 1.23 A(DC) L1 CD54180MC Sumida 2 Capacitor, 33 µF, 20 V, tantalum TAPSD336M020R0200 AVX 1 Capacitor, 0.01 µF, 50 V, ceramic, 0805 C2 1 Capacitor, 0.047 µF, 50 V, ceramic, 1206 C3 1 Capacitor, 0.001 µF, 50 V, ceramic, 0805 C4 2 Connector, header, 4-pin 1 PCB, TPS6734 C1,5 P1,2 POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 Molex TPS6734I FIXED 12-V 120-mA BOOST-CONVERTER SUPPLY SLVS127A – AUGUST 1995 – REVISED JANUARY 1999 APPLICATION INFORMATION REDUCE TO 2.000 +/– .005 REDUCE TO 2.500 +/– .005 1 P1 R1 C1 C2 C3 D1 SLVP081 P2 1 L1 U1 C4 C5 4 4 TPS6734 EVALUATION BOARD SILKSCREEN – TOP Figure 14. Component Placement REDUCE TO 2.000 +/– .005 REDUCE TO 2.500 +/– .005 1 P1 C2 C3 4 R1 C1 SLVP081 1 P2 L1 D1 U1 C4 C5 4 SS JMPR TPS6734 EVALUATION BOARD SILKSCREEN – TOP Figure 15. Solder Paste Mask POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 15 TPS6734I FIXED 12-V 120-mA BOOST-CONVERTER SUPPLY SLVS127A – AUGUST 1995 – REVISED JANUARY 1999 APPLICATION INFORMATION REDUCE TO 2.000 +/– .005 REDUCE TO 2.500 +/– .005 COMPONENT SIDE Figure 16. Printed Circuit, Component Side REDUCE TO 2.000 +/– .005 REDUCE TO 2.500 +/– .005 Figure 17. Printed Circuit, Wiring Side (Viewed from Component Side) 16 POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 TPS6734I FIXED 12-V 120-mA BOOST-CONVERTER SUPPLY SLVS127A – AUGUST 1995 – REVISED JANUARY 1999 MECHANICAL DATA D (R-PDSO-G**) PLASTIC SMALL-OUTLINE PACKAGE 14 PIN SHOWN 0.050 (1,27) 0.020 (0,51) 0.014 (0,35) 14 0.010 (0,25) M 8 0.008 (0,20) NOM 0.244 (6,20) 0.228 (5,80) 0.157 (4,00) 0.150 (3,81) Gage Plane 0.010 (0,25) 1 7 0°– 8° A 0.044 (1,12) 0.016 (0,40) Seating Plane 0.069 (1,75) MAX 0.010 (0,25) 0.004 (0,10) PINS ** 0.004 (0,10) 8 14 16 A MAX 0.197 (5,00) 0.344 (8,75) 0.394 (10,00) A MIN 0.189 (4,80) 0.337 (8,55) 0.386 (9,80) DIM 4040047 / D 10/96 NOTES: A. B. C. D. All linear dimensions are in inches (millimeters). This drawing is subject to change without notice. Body dimensions do not include mold flash or protrusion, not to exceed 0.006 (0,15). Falls within JEDEC MS-012 POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 17 TPS6734I FIXED 12-V 120-mA BOOST-CONVERTER SUPPLY SLVS127A – AUGUST 1995 – REVISED JANUARY 1999 MECHANICAL DATA P (R-PDIP-T8) PLASTIC DUAL-IN-LINE PACKAGE 0.400 (10,60) 0.355 (9,02) 8 5 0.260 (6,60) 0.240 (6,10) 1 4 0.070 (1,78) MAX 0.310 (7,87) 0.290 (7,37) 0.020 (0,51) MIN 0.200 (5,08) MAX Seating Plane 0.125 (3,18) MIN 0.100 (2,54) 0.021 (0,53) 0.015 (0,38) 0°– 15° 0.010 (0,25) M 0.010 (0,25) NOM 4040082 / B 03/95 NOTES: A. All linear dimensions are in inches (millimeters). B. This drawing is subject to change without notice. C. Falls within JEDEC MS-001 18 POST OFFICE BOX 655303 • DALLAS, TEXAS 75265 PACKAGE OPTION ADDENDUM www.ti.com 14-Oct-2022 PACKAGING INFORMATION Orderable Device Status (1) Package Type Package Pins Package Drawing Qty Eco Plan (2) Lead finish/ Ball material MSL Peak Temp Op Temp (°C) Device Marking (3) Samples (4/5) (6) TPS6734ID ACTIVE SOIC D 8 75 RoHS & Green NIPDAU Level-1-260C-UNLIM -40 to 85 6734I Samples TPS6734IDR ACTIVE SOIC D 8 2500 RoHS & Green NIPDAU Level-1-260C-UNLIM -40 to 85 6734I Samples TPS6734IP ACTIVE PDIP P 8 50 RoHS & Green NIPDAU N / A for Pkg Type -40 to 85 TPS6734IP Samples (1) The marketing status values are defined as follows: ACTIVE: Product device recommended for new designs. LIFEBUY: TI has announced that the device will be discontinued, and a lifetime-buy period is in effect. NRND: Not recommended for new designs. Device is in production to support existing customers, but TI does not recommend using this part in a new design. PREVIEW: Device has been announced but is not in production. Samples may or may not be available. OBSOLETE: TI has discontinued the production of the device. (2) RoHS: TI defines "RoHS" to mean semiconductor products that are compliant with the current EU RoHS requirements for all 10 RoHS substances, including the requirement that RoHS substance do not exceed 0.1% by weight in homogeneous materials. Where designed to be soldered at high temperatures, "RoHS" products are suitable for use in specified lead-free processes. TI may reference these types of products as "Pb-Free". RoHS Exempt: TI defines "RoHS Exempt" to mean products that contain lead but are compliant with EU RoHS pursuant to a specific EU RoHS exemption. Green: TI defines "Green" to mean the content of Chlorine (Cl) and Bromine (Br) based flame retardants meet JS709B low halogen requirements of