PB58

P r B58, IPB58Ao n FF r o m P o d u c t Innnnoovvaa t i r o m PB58 • PB58A PB58 • PB58A Power Booster Amplifier FEATURES • WIDE SUPPLY RANGE — ±15V to ±150V • HIGH OUTPUT CURRENT — 1.5A Continuous (PB58) 2.0A Continuous (PB58A) • VOLTAGE AND CURRENT GAIN • HIGH SLEW — 50V/µs Minimum (PB58) 75V/µs Minimum (PB58A) • PROGRAMMABLE OUTPUT CURRENT LIMIT • HIGH POWER BANDWIDTH — 320 kHz Minimum • LOW QUIESCENT CURRENT — 12mA Typical • EVALUATION KIT — See EK50 8-PIN TO-3 PACKAGE STYLE CE EQUIVALENT SCHEMATIC 3 +Vs Q1 APPLICATIONS • HIGH VOLTAGE INSTRUMENTATION • Electrostatic TRANSDUCERS & DEFLECTION • Programmable Power Supplies Up to 280V p-p Q2 Q3 IN 4 GAIN 6.2K 7 50K COM 5 COMP 8 Q9 Q10 3.1K Q7 Q11 Q8 Q4 Q6 Q5 DESCRIPTION The PB58 is a high voltage, high current amplifier designed to provide voltage and current gain for a small signal, general purpose op amp. Including the power booster within the feedback loop of the driver amplifier results in a composite amplifier with the accuracy of the driver and the extended output voltage range and current capability of the booster. The PB58 can also be used without a driver in some applications, requiring only an external current limit resistor to function properly. The output stage utilizes complementary MOSFETs, providing symmetrical output impedance and eliminating second breakdown limitations imposed by Bipolar Transistors. Internal feedback and gainset resistors are provided for a pin-strapable gain of 3. Additional gain can be achieved with a single external resistor. Compensation is not required for most driver/gain configurations, but can be accomplished with a single external capacitor. Enormous flexibility is provided through the choice of driver amplifier, current limit, supply voltage, voltage gain, and compensation. This hybrid circuit utilizes a beryllia (BeO) substrate, thick film resistors, ceramic capacitors and semiconductor chips to maximize reliability, minimize size and give top performance. Ultrasonically bonded aluminum wires provide reliable interconnections at all operating temperatures. The 8-pin TO-3 package is electrically isolated and hermetically sealed using one-shot resistance welding. The use of compressible isolation washers voids the warranty. OUT 1 2 CL –Vs 6 EXTERNAL CONNECTIONS +VS IN 4 TOP VIEW COM 5 –VS 6 7 GAIN 8 COMP CC CL 3 2 1 OUT RCL TYPICAL APPLICATION CF RF Figure 1. Inverting composite amplifier. +Vs IN COM PB58 OUT CC RG RL RCL VIN RI +15V OP AMP RG –15V –Vs PB58U http://www.cirrus.com Copyright © Cirrus Logic, Inc. 2009 (All Rights Reserved) MAY 2009 1 APEX − PB58UREVK PB58 • PB58A ABSOLUTE MAXIMUM RATINGS P r o d u c t I n n o v a t i o nF r o m SUPPLY VOLTAGE, +VS to –VS OUTPUT CURRENT, within SOA POWER DISSIPATION, internal at TC = 25°C1 INPUT VOLTAGE, referred to COM TEMPERATURE, pin solder—10 sec max TEMPERATURE, junction1 TEMPERATURE, storage OPERATING TEMPERATURE RANGE, case 300V 2.0A 83W ±15V 300°C 175°C –65 to +150°C –55 to +125°C SPECIFICATIONS PARAMETER INPUT OFFSET VOLTAGE, initial OFFSET VOLTAGE, vs. temperature INPUT IMPEDANCE, DC INPUT CAPACITANCE CLOSED LOOP GAIN RANGE GAIN ACCURACY, internal Rg, Rf GAIN ACCURACY, external Rf PHASE SHIFT OUTPUT VOLTAGE SWING VOLTAGE SWING VOLTAGE SWING CURRENT, continuous SLEW RATE CAPACITIVE LOAD SETTLING TIME to .1% POWER BANDWIDTH SMALL SIGNAL BANDWIDTH SMALL SIGNAL BANDWIDTH POWER SUPPLY VOLTAGE, ±VS4 CURRENT, quiescent TEST CONDITIONS2 MIN PB58 TYP ±.75 –4.5 50 3 10 ±10 ±15 10 60 VS –8 VS –7 VS –5 100 2200 2 320 100 1 ±60 11 12 14 1.2 1.6 30 25 ±150 18 1.3 1.8 85 * MAX ±1.75 –7 * 25 ±15 ±25 * MIN PB58A TYP * * * * * * * * * VS–11 * * * * * * * * * * * * * * * * * * * * * MAX ±1.0 * * * * UNITS V mV/°C kΩ pF V/V % % ° ° V V V A V/µs pF µs kHz kHz MHz V mA mA mA °C/W °C/W °C/W °C Full temperature range3 25 3 AV = 3 AV = 10 f = 10kHz, AVCL = 10, CC = 22pF f = 200kHz, AVCL = 10, CC = 22pF Io = 1.5A (PB58), 2A (PB58A) Io = 1A Io = .1A Full temperature range Full temperature range RL = 100Ω, 2V step VC = 100 Vpp CC = 22pF, AV = 25, Vcc = ±100 CC = 22pF, AV = 3, Vcc = ±30 Full temperature range VS = ±15 VS = ±60 VS = ±150 Full temp. range, f > 60Hz Full temp. range, f < 60Hz Full temperature range Meets full range specifications VS–11 VS–10 VS–8 1.5 50 160 VS–15 * * 2.0 75 240 ±156 * THERMAL RESISTANCE, AC junction to case5 RESISTANCE, DC junction to case RESISTANCE, junction to air TEMPERATURE RANGE, case –25 NOTES: * The specification of PB58A is identical to the specification for PB58 in applicable column to the left. 1. Long term operation at the maximum junction temperature will result in reduced product life. Derate internal power dissipation to achieve high MTTF (Mean Time to Failure). 2. The power supply voltage specified under typical (TYP) applies, TC = 25°C unless otherwise noted. 3. Guaranteed by design but not tested. 4. +VS and –VS denote the positive and negative supply rail respectively. 5. Rating applies if the output current alternates between both output transistors at a rate faster than 60Hz. 6. +VS/–VS must be at least 15V above/below COM. CAUTION The PB58 is constructed from MOSFET transistors. ESD handling procedures must be observed. The internal substrate contains beryllia (BeO). Do not break the seal. If accidentally broken, do not crush, machine, or subject to temperatures in excess of 850°C to avoid generating toxic fumes. 2 PB58U P r o d u c t I n n o v a t i o nF r o m PB58 • PB58A VOLTAGE DROP FROM SUPPLY, VS - VO (V) INTERNAL POWER DISSIPATION, P(W) 100 80 60 40 20 0 –25 POWER DERATING 2 CURRENT LIMIT, ILIM (A) CURRENT LIMIT OUTPUT VOLTAGE SWING 14 12 10 8 6 VO VO + 1.5 R CL = .4 7Ω 1 RC = L .68 Ω .5 RCL = 1.5Ω 0 25 50 75 100 125 CASE TEMPERATURE, TC (°C) 0 CLOSED LOOP GAIN, A (dB) OPEN LOOP PHASE, Ф (°) 0 –25 0 50 75 100 125 25 CASE TEMPERATURE, TC (°C) 4 .01 .05 1 1.5 OUTPUT CURRENT, IO (A) 2 80 OPEN LOOP GAIN, A (dB) SMALL SIGNAL RESPONSE 30 SMALL SIGNAL RESPONSE 0 CLOSED LOOP PHASE, Ф (°) SMALL SIGNAL RESPONSE AVCL = 3 AVCL = 10 AVCL = 25 –90 AVCL = 25 20 AVCL = 10 10 AVCL = 3 0 CC = 22pF 100K 1M 10K FREQUENCY, F (Hz) 10M 60 –45 –45 40 –90 20 –135 –135 CC = 22pF –180 1K 10K 1M 100K FREQUENCY, F (Hz) 10M 0 100 1K 10K 100K 1M FREQUENCY, F (Hz) –180 10M –10 1K QUIESCENT CURRENT 20 INPUT OFFSET VOLTAGE, VOS (V) QUIESCENT CURRENT, IQ (mA) .5 INPUT OFFSET VOLTAGE 400 SLEW RATE VS. TEMP. 15 Vs = 15 0V 0 SLEW RATE, SR (V/µs) 300 +S LE 10 Vs = 10 0V -.5 200 -SLEW W Vs = 30 5 V -1 100 0 –25 50 75 100 125 0 25 CASE TEMPERATURE, TC (°C) -1.5 –25 0 25 50 75 100 125 CASE TEMPERATURE, TC (°C) 0 –25 0 25 50 75 100 125 CASE TEMPERATURE, TC (°C) 300 OUTPUT VOLTAGE, VQ (VP-P) POWER RESPONSE OUTPUT VOLTAGE, VQ (V) 80 60 40 20 0 -20 -40 -60 -80 1 PULSE RESPONSE .1 HARMONIC DISTORTION DRIVER = TL070 VS = 60V VO = 95VP-P 200 100 50 40 30 20 10 100K DISTORTION, THD (%) R L =3 .03 5Ω .003 1M 300K 3M FREQUENCY, F (Hz) 10M 2 3 4 5 TIME, t (µs) 6 7 8 .001 300 10K 1K 3K FREQUENCY, F (Hz) R L = 30K .01 PB58U 1K Ω 3 PB58 • PB58A GENERAL P r o d u c t I n n o v a t i o nF r o m Please read Application Note 1 "General Operating Considerations" which covers stability, supplies, heat sinking, mounting, current limit, SOA interpretation, and specification interpretation. Visit www.Cirrus.com for design tools that help automate tasks such as calculations for stability, internal power dissipation, current limit; heat sink selection; Apex Precision Power’s complete Application Notes library; Technical Seminar Workbook; and Evaluation Kits. STABILITY Stability can be maximized by observing the following guidelines: 1. Operate the booster in the lowest practical gain. 2. Operate the driver amplifier in the highest practical effective gain. 3. Keep gain-bandwidth product of the driver lower than the closed loop bandwidth of the booster. 4. Minimize phase shift within the loop. A good compromise for (1) and (2) is to set booster gain from 3 to 10 with total (composite) gain at least a factor of 3 times booster gain. Guideline (3) implies compensating the driver as required in low composite gain configurations. Phase shift within the loop (4) is minimized through use of booster and loop compensation capacitors Cc and Cf when required. Typical values are 5pF to 33pF. Stability is the most difficult to achieve in a configuration where driver effective gain is unity (ie; total gain = booster gain). For this situation, Table 1 gives compensation values for optimum square wave response with the op amp drivers listed. CF CC DRIVER CCH OP07 22p 22p 741 18p 10p LF155 4.7p 10p LF156 4.7p 10p TL070 22p 15p 10p For: RF = 33K, RI = 3.3K, RG = 22K FPBW 4kHz 20kHz 60kHz 80kHz 80kHz SR 1.5 7 >60 >60 >60 CURRENT LIMIT For proper operation, the current limit resistor (RCL) must be connected as shown in the external connection diagram. The minimum value is 0.33Ω with a maximum practical value of 47Ω. For optimum reliability the resistor value should be set as high as possible. The value is calculated as follows: +IL= .65/RCL + .010, -IL = .65/RCL. OUTPUT CURRENT FROM +VS or –VS (A) 3 2 1 .5 .4 .3 .2 .1 ste ad SOA t= ad C ys ste ta te ad C ste ys = ta te 5° 10 ys 0m s ta T T C te 12 = T 85 C = °C 25 °C 10 20 30 40 50 100 200 300 SUPPLY TO OUTPUT DIFFERENTIAL VOLTAGE, VS –VO (V) Table 1: Typical values for case where op amp effective gain = 1. CF RF +15V CCH OP AMP –15V –Vs +Vs IN COM PB58 OUT COMP CC GAIN RG RCL SAFE OPERATING AREA NOTE: The output stage is protected against transient flyback. However, for protection against sustained, high energy flyback, external fast-recovery diodes should be used. RI VIN COMPOSITE AMPLIFIER CONSIDERATIONS Cascading two amplifiers within a feedback loop has many advantages, but also requires careful consideration of several amplifier and system parameters. The most important of these are gain, stability, slew rate, and output swing of the driver. Operating the booster amplifier in higher gains results in a higher slew rate and lower output swing requirement for the driver, but makes stability more difficult to achieve. RL Figure 2. Non-inverting composite amplifier. SLEW RATE The slew rate of the composite amplifier is equal to the slew rate of the driver times the booster gain, with a maximum value equal to the booster slew rate. GAIN SET RG = [ (Av-1) • 3.1K] – 6.2K RG + 6.2K Av = +1 3.1K The booster’s closed-loop gain is given by the equation above.The composite amplifier’s closed loop gain is determined by the feedback network, that is: –Rf/Ri (inverting) or 1+Rf/Ri (non-inverting). The driver amplifier’s “effective gain” is equal to the composite gain divided by the booster gain. Example: Inverting configuration (figure 1) with R i = 2K, R f = 60K, R g = 0 : Av (booster) = (6.2K/3.1K) + 1 = 3 Av (composite) = 60K/2K = – 30 Av (driver) = – 30/3 = –10 4 OUTPUT SWING The maximum output voltage swing required from the driver op amp is equal to the maximum output swing from the booster divided by the booster gain. The Vos of the booster must also be supplied by the driver, and should be subtracted from the available swing range of the driver. Note also that effects of Vos drift and booster gain accuracy should be considered when calculating maximum available driver swing. PB58U P r o d u c t I n n o v a t i o nF r o m PB58 • PB58A ContACting CiRRUs LogiC sUPPoRt For all Apex Precision Power product questions and inquiries, call toll free 800-546-2739 in North America. For inquiries via email, please contact apex.support@cirrus.com. International customers can also request support by contacting their local Cirrus Logic Sales Representative. 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