19-1776; Rev 4; 8/09
KIT
ATION
EVALU
E
L
B
AVAILA
High-Voltage, Step-Down DC-DC
Controllers in µMAX
The MAX1744/MAX1745 are step-down DC-DC controllers capable of handling up to 36V inputs. These
parts use a proprietary current-limited control scheme
for excellent light- and full-load efficiency, while their
330kHz (max) switching frequency permits small external components for space-critical applications.
Operation to 100% duty cycle permits the lowest possible dropout voltage.
The MAX1744 contains an internal feedback network
that provides a pin-selectable output voltage of either
3.3V or 5V. The MAX1745 uses an external feedback
network to generate an adjustable output voltage
between 1.25V and 18V.
The MAX1744/MAX1745 are available in a space-saving 10-pin μMAX® package.
________________________Applications
Automotive Electronics
____________________________Features
♦ High-Voltage Operation (Up to 36V IN)
♦ Efficiency > 90%
♦ Output Power Capability Exceeds 50W
♦ 10-Pin µMax Package
♦ Low-Dropout Voltage
♦ 100% (max) Duty Cycle
♦ 90µA Quiescent Current
♦ 4µA Shutdown Current
♦ Up to 330kHz Switching Frequency
♦ Output Voltage
5V or 3.3V (MAX1744)
Adjustable 1.25V to 18V (MAX1745)
♦ Current-Limited Control Scheme
Telecom Systems
Ordering Information
Wall-Cube-Powered Devices
TEMP RANGE
PIN-PACKAGE
Industrial Control Systems
MAX1744EUB+
PART
-40°C to +85°C
10 μMAX
Firewire®/IEEE® 1394
MAX1744AUB+
-40°C to +125°C
10 μMAX
MAX1744EUB/V+
-40°C to +85°C
10 μMAX
MAX1745EUB+
-40°C to +85°C
10 μMAX
MAX1745AUB+
-40°C to +125°C
10 μMAX
MAX1745EUB/V+
-40°C to +85°C
10 μMAX
μMAX is a registered trademark of Maxim Integrated Products, Inc.
Firewire is a registered trademark of Apple, Inc.
IEEE is a registered service mark of the Institute of Electrical
and Electronics Engineers, Inc.
+Denotes a lead(Pb)-free/RoHS-compliant package.
/V Denotes an automotive qualified part.
Typical Operating Circuit
IN
4.5V TO 36V
Pin Configuration
TOP VIEW
+
IN
VH
ON
5V
OFF
SHDN
3.3V
3/5
VL
EXT
GND 1
P
MAX1744
CS
REF
GND
OUT
OUT
3.3V
OR 5V
10 IN
VL
2
REF
3
3/5 (FB)
4
7
SHDN
OUT
5
6
CS
MAX1744
MAX1745
9
EXT
8
VH
μMAX
( ) ARE FOR MAX1745 ONLY.
________________________________________________________________ Maxim Integrated Products
For pricing, delivery, and ordering information, please contact Maxim Direct at 1-888-629-4642,
or visit Maxim's website at www.maxim-ic.com.
1
MAX1744/MAX1745
General Description
MAX1744/MAX1745
High-Voltage, Step-Down DC-DC
Controllers in µMAX
ABSOLUTE MAXIMUM RATINGS
IN, EXT, SHDN to GND...........................................-0.3V to +38V
VH to GND..............................................................-0.3V to +34V
VH, EXT to IN............................................................-7V to +0.3V
CS, OUT to GND ....................................................-0.3V to +20V
FB, 3/5, REF to GND .....................................-0.3V to (VL + 0.3V)
VL to GND...................................................................-0.3V to 6V
Continuous Power Dissipation (TA = +70°C)
10-Pin μMAX (derate 5.6mW/°C above 70°C) .............444mW
Operating Temperature Range
MAX174_EUB ..................................................-40°C to +85°C
MAX174_AUB ................................................-40°C to +125°C
Junction Temperature ......................................................+150°C
Storage Temperature Range .............................-65°C to +150°C
Lead Temperature (soldering, 10s) ................................+300°C
Stresses beyond those listed under “Absolute Maximum Ratings” may cause permanent damage to the device. These are stress ratings only, and functional
operation of the device at these or any other conditions beyond those indicated in the operational sections of the specifications is not implied. Exposure to
absolute maximum rating conditions for extended periods may affect device reliability.
ELECTRICAL CHARACTERISTICS
(VIN = VSHDN = 5.5V to 36V, 3/5 = GND, ILOAD = 0, TA = 0°C to +85°C, unless otherwise noted. Typical values at VIN = VSHDN =
36V, TA = +25°C.)
PARAMETER
CONDITIONS
Input Voltage Range
MIN
MAX
UNITS
36
V
Supply Current into IN
VSHDN = VIN = 5.5V to 36V
90
140
μA
Shutdown Supply Current
SHDN = GND
4
12
μA
Output Voltage (MAX1744)
3/5 = VL
4.85
5.00
5.15
3/5 = GND
3.20
3.30
3.40
28
44
μA
1.25
1.28
V
50
nA
V
OUT Input Current (MAX1744)
3/5 = VL, VOUT = 5V
FB Threshold Voltage (MAX1745)
Falling edge, hysteresis = 8mV
1.22
VH Output Voltage with Respect to IN
VIN = 5.5V to 36V, IVH = 100μA to 20mA
-6.0
-5.3
-4.3
V
VL Output Voltage
VIN = 5.5V to 36V, IVL = 100μA to 2mA
4.5
5.0
5.5
V
V
FB Input Current (MAX1745)
-50
VL Undervoltage Lockout
CS Threshold Voltage
CS Input Current
2.0
3.0
4.1
VCS = VOUT = 2.5V to 18V
85
100
115
VCS = VOUT = VGND
80
110
150
0
15
25
VCS = VOUT = 2.5V to 18V
μA
-25
SHDN, 3/5 Logic-High Threshold
VIN = 4.5V to 36V
2.4
SHDN, 3/5 Logic-Low Threshold
VIN = 4.5V to 36V
0.4
V
3/5 Input Current
SHDN = GND
±1
μA
3/5 = GND
±1
VSHDN = 36V
12
Minimum EXT On-Time
Output Line Regulation
Figure 1, VIN = 12V, 30mA < ILOAD < 2A
Reference Voltage
IREF = 0
REF Load Regulation
REF Line Regulation
μA
8
20
Ω
2.0
2.5
μs
0.7
1.0
1.5
Figure 1, 5.5V < VIN < 36V, ILOAD = 1A
Output Load Regulation
V
1.5
EXT Resistance
Minimum EXT Off-Time
0
mV
VCS = VOUT = VGND
SHDN Input Current
2
TYP
4.5
5
15
1.22
μs
mV/V
mV/A
1.25
1.28
V
0 ≤ IREF ≤ 100μA
4
10
mV
VIN = 4.5V to 36V, IREF = 0
30
60
μV/V
_______________________________________________________________________________________
High-Voltage, Step-Down DC-DC
Controllers in µMAX
(VIN = VSHDN = 5.5V to 36V, 3/5 = GND, ILOAD = 0, TA = -40°C to +85°C, unless otherwise noted.) (Note 1)
PARAMETER
CONDITIONS
Input Voltage Range
MIN
MAX
UNITS
4.5
36
V
Supply Current into IN
VSHDN = VIN = 5.5V to 36V
140
μA
Shutdown Supply Current
SHDN = GND
12
μA
Output Voltage (MAX1744)
3/5 = VL
4.85
5.15
3/5 = GND
3.20
3.40
44
μA
1.28
V
V
OUT Input Current (MAX1744)
3/5 = VL, VOUT = 5V
FB Threshold Voltage (MAX1745)
Falling edge, hysteresis = 8mV
1.22
-50
50
nA
VH Output Voltage with Respect to IN
VIN = 5.5V to 36V, IVH = 100μA to 20mA
-6.0V
-4.3V
V
VL Output Voltage
VIN = 5.5V to 36V, IVL = 100μA to 2mA
4.5
5.5
V
V
FB Input Current (MAX1745)
VL Undervoltage Lockout
CS Threshold Voltage
2.0
4.1
VCS = VOUT = 2.5V to 18V
85
115
VCS = VOUT = VGND
80
150
VCS = VOUT = 2.5V to 18V
mV
0
25
VCS = VOUT = VGND
-25
0
SHDN, 3/5 Logic-High Threshold
VIN = 4.5V to 36V
2.4
SHDN, 3/5 Logic-Low Threshold
VIN = 4.5V to 36V
0.4
V
3/5 Input Current
SHDN = GND
±1
μA
3/5 = GND
±1
VSHDN = 36V
12
CS Input Current
SHDN Input Current
EXT Resistance
μA
V
μA
20
Ω
Minimum EXT Off-Time
1.5
2.5
μs
Minimum EXT On-Time
0.7
1.5
μs
1.22
1.28
V
Reference Voltage
IREF = 0
REF Load Regulation
0 ≤ IREF ≤ 100μA
10
mV
REF Line Regulation
VIN = 4.5V to 36V, IREF = 0
60
μV/V
_______________________________________________________________________________________
3
MAX1744/MAX1745
ELECTRICAL CHARACTERISTICS
MAX1744/MAX1745
High-Voltage, Step-Down DC-DC
Controllers in µMAX
ELECTRICAL CHARACTERISTICS
(VIN = VSHDN = 5.5V to 36V, 3/5 = GND, ILOAD = 0, TA = -40°C to +125°C, unless otherwise noted.) (Note 1)
PARAMETER
CONDITIONS
Input Voltage Range
MIN
MAX
UNITS
4.5
36
V
Supply Current into IN
VSHDN = VIN = 5.5V to 36V
140
μA
Shutdown Supply Current
SHDN = GND
15
μA
Output Voltage (MAX1744)
3/5 = VL
4.85
5.15
3/5 = GND
3.20
3.40
44
μA
1.28
V
OUT Input Current (MAX1744)
3/5 = VL, VOUT = 5V
FB Threshold Voltage (MAX1745)
Falling edge, hysteresis = 8mV
1.22
-50
50
nA
VH Output Voltage with Respect to IN
VIN = 5.5V to 36V, IVH = 100μA to 20mA
-6.0V
-4.3V
V
VL Output Voltage
VIN = 5.5V to 36V, IVL = 100μA to 2mA
4.5
5.5
V
V
FB Input Current (MAX1745)
VL Undervoltage Lockout
CS Threshold Voltage
1.6
4.1
VCS = VOUT = 2.5V to 18V
85
115
VCS = VOUT = VGND
80
150
VCS = VOUT = 2.5V to 18V
mV
0
25
VCS = VOUT = VGND
-25
0
SHDN, 3/5 Logic-High Threshold
VIN = 4.5V to 36V
2.4
SHDN, 3/5 Logic-Low Threshold
VIN = 4.5V to 36V
0.4
V
3/5 Input Current
SHDN = GND
±1
μA
3/5 = GND
±1
VSHDN = 36V
12
CS Input Current
SHDN Input Current
EXT Resistance
μA
V
μA
20
Ω
Minimum EXT Off-Time
1.5
2.5
μs
Minimum EXT On-Time
0.7
1.5
μs
1.22
1.28
V
Reference Voltage
IREF = 0
REF Load Regulation
0 ≤ IREF ≤ 100μA
10
mV
REF Line Regulation
VIN = 4.5V to 36V, IREF = 0
80
μV/V
Note 1: Specifications to -40°C are guaranteed by design, not production tested.
4
V
_______________________________________________________________________________________
High-Voltage, Step-Down DC-DC
Controllers in µMAX
EFFICIENCY vs. LOAD CURRENT
(VOUT = +3.3V)
D
40
A: VIN = +5.5V
B: VIN = +12.0V
C: VIN = +24.0V
D: VIN = +36.0V
20
40
A: VIN = +7.2V
B: VIN = +12.0V
C: VIN = +24.0V
D: VIN = +36.0V
20
0
0.001
0.01
0.1
1
10
0.0001
0.001
0.01
0.1
1
100
95
90
85
80
0
10
10
20
30
40
LOAD CURRENT (A)
LOAD CURRENT (A)
INPUT VOLTAGE (V)
IN PIN QUIESCENT CURRENT
vs. INPUT VOLTAGE (3.5V TO 5.5V)
SWITCHING FREQUENCY
vs. INPUT VOLTAGE
IN PIN QUIESCENT CURRENT
vs. TEMPERATURE
3
2
100
80
60
40
94
VOUT = 3.3V
IOUT = 2.0A
20
VOUT = 3.3V
4.5
92
91
90
89
88
86
85
0
3.5
93
87
1
0
MAX1744/5toc06
120
95
QUIESCENT CURRENT (μA)
4
MAX1744/5toc05
5
140
SWITCHING FREQUENCY (kHz)
MAX1744/5toc04
6
5.5
0
10
20
30
-50
40
-25
0
25
50
75
INPUT VOLTAGE (V)
TEMPERATURE (°C)
EXT RISE AND FALL TIMES
vs. CAPACITANCE
EXT RISE AND FALL TIMES
vs. TEMPERATURE
CURRENT-SENSE TRIP LEVEL
vs. TEMPERATURE
60
tFALL
40
tRISE
35
30
25
tFALL
20
15
10
tRISE
MAX1744/5toc09
MAX1744/5toc08
40
115
CURRENT-SENSE TRIP LEVEL (mV)
80
VIN = +5V
CL = 1000pF
45
tRISE AND tFALL (ns)
100
20
50
MAX1744/5toc07
VIN = +5V
125
100
INPUT VOLTAGE (V)
120
tRISE AND tFALL (ns)
105
0
0.0001
QUIESCENT CURRENT (mA)
D
C
60
MAX1744/5toc03
A
110
QUIESCENT CURRENT (μA)
C
B
80
EFFICIENCY (%)
80
MAX1744/5toc02
B
A
EFFICIENCY (%)
100
MAX1744/5toc01
100
60
IN PIN QUIESCENT CURRENT
vs. INPUT VOLTAGE (5.5V TO 36V)
EFFICIENCY vs. LOAD CURRENT
(VOUT = +5.0V)
110
105
100
95
90
5
0
0
0
1000
2000
3000
CAPACITANCE (pF)
4000
5000
85
-50
-25
0
25
50
75
TEMPERATURE (°C)
100
125
-50
-25
0
25
50
75
100
125
TEMPERATURE (°C)
_______________________________________________________________________________________
5
MAX1744/MAX1745
Typical Operating Characteristics
(Circuit of Figure 1, TA = +25°C, unless otherwise specified.)
Typical Operating Characteristics (continued)
(Circuit of Figure 1, TA = +25°C, unless otherwise specified.)
REFERENCE OUTPUT VOLTAGE CHANGE
vs. TEMPERATURE
MAX1744
ENTERING/EXITING SHUTDOWN
MAX1744/5toc11
MAX1744/5toc10
5
REFERENCE OUTPUT VOLTAGE CHANGE (%)
4
3
2
RL = 3.3Ω
VOUT
2V/div
1
0
-1
SHUTDOWN
PULSE
5V/div
-2
-3
-4
-5
-50
-25
0
25
50
75
100
2ms/div
125
TEMPERATURE (°C)
LOAD-TRANSIENT RESPONSE
LINE-TRANSIENT RESPONSE
A
MAX1744/5toc13
MAX1744/5toc12
MAX1744/MAX1745
High-Voltage, Step-Down DC-DC
Controllers in µMAX
A
B
B
50μs/div
VIN = 7.2V, VOUT = 3.3V, LOAD CURRENT = 0.1A TO 2A
A: VOUT, 50mV/div, 3.3V AC-COUPLED
B: LOAD CURRENT, 1A/div
6
4ms/div
VOUT = 5V, LOAD CURRENT = 1A
A: VOUT, 100mV/div, AC-COUPLED
B: VIN, 6V TO 12V, 5V/div
_______________________________________________________________________________________
High-Voltage, Step-Down DC-DC
Controllers in µMAX
NAME
PIN
FUNCTION
MAX1744
MAX1745
1
GND
GND
2
VL
VL
5V Linear Regulator Output. VL provides power to the internal circuitry and can supply up
to 1mA to an external load. Bypass VL to GND with 4.7μF or greater capacitor.
3
REF
REF
1.25V Reference Output. REF can supply up to 100μA to an external load. Bypass REF to
GND with a 0.1μF or greater ceramic capacitor.
4
3/5
—
3.3V or 5V Selection. Connect 3/5 to GND to set the output voltage to 3.3V. Connect 3/5 to
VL to set the output voltage to 5V.
4
—
FB
Feedback Input for Adjustable Output Operation. Connect to an external voltage-divider
between the output and FB to set the output voltage. The regulation voltage threshold is
1.25V.
5
OUT
OUT
6
CS
CS
7
SHDN
SHDN
8
VH
VH
High-Side Linear Regulator Output. VH provides a regulated output voltage that is 5V below
IN. The external P-channel MOSFET gate is driven between IN and VH. Bypass VH to IN
with a 4.7μF or greater capacitor (see the Capacitor Selection section).
9
EXT
EXT
Gate Drive for External P-Channel MOSFET. EXT swings between IN and VH.
10
IN
IN
Ground
Sense Input for Fixed 5V or 3.3V Output Operation (MAX1744) and Negative Current-Sense
Input (MAX1744/5). OUT is connected to an internal voltage-divider (MAX1744). OUT does
not supply current.
Current-Sense Input. Connect the current-sense resistor between CS and OUT. External
MOSFET is turned off when the voltage across the resistor is equal to or greater than the
current limit trip level (100mV).
Active-Low Shutdown Input. Connect SHDN to IN for normal operation. Drive SHDN to low
to shut the part off. In shutdown mode, the reference, output, external MOSFET, and
internal regulators are turned off.
Positive Supply Input. Bypass IN to GND with a 0.47μF or greater ceramic capacitor.
Detailed Description
The MAX1744/MAX1745 are high-voltage step-down
DC-DC converter controllers. These devices offer high
efficiency over a wide range of input/output voltages
and currents, making them optimal for use in applications such as telecom, automotive, and industrial control. Using an external P-channel MOSFET and
current-sense resistor allows design flexibility and
improved efficiency. The MAX1744/MAX1745 automatically switch from PWM operation at medium and heavy
loads to pulse-skipping operation at light loads to
improve light-load efficiency. The low 90μA quiescent
current further optimizes these parts for applications
where low input current is critical. Operation to 100%
duty cycle allows the lowest possible dropout voltage,
which allows a wider input voltage variation. The small
size, high switching frequency, and low parts count
minimize the required circuit board area and component cost. Figure 1 shows the MAX1744 typical application circuit.
Operating Modes
When delivering low output currents, the MAX1744/
MAX1745 operate in discontinuous-conduction mode.
Current through the inductor starts at zero, rises as
high as the current limit, then ramps down to zero during each cycle (Figure 3). The switch waveform exhibits
ringing, which occurs at the resonant frequency of the
inductor and stray capacitance, due to residual energy
trapped in the core when the commutation diode (D1 in
Figure 1) turns off.
When delivering medium-to-high output currents, the
MAX1744/MAX1745 operate in PWM continuous-conduction mode (Figure 4). In this mode, current always
flows through the inductor and never ramps to zero.
The control circuit adjusts the switch duty cycle to
maintain regulation without exceeding the peak switching current set by the current-sense resistor.
_______________________________________________________________________________________
7
MAX1744/MAX1745
Pin Description
MAX1744/MAX1745
High-Voltage, Step-Down DC-DC
Controllers in µMAX
INPUT
4.5V TO 36V
C2
4.7μF
LOW ESR
C3
4.7μF
D2
0.47μF
5V
VH
IN
ON
OFF
SHDN
3.3V
3/5
EXT
MAX1744
VL
P M1
FAIRCHILD
NDS9407
L1
22μH
CS
OUT
REF
GND
D1
NIHON
EC2IQ506
RSENSE
40mΩ
OUT
3.3V OR 5V
2A
C1
220μF
Figure 1. Typical Application Circuit
100% Duty Cycle and Dropout
The MAX1744/MAX1745 operate with a duty cycle up to
100%. This feature extends the input voltage range by
turning the MOSFET on continuously when the supply
voltage approaches the output voltage. This services
the load when conventional switching regulators with
less than 100% duty cycle would fail. Dropout voltage is
defined as the difference between the input and output
voltages when the input is low enough for the output to
drop out of regulation. Dropout depends on the
MOSFET drain-to-source on-resistance, current-sense
resistor, and inductor series resistance, and is proportional to the load current:
Dropout voltage=
IOUT x ⎡⎣ R DS(ON) + R SEN
NSE + RINDUCTOR ⎤⎦
Regulation Control Scheme
The MAX1744/MAX1755 have a unique operating
scheme that allows PWM operation at medium and high
current, with automatic switching to pulse-skipping
mode at lower currents to improve light-load efficiency.
Figure 2 shows the simplified block diagram.
Under medium- and heavy-load operation, the inductor
current is continuous and the part operates in PWM
mode. In this mode, the switching frequency is set by
either the 1μs minimum on-time or the 2μs minimum offtime, depending on the duty cycle. The duty cycle is
approximately the output voltage divided by the input
voltage. If the duty cycle is less than 33%, the minimum
on-time controls the frequency; and the frequency is
approximately f ≈ 1MHz ✕ D, where D is the duty cycle.
8
If the duty cycle is greater than 33%, the off-time sets the
frequency; and the frequency is approximately f ≈ 500kHz
✕ (1 - D).
In both cases, the voltage is regulated by the error
comparator. For low duty cycles (33%), the
MOSFET remains off for the minimum off-time, causing
fixed-off-time operation. In this case, the MOSFET
remains on until the output voltage rises to the regulation threshold. Then the MOSFET turns off for the minimum off-time, initiating another cycle.
By switching between fixed-on-time and fixed-off-time
operation, the MAX1744/MAX1745 can operate at high
input-output ratios, yet still operate up to 100% duty
cycle for low dropout. Note that when transitioning from
fixed-on-time to fixed-off-time operation, the output voltage drops slightly due to the output ripple voltage. In
fixed-on-time operation, the minimum output voltage is
regulated, but in fixed-off-time operation, the maximum
output voltage is regulated. Thus, as the input voltage
drops below approximately three times the output voltage, a decrease in line regulation can be expected.
The drop in voltage is approximately VDROP ≈ VRIPPLE / 2.
At light output loads, the inductor current is discontinuous, causing the MAX1744/MAX1745 to operate at
_______________________________________________________________________________________
High-Voltage, Step-Down DC-DC
Controllers in µMAX
MAX1744/MAX1745
EXT
IN
REF
VH
SHDN
VH
LINEAR
REGULATOR
VL
VL
LINEAR
REGULATOR
Q
1.25
REFERENCE
TRIG
MINIMUM
ON-TIME
ONE SHOT
OUT
ERROR
COMPARATOR
Q
(FB)
TRIG
MINIMUM
OFF-TIME
ONE SHOT
3/5
Q
S
R
( ) MAX1745 ONLY
- - - MAX1744 ONLY
SHDN
- +
CS
100mV
Figure 2. Simplified Functional Diagram
lower frequencies, reducing the MOSFET gate drive
and switching losses. In discontinuous mode, under
most circumstances, the on-time will be the fixed minimum on-time of 1μs. If the inductor value is small, or
the current-sense resistor large, the current limit will be
tripped before the minimum on-time, terminating the
on-time and thus setting the fixed on-time.
If the inductance is too large, or the output capacitance
high and equivalent series resistance (ESR) low, then
the MOSFET remains on longer than the minimum ontime, until the output capacitor charges beyond the
error comparator’s (VOUT / 1.25V) ✕ 8mV hysteresis,
causing the part to operate in hysteretic mode.
Operating in hysteretic mode results in lower frequency
operation. The transition to hysteretic mode occurs at
the critical output capacitor ESR:
where IRIPPLE is the inductor ripple current, and can be
determined by:
IRIPPLE = (VIN - VOUT) ✕ tON(MIN) / L
where tON(MIN) is the minimum on-time (1μs) for minimum on-time-control, or:
IRIPPLE = (VOUT) ✕ tOFF(MIN) / L
where tOFF(MIN) is the minimum off-time (2μs) for minimum off-time-control.
ESRCRITICAL = (VOUT / 1.25V) ✕ 8mV / IRIPPLE
_______________________________________________________________________________________
9
MAX1744/MAX1745
High-Voltage, Step-Down DC-DC
Controllers in µMAX
A
A
B
B
C
C
10μs/div
10μs/div
CIRCUIT OF FIGURE 1, VIN = 18V, VOUT = 3.3V, ILOAD = 100mA
A: MOSFET DRAIN, 10V/div
B: OUT, 50mV/div, 3.3V DC OFFSET
C: INDUCTOR CURRENT, 1A/div
CIRCUIT OF FIGURE 1, VIN = 18V, VOUT = 3.3V, ILOAD = 1.5A
A: MOSFET DRAIN, 10V/div
B: OUT, 50mV/div, 3.3V DC OFFSET
C: INDUCTOR CURRENT, 1A/div
Figure 3. Discontinuous-Conduction Mode, Light-Load-Current
Waveform
Figure 4. Continuous-Conduction Mode, Heavy-Load-Current
Waveform
VL Linear Regulator
Shutdown Mode
The MAX1744/MAX1745 contain a 5V low-side linear regulator (VL) that powers the internal circuit and can supply
up to 1mA to an external load. This allows the
MAX1744/MAX1745 to operate up to 36V input, while
maintaining low quiescent current and high switching frequency. When the input voltage goes below 5.5V, this
regulator goes into dropout and the IN pin quiescent current will rise. See the Typical Operating Characteristics.
Bypass VL with a 4.7μF or greater capacitor.
When SHDN is low, the device enters shutdown mode. In
this mode, the internal circuitry is turned off. EXT is pulled
to IN, turning off the external MOSFET. The shutdown
supply current drops to less than 10μA. SHDN is a logiclevel input. Connect SHDN to IN for normal operation.
VH Linear Regulator
The MAX1744/MAX1745 contain a high-side linear regulator (VH) that regulates its output to 5V below IN (the
positive supply input voltage). This regulator limits the
external P-channel MOSFET gate swing (EXT), allowing
high input voltage operation without exceeding the
MOSFET gate-source breakdown. Bypass VH with a
4.7μF or greater capacitor between IN and VH. Fast line
transients may drive the voltage on VH negative. The
clamp diode (D2) prevents damage to the IC during
such a condition. A Schottky diode with a minimum 40V
reverse rating such as the Nihon EP05Q04 is sufficient
for most applications.
Quiescent Current
The devices’ typical quiescent current is 90μA.
However, actual applications draw additional current to
supply MOSFET switching currents, OUT pin current,
external feedback resistors (if used), and both the diode
and capacitor leakage currents. For example, in the circuit of Figure 1, with IN at 30V and VOUT at 5V, typical
no-load supply current for the entire circuit is 100μA.
10
Reference
The 1.25V reference is suitable for driving small external
loads. It has a guaranteed 10mV maximum load regulation while sourcing load currents up to 100μA. The reference is turned off during shutdown. Bypass the
reference with 0.1μF for normal operation. Place the
bypass capacitor within 0.2in (5mm) of REF, with a direct
trace to GND.
Design Information
Setting the Output Voltage
The MAX1744’s output voltage can be selected to 3.3V
or 5V under logic control by using the 3/5 pin. Connect
the 3/5 pin to GND to ensure a 3.3V output, or connect
the 3/5 pin to VL to ensure a 5V output.
The MAX1745’s output voltage is set using two resistors, R2 and R3 (Figure 5), which form a voltage-divider
between the output and FB. R2 is given by:
⎛V
⎞
R2= R3 x ⎜ OUT − 1⎟
⎝ VREF
⎠
where VREF = 1.25V. Since the input bias current at FB
has a maximum value of 50nA, large values (10kΩ to
200kΩ) can be used for R3 with no significant accuracy
______________________________________________________________________________________
High-Voltage, Step-Down DC-DC
Controllers in µMAX
Current-Sense-Resistor Selection
The current-sense comparator limits the peak switching
current to VCS/RSENSE, where RSENSE is the value of
the current-sense resistor and VCS is the current-sense
threshold. VCS is typically 100mV. Minimizing the peak
switching current will increase efficiency and reduce
the size and cost of external components. However,
since available output current is a function of the peak
switching current, the peak current limit must not be set
too low.
Set the peak current limit to 1.3 times the maximum
load current by setting the current-sense resistor to:
R CS =
VCS(MIN)
1.3 x IOUT(MAX)
Inductor Selection
The essential parameters for inductor selection are inductance and current rating. The MAX1744/MAX1745 operate with a wide range of inductance values. In many
applications, values between 4.7μH and 100μH take best
advantage of the controller’s high switching frequency.
Calculate the minimum inductance value as follows:
L (MIN) =
( VIN - VOUT ) x 1μs
VCS(MIN)
R CS
where 1μs is the minimum on-time. Inductor values
between 2 and 10 times L(MIN) are recommended. With
high inductor values, the MAX1744/MAX1745 begin
continuous-conduction operation at a lower fraction of
the full load (see the Detailed Description section).
The inductor’s saturation and heating current ratings
must be greater than the peak switching current to prevent overheating and core saturation. Saturation occurs
when the inductor’s magnetic flux density reaches the
maximum level the core can support, and inductance
starts to fall. The heating current rating is the maximum
DC current the inductor can sustain without overheating.
For optimum efficiency, the inductor windings’ resistance should be less than the current-sense resistance.
If necessary, use a toroid, pot-core, or shielded-core
inductor to minimize radiated noise. Table 1 lists inductor types and suppliers for various applications.
FROM
OUTPUT
R2
TO FB
R3
Figure 5. Adjustable-Output Operation Using the MAX1745
External Switching Transistor
The MAX1744/MAX1745 drive a P-channel enhancement-mode MOSFET. The EXT output swings from VH
to IN. Be sure that the MOSFET’s on-resistance is specified for 5V gate drive or less. Table 1 recommends
MOSFET suppliers.
Four important parameters for selecting a P-channel
MOSFET are drain-to-source breakdown voltage, current rating, total gate charge (Qg), and RDS(ON). The
drain-to-source breakdown voltage rating should be at
least a few volts higher than VIN. Choose a MOSFET
with a maximum continuous drain-current rating higher
than the peak current limit:
VCS(MAX)
ID(MAX) ≥ ILIM(MAX) =
R SENSE
The Qg specification should be 80nC or less to ensure
fast drain voltage rise and fall times, and reduce power
losses during transition through the linear region. Qg
specifies all of the capacitances associated with charging
the MOSFET gate. EXT pin rise and fall times vary with different capacitive loads, as shown in the Typical Operating
Characteristics. RDS(ON) should be as low as practical to
reduce power losses while the MOSFET is on. It should
be equal to or less than the current-sense resistor.
______________________________________________________________________________________
11
MAX1744/MAX1745
loss. For 1% error, the current through R2 should be at
least 100 times FB’s input bias current.
MAX1744/MAX1745
High-Voltage, Step-Down DC-DC
Controllers in µMAX
Capacitor Selection
Table 1. Component Suppliers
COMPANY
COUNTRY
PHONE
FAX
803-946-0690
AVX
USA
803-626-3123
or
800-282-4975
Coilcraft
USA
847-639-6400
847-639-1469
Coiltronics
USA
516-241-7876
516-241-9339
Dale/Vishay
USA
402-564-3131
402-563-6418
Kemet
USA
408-986-0424
408-986-1442
International
Rectifier
USA
310-322-3331
310-322-3332
IRC
USA
512-992-7900
512-992-3377
Motorola
USA
602-303-5454
602-994-6430
Nichicon
USA
Japan
847-843-7500
81-7-5231-8461
847-843-2798
81-7-5256-4158
Nihon
USA
Japan
805-867-2555
81-3-3494-7411
805-867-2698
81-3-3494-7414
Sanyo
USA
Japan
619-661-6835
81-7-2070-6306
619-661-1055
81-7-2070-1174
Choose filter capacitors to service input and output
peak currents with acceptable voltage ripple. ESR in
the output capacitor is a major contributor to output ripple, so low-ESR capacitors are recommended. LowESR tantalum, polymer, or ceramic capacitors are best.
Low-ESR aluminum electrolytic capacitors are tolerable, but standard aluminum electrolytic capacitors are
not recommended.
Voltage ripple is the sum of contributions from ESR and
the capacitor value:
VRIPPLE ≈ VRIPPLE,ESR + VRIPPLE,C
For tantalum capacitors, the ripple is determined by the
ESR, but for ceramic capacitors, the ripple is mostly
due to the capacitance. Voltage ripple as a consequence of ESR is approximated by:
VRIPPLE,ESR ≈ (R ESR )Δ Ip −p
The ripple due to the capacitance is approximately:
VRIPPLE,C ≈
408-988-8000
Siliconix
USA
or
408-970-3950
800-554-5565
Sprague
USA
603-224-1961
603-224-1430
Sumida
USA
Japan
847-956-0666
81-3-3607-5111
847-956-0702
81-3-3607-5144
USA
714-255-9500
714-255-9400
United
Chemi-Con
LI 2 PEAK
2CVO
Estimate input and output capacitor values for given
voltage ripple as follows:
C IN =
1 LI 2
2 ΔL
VRIPPLE,CINVIN
C OUT =
1 LI 2
2 ΔL
⎛
⎞
VIN
⎜
VRIPPLE,COUT VOUT ⎝ VIN − VOUT ⎟⎠
Diode Selection
The MAX1744/MAX1745’s high switching frequency
demands a high-speed rectifier. Schottky diodes, such
as the 1N5817–1N5822 family or surface-mount equivalents, are recommended. Ultra-high-speed rectifiers
with reverse recovery times around 50ns or faster
should be used for high output voltages, where the
increased forward drop causes less efficiency degradation. Make sure that the diode’s peak current rating
exceeds the peak current limit set by RSENSE, and that
its breakdown voltage exceeds VIN. Schottky diodes
are preferred for heavy loads due to their low forward
voltage, especially in low-voltage applications. For
high-temperature applications, some Schottky diodes
may be inadequate due to their high leakage currents.
In such cases, ultra-high-speed rectifiers are recommended, although a Schottky diode with a higher
reverse voltage rating can often provide acceptable
performance.
12
where IΔL is the change in inductor current.
These equations are suitable for initial capacitor selection; final values should be set by testing a prototype or
evaluation kit. When using tantalum capacitors, use
good soldering practices to prevent excessive heat
from damaging the devices and increasing their ESR.
Also, ensure that the tantalum capacitors’ surge-current
ratings exceed the startup inrush and peak switching
currents.
Pursuing output ripple lower than the error comparator’s hysteresis (0.6% of the output voltage) is not practical, since the MAX1744/MAX1745 will switch at slower
frequencies, increasing inductor ripple current threshold. Choose an output capacitor with a working voltage
rating higher than the output voltage.
The input filter capacitor reduces peak currents drawn
from the power source and reduces noise and voltage
______________________________________________________________________________________
High-Voltage, Step-Down DC-DC
Controllers in µMAX
degrade performance. The current-sense resistor must
be placed within 0.2 inches (5mm) of the controller IC,
directly between OUT and CS. Place voltage feedback
resistors (MAX1745) next to the FB pin (no more than
0.2in) rather than near the output. Place the 0.47μF input
bypass capacitor within 0.2in (5mm) of IN.
Refer to the MAX1744 Evaluation Kit manual for a twolayer PC board example.
Chip Information
PROCESS: BiCMOS
Layout Considerations
High-frequency switching regulators are sensitive to PC
board layout. Poor layout introduces switching noise into
the current and voltage feedback signals and may
______________________________________________________________________________________
13
MAX1744/MAX1745
ripple at IN, caused by the circuit’s switching action.
Use a low-ESR capacitor. Two smaller-value low-ESR
capacitors can be connected in parallel if necessary.
Choose input capacitors with working voltage ratings
higher than the maximum input voltage.
Place a surface-mount ceramic capacitor very close to
IN and GND. This capacitor bypasses the MAX1744/
MAX1745, minimizing the effects of spikes and ringing
on the power source (IN).
Bypass REF with 0.1μF. This capacitor should be
placed within 0.2 inches (5mm) of the IC, next to REF,
with a direct trace to GND.
Package Information
For the latest package outline information and land patterns, go to www.maxim-ic.com/packages.
PACKAGE TYPE
PACKAGE CODE
DOCUMENT NO.
10 μMAX
U10CN+1
21-0061
10LUMAX.EPS
MAX1744/MAX1745
High-Voltage, Step-Down DC-DC
Controllers in µMAX
α
α
Note: MAX1744/MAX1745 do not feature exposed pads.
14
______________________________________________________________________________________
High-Voltage, Step-Down DC-DC
Controllers in µMAX
PAGES
CHANGED
REVISION
NUMBER
REVISION
DATE
0
7/00
Initial release.
—
2
8/06
—
—
3
4/09
Added lead-free and automotive qualified packages to Ordering Information.
4
8/09
Added MAX1744 automotive package to Ordering Information.
DESCRIPTION
1–4, 10, 13
1
Maxim cannot assume responsibility for use of any circuitry other than circuitry entirely embodied in a Maxim product. No circuit patent licenses are
implied. Maxim reserves the right to change the circuitry and specifications without notice at any time.
Maxim Integrated Products, 120 San Gabriel Drive, Sunnyvale, CA 94086 408-737-7600 ____________________ 15
© 2009 Maxim Integrated Products
Maxim is a registered trademark of Maxim Integrated Products, Inc.
MAX1744/MAX1745
Revision History
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